Power stabilizing circuit

Abstract

The utility model discloses a power stabilizing circuit, which comprises a transformer, a primary side winding of the transformer is connected with a power supply voltage through a voltage regulation module, a secondary side winding of the transformer is used for being connected with a load, and the secondary side winding is provided with a tap; the output end of the phase-locked loop is electrically connected with the primary side winding, the input end of the phase-locked loop is electrically connected with the tap, the phase-locked loop is used for enabling phase synchronization between a signal output by the phase-locked loop and a signal input by the phase-locked loop, and an initial output signal of the phase-locked loop works at the estimated resonant frequency of the load; the inverted input end of the first comparator is electrically connected with the tap, the inverted input end of the first comparator is further electrically connected with a signal control port, the signal control port is used for inputting a power control signal, and the in-phase input end of the first comparator is electrically connected with the output end of the phase-locked loop; the output end of the first comparator is electrically connected with the control end of the voltage adjusting module. According to the embodiment provided by the invention, the power stability can be improved.

Description

Technical Field

[0001] This application relates to the field of power electronics technology, and in particular to a power stabilization circuit. Background Technology

[0002] Currently, the resonant point of some load systems changes constantly, but the corresponding drive circuits cannot effectively track it. For example, a load system consisting of an ultrasonic generator, a liquid medium, and a sample will change constantly due to factors such as temperature, liquid level, stirrer disturbance, and the properties of the medium and sample. However, some traditional ultrasonic drive circuits usually operate at a fixed frequency and cannot track the resonant point by frequency conversion. Other traditional ultrasonic drive circuits use a combination of a microcontroller and an analog-to-digital converter to track power fluctuations in software to make stable adjustments, which is costly and has low real-time performance. Utility Model Content

[0003] The following is an overview of the subject matter described in detail herein, and this overview is not intended to limit the scope of the claims.

[0004] This application proposes a power stabilization circuit that can improve the real-time performance of tracking the resonant point, thereby improving power stability.

[0005] This application provides a power stabilization circuit, comprising: a transformer, wherein the primary winding of the transformer is connected to a power supply voltage via a voltage regulation module, the secondary winding of the transformer is used to connect a load, and a tap is provided on the secondary winding; a phase-locked loop (PLL), wherein the output terminal of the PLL is electrically connected to the primary winding, the input terminal of the PLL is electrically connected to the tap, the PLL is used to synchronize the phase of the signal output by the PLL with the signal input by the PLL, and the initial output signal of the PLL operates at the estimated resonant frequency of the load; a first comparator, wherein the inverting input terminal of the first comparator is electrically connected to the tap, the inverting input terminal of the first comparator is also electrically connected to a signal control port, the signal control port is used to input a power control signal, the non-inverting input terminal of the first comparator is electrically connected to the output terminal of the PLL, and the output terminal of the first comparator is electrically connected to the control terminal of the voltage regulation module, the first comparator is used to control the operating state of the voltage regulation module.

[0006] In some embodiments, the input terminal of the phase-locked loop is electrically connected to the tap via a shaping and amplification module. The shaping and amplification module includes a first shaper and a first amplifier. The tap is electrically connected to the inverting input terminal of the first shaper, the output terminal of the first shaper is electrically connected to the inverting input terminal of the first amplifier, the output terminal of the first amplifier is electrically connected to the input terminal of the phase-locked loop, and both the non-inverting input terminal of the first shaper and the non-inverting input terminal of the first amplifier are connected to a bias voltage.

[0007] In some embodiments, the voltage regulation module is provided with a voltage input terminal and a voltage output terminal. The voltage input terminal is electrically connected to the power supply voltage, and the voltage output terminal is electrically connected to the primary winding of the transformer. When the voltage regulation module is in a first operating state, the voltage at the voltage output terminal increases, and when the voltage regulation module is in a second operating state, the voltage at the voltage output terminal decreases.

[0008] In some embodiments, the inverting input of the first comparator is electrically connected to the tap via a negative charge pump.

[0009] In some embodiments, the inverting input of the first comparator is electrically connected to the negative charge pump via a second amplifier, and the inverting input of the first comparator is also electrically connected to a signal control port via the second amplifier. The output of the second amplifier is electrically connected to the inverting input of the first comparator, the non-inverting input of the second amplifier is electrically connected to the negative charge pump, the non-inverting input of the second amplifier is also electrically connected to the signal control port, and the inverting input of the second amplifier is also electrically connected to the output of the second amplifier.

[0010] In some embodiments, the output terminal of the phase-locked loop is electrically connected to the primary winding via a transformer drive module. The transformer drive module includes a gate driver, a forward output circuit, and a reverse output circuit. The control terminal of the gate driver is electrically connected to the output terminal of the phase-locked loop. The forward output terminal of the gate driver is electrically connected to one end of the primary winding via the forward output circuit, and the reverse output terminal of the gate driver is electrically connected to the other end of the primary winding via the reverse output circuit. The gate driver is used to control the operating states of the forward output circuit and the reverse output circuit to be opposite.

[0011] In some embodiments, the forward output circuit includes a forward conducting element, the reverse output circuit includes a reverse conducting element, the forward output terminal is electrically connected to the control terminal of the forward conducting element, the first conducting terminal of the forward conducting element is electrically connected to one end of the primary winding, the reverse output terminal is electrically connected to the control terminal of the reverse conducting element, the first conducting terminal of the reverse conducting element is electrically connected to the other end of the primary winding, and the second conducting terminal of the forward conducting element is electrically connected to the second conducting terminal of the reverse conducting element.

[0012] In some embodiments, a power protection module is further included, wherein the input terminal of the power protection module is electrically connected to the second conducting terminal of the forward conducting element, the input terminal of the power protection module is also electrically connected to the second conducting terminal of the reverse conducting element, and the output terminal of the power protection module is electrically connected to the inverting input terminal of the first comparator.

[0013] In some embodiments, the phase-locked loop is electrically connected to the non-inverting input of the first comparator via a second shaper.

[0014] In some embodiments, the phase-locked loop includes a phase detector, a loop filter, and a voltage-controlled oscillator (VCO). The output of the phase detector is connected to the control terminal of the VCO through the loop filter. The output of the VCO is electrically connected to the first input of the phase detector. The second input of the phase detector is the input of the phase-locked loop, and the output of the VCO is the output of the phase-locked loop.

[0015] The embodiments of this application include at least the following beneficial effects: Since the secondary winding of the transformer is used to connect the load, and taps are provided on the secondary winding, the phase change of the tap signal can reflect the phase change of the load signal. Furthermore, since the output terminal of the phase-locked loop (PLL) is electrically connected to the primary winding of the transformer, and the input terminal of the PLL is electrically connected to the taps, the PLL can synchronize the phase between the signal output to the primary winding and the signal input from the taps, effectively synchronizing the phase between the signal output to the primary winding and the load signal. Since the initial output signal of the PLL operates at the estimated resonant frequency of the load, and the phase synchronization of the PLL is accompanied by frequency synchronization, when the load's resonant point changes, the frequency of the primary winding signal can match the current resonant frequency of the load in real time. Therefore, when the signal from the primary winding is output to the load through the secondary winding, real-time tracking of the load's resonant point is achieved. Simultaneously, the components used in the circuit have high response speed. Higher-quality basic components improve the real-time performance of tracking the load resonant point, thereby enhancing power efficiency and stability. Furthermore, the output of the first comparator is electrically connected to the control terminal of the voltage regulation module, and the primary winding is supplied with voltage through the voltage regulation module. Therefore, the first comparator can control the power supply state of the voltage regulation module to the primary winding. Simultaneously, the inverting input of the first comparator is electrically connected to a tap and also to a signal control port. Since changes in the signal strength of the tap reflect changes in the load's power, the signal control port is used to input a power control signal. This allows changes in the load's power drift to affect the power control signal at the inverting input of the first comparator. Additionally, the non-inverting input of the first comparator is electrically connected to the output of the phase-locked loop (PLL). Essentially, the first comparator uses the PLL's output signal as a reference signal, combining it with power drift changes to optimize the power supply state of the primary winding, resulting in more efficient and stable power delivery to the load.

[0016] Other features and advantages of this application will be set forth in the following description and will be apparent in part from the description or may be learned by practicing the application. The objectives and other advantages of this application may be realized and obtained by means of the structures particularly pointed out in the description, claims and drawings. Attached Figure Description

[0017] The accompanying drawings are used to provide a further understanding of the technical solutions of this application and constitute a part of the specification. They are used together with the embodiments of this application to explain the technical solutions of this application and do not constitute a limitation on the technical solutions of this application.

[0018] Figure 1 A system block diagram of the power stabilization circuit provided in the embodiments of this application;

[0019] Figure 2An optional circuit schematic diagram of a phase-locked loop and shaping amplification module provided in an embodiment of this application;

[0020] Figure 3 An optional circuit schematic diagram of a transformer and transformer drive module provided in an embodiment of this application;

[0021] Figure 4 An optional circuit schematic diagram of the power regulation circuit provided in an embodiment of this application;

[0022] Figure 5 This is an optional circuit schematic diagram of the voltage regulation module provided in an embodiment of this application. Detailed Implementation

[0023] The embodiments of this application are described in detail below. Examples of the embodiments are shown in the accompanying drawings, wherein the same or similar reference numerals denote the same or similar elements or elements having the same or similar functions throughout. The embodiments described below with reference to the accompanying drawings are exemplary and are only used to explain this application, and should not be construed as limiting this application.

[0024] In the description of this application, it should be understood that the orientation descriptions, such as up, down, front, back, left, right, etc., indicate the orientation or positional relationship based on the orientation or positional relationship shown in the accompanying drawings. They are only for the convenience of describing this application and simplifying the description, and do not indicate or imply that the device or element referred to must have a specific orientation, or be constructed and operated in a specific orientation. Therefore, they should not be construed as limitations on this application.

[0025] In the description of this application, "several" means one or more, "more than" means two or more, "greater than," "less than," and "exceeding" are understood to exclude the stated number, while "above," "below," and "within" are understood to include the stated number. The use of "first" and "second" in the description is merely for distinguishing technical features and should not be construed as indicating or implying relative importance, or implicitly indicating the number of indicated technical features, or implicitly indicating the order of the indicated technical features.

[0026] In the description of this application, unless otherwise expressly defined, terms such as "setup," "installation," and "connection" should be interpreted broadly, and those skilled in the art can reasonably determine the specific meaning of the above terms in this application in conjunction with the specific content of the technical solution.

[0027] Currently, the resonant point of some load systems changes constantly, but the corresponding drive circuits cannot effectively track it. For example, a load system consisting of an ultrasonic generator, a liquid medium, and a sample will change constantly due to factors such as temperature, liquid level, stirrer disturbance, and the properties of the medium and sample. However, some traditional ultrasonic drive circuits usually operate at a fixed frequency and cannot track the resonant point by frequency conversion. Other traditional ultrasonic drive circuits use a combination of a microcontroller and an analog-to-digital converter to track power fluctuations in software to make stable adjustments, which is costly and has low real-time performance.

[0028] To address the issues of low real-time performance and poor power stability in tracking resonant points, this application provides a power stabilization circuit. This circuit includes: a transformer, whose primary winding is connected to the power supply voltage via a voltage regulation module, and whose secondary winding is used to connect to the load; a phase-locked loop (PLL), whose output is electrically connected to the primary winding, and whose input is electrically connected to the tap; the PLL is used to synchronize the phase of its output signal with the input signal, and the initial output signal of the PLL operates at the estimated resonant frequency of the load; and a first comparator, whose inverting input is electrically connected to the tap and also to a signal control port for inputting a power control signal; its non-inverting input is electrically connected to the output of the PLL; and its output is electrically connected to the control terminal of the voltage regulation module; the first comparator is used to control the operating state of the voltage regulation module. According to the solution provided in the embodiments of this application, since the secondary winding of the transformer is used to connect the load, and taps are provided on the secondary winding of the transformer, the phase change of the tap signal can reflect the phase change of the load signal. Furthermore, since the output terminal of the phase-locked loop (PLL) is electrically connected to the primary winding of the transformer, and the input terminal of the PLL is electrically connected to the taps, the PLL can synchronize the phase between the signal output to the primary winding and the signal input from the taps, which is equivalent to synchronizing the phase between the signal output to the primary winding and the load signal. Since the initial output signal of the PLL operates at the estimated resonant frequency of the load, and the phase synchronization of the PLL is accompanied by frequency synchronization, when the resonant point of the load changes, the frequency of the primary winding signal can match the current resonant frequency of the load in real time. Therefore, when the signal from the primary winding is output to the load through the secondary winding, real-time tracking of the load resonant point is achieved. Simultaneously, the components used in the circuit have a relatively fast response speed. High-performance components improve the real-time tracking of the load resonant point, thereby enhancing power efficiency and stability. Furthermore, the output of the first comparator is electrically connected to the control terminal of the voltage regulation module, and the primary winding is supplied with voltage through the voltage regulation module. Therefore, the first comparator can control the power supply state of the voltage regulation module to the primary winding. Simultaneously, the inverting input of the first comparator is electrically connected to a tap and also to a signal control port. Since changes in the signal strength of the tap reflect changes in the load's power, the signal control port is used to input a power control signal. This allows changes in the load's power drift to affect the power control signal at the inverting input of the first comparator. Additionally, the non-inverting input of the first comparator is electrically connected to the output of the phase-locked loop (PLL). Essentially, the first comparator uses the PLL's output signal as a reference signal, combining power drift changes to optimize the power supply state of the primary winding, resulting in more efficient and stable power delivery to the load.

[0029] The embodiments of this application will be further described below with reference to the accompanying drawings.

[0030] Reference Figure 1 , Figure 1 This is a system block diagram of a power stabilization circuit provided in an embodiment of this application. The embodiment of this application provides a power stabilization circuit, including:

[0031] Transformer 100, the primary winding 110 of transformer 100 is connected to the power supply voltage 530 through voltage regulation module 500, the secondary winding 120 of transformer 100 is used to connect the load 410, and a tap 200 is provided on the secondary winding 120.

[0032] Phase-locked loop 300, the output terminal of phase-locked loop 300 is electrically connected to the primary winding 110, and the input terminal of phase-locked loop 300 is electrically connected to tap 200. Phase-locked loop 300 is used to synchronize the phase of the signal output by phase-locked loop 300 with the signal input by phase-locked loop 300. The initial output signal of phase-locked loop 300 operates at the estimated resonant frequency of load 410.

[0033] The first comparator 400 has its inverting input terminal electrically connected to tap 200 and also electrically connected to signal control port 420, which is used to input power control signals. The non-inverting input terminal of the first comparator 400 is electrically connected to the output terminal of phase-locked loop 300, and the output terminal of the first comparator 400 is electrically connected to the control terminal of voltage regulation module 500. The first comparator 400 is used to control the operating state of voltage regulation module 500.

[0034] Among them, the output signal of the phase-locked loop 300 is a square wave signal, and the load 410 is an ultrasonic generator. Due to the constant changes in factors such as temperature, liquid level, stirrer disturbance, medium and sample properties, the resonant point of the ultrasonic generator changes constantly. The load feedback signal corresponding to the ultrasonic generator is a sine wave signal. In addition, the load can also be other devices or systems whose resonant points change constantly.

[0035] The load 410 is electrically connected to the secondary winding 120 of the transformer 100 via the port PROBE_OUT.

[0036] The tap 200 is located between the upper and lower ends of the secondary winding 120.

[0037] It should be noted that the estimated resonant frequency was calculated in advance based on the load 410 and the overall circuit system before the load 410 was started.

[0038] It should be noted that PWM pulse signal, or Pulse Width Modulation (PWM), is a technique used to regulate the output signal in electronic devices. PWM controls the average level of the signal by changing the pulse width of the signal.

[0039] Specifically, the square wave signal output by the phase-locked loop 300 can be converted into a sawtooth wave signal before being output to the non-inverting input of the first comparator 400. The sawtooth wave signal is used as the reference signal input to the non-inverting input of the first comparator 400. When the signal amplitude at the inverting input of the first comparator 400 is less than or equal to the reference signal amplitude, the first comparator 400 outputs a high level; when the signal amplitude at the inverting input of the first comparator 400 is greater than the reference signal amplitude, the first comparator 400 outputs a low level. Specifically, the signal amplitude at the inverting input of the first comparator 400 is compared with the sawtooth wave signal amplitude to determine the width of the PWM pulse signal output by the first comparator 400. When the voltage at the inverting input of the first comparator 400 decreases, the high-level duty cycle of the PWM pulse signal increases; when the voltage at the inverting input of the first comparator 400 increases, the low-level duty cycle of the PWM pulse signal increases.

[0040] The power control signal can be an externally input control signal. For example, if a user wants to adjust the power of the load 410, they can connect the signal control port 420 through the signal generation module of the peripheral device to input a power control signal that meets the target power.

[0041] Based on this, since the secondary winding 120 of transformer 100 is used to connect the load 410, and a tap 200 is provided on the secondary winding 120 of transformer 100, the phase change of the signal at tap 200 can reflect the phase change of the signal at load 410. Furthermore, since the output terminal of phase-locked loop 300 is electrically connected to the primary winding 110 of transformer 100, and the input terminal of phase-locked loop 300 is electrically connected to tap 200, phase-locked loop 300 can synchronize the phase of the signal output to the primary winding 110 with the phase of the signal input from tap 200, effectively synchronizing the phase of the output signal to the primary winding 110 with the phase of the signal input from tap 200. The signal output to the primary winding 110 is phase-synchronized with the signal of the load 410. Since the initial output signal of the phase-locked loop 300 operates at the estimated resonant frequency of the load 410, and the phase synchronization of the phase-locked loop 300 is accompanied by frequency synchronization, the frequency of the signal from the primary winding 110 can match the current resonant frequency of the load 410 in real time when the resonant point of the load 410 changes. Therefore, when the signal from the primary winding 110 is output to the load 410 through the secondary winding 120, real-time tracking of the resonant point of the load 410 is achieved. Simultaneously, the components used in the circuit are high-response-rate... The use of high-precision basic components can improve the real-time performance of tracking the resonant point of the load 410, thereby improving the effectiveness and stability of power. Furthermore, the output of the first comparator 400 is electrically connected to the control terminal of the voltage regulation module 500, and the primary winding 110 is connected to the voltage regulation module 500 for voltage supply. Therefore, the first comparator 400 can control the power supply state of the voltage regulation module 500 to the primary winding 110. Simultaneously, the inverting input of the first comparator 400 is electrically connected to the tap 200, and also to the signal control port 420. Since the signal strength change of tap 200 can reflect the power change of load 410, the signal control port 420 is used to input the power control signal, so that the power drift change of load 410 can affect the power control signal on the inverting input of the first comparator 400. Furthermore, the non-inverting input of the first comparator 400 is electrically connected to the output of the phase-locked loop 300. This means that the first comparator 400 uses the output signal of the phase-locked loop 300 as a reference signal and optimizes the power supply state of the primary winding 110 in combination with the power drift change, making the power transmitted to the load 410 more efficient and stable.

[0042] Additionally, refer to Figure 2 , Figure 2 This is an optional circuit diagram of a phase-locked loop and shaping amplifier module provided in an embodiment of this application. In some embodiments of this application, the input terminal of the phase-locked loop 300 is electrically connected to the tap 200 through the shaping amplifier module 600.

[0043] The shaping and amplification module 600 includes a first shaper 610 and a first amplifier 620. Tap 200 is electrically connected to the inverting input terminal of the first shaper 610. The output terminal of the first shaper 610 is electrically connected to the inverting input terminal of the first amplifier 620. The output terminal of the first amplifier 620 is electrically connected to the input terminal of the phase-locked loop 300. The non-inverting input terminals of the first shaper 610 and the first amplifier 620 are both connected to a bias voltage.

[0044] Among them, refer to again Figure 2 and reference Figure 3 , Figure 3 This is an optional circuit schematic diagram of the transformer and transformer drive module provided in the embodiments of this application. Tap 200 corresponds to port T1-TAP, and the bias voltage is VDD5V6.

[0045] Tap 200 is used to sample the load feedback signal generated when the load 410 is running.

[0046] Among them, reference Figure 2 The first shaper 610 is an amplifier with negative feedback. It amplifies and rectifies the load feedback signal. Current-limiting resistors R31 and R34 are electrically connected. R34 connects one end of R31 to tap 200, and the other end is grounded. The circuit consisting of current-limiting resistors R31 and R34, filter capacitor C30, voltage-limiting diode D14, and voltage-limiting diode D13 is used to limit the voltage of the load feedback signal. One end of filter capacitor C30 is grounded, and the other end is connected to the inverting input of the first shaper 610 via resistor R30 and filter capacitor C28. One end of filter capacitor C27 is connected to the output of the first shaper 610, and the other end is connected to one end of resistor R30 connected to filter capacitor C28. The output of the first shaper 610... The first shaper 610 is electrically connected to the inverting input terminal via resistor R28. The output terminal of the first shaper 610 is electrically connected to the inverting input terminal of the first amplifier 620 via resistor R27. The output terminal of the first amplifier 620 is electrically connected to the inverting input terminal of the first amplifier 620 via resistor R26. Filter capacitors C30, C28, and C27 are used for bandpass filtering of the load feedback signal. Resistors R28 and R30 are used to determine the amplification factor of the first shaper 610, and resistors R26 and R27 are used to determine the amplification factor of the first amplifier 620. One end of filter capacitor C28 connected to resistor R30 is grounded through amplitude modulation resistor R29 and sliding rheostat RV2. Amplitude modulation resistor R29 and sliding rheostat RV2 are used to adjust the phase and amplitude of the feedback signal. The bias voltage is used to raise the reference voltage of the operational amplifier, converting the feedback alternating signal into a DC signal.

[0047] Based on this, the first shaper 610 can shift the phase of the load feedback signal by 180 degrees, and the second amplifier can shift the load feedback signal by another 180 degrees in the same direction. At the same time, the load feedback signal is shaped and filtered, and the load feedback signal is finally converted into a clearer signal, which is beneficial to improving the performance of the phase-locked loop.

[0048] Additionally, refer to again Figure 3 and reference Figure 4 and Figure 5 , Figure 4 This is an optional circuit schematic diagram of the power regulation circuit provided in an embodiment of this application. Figure 5 This is an optional circuit diagram of a voltage regulation module provided in an embodiment of this application. In some embodiments of this application, the voltage regulation module 500 is provided with a voltage input terminal 510 and a voltage output terminal 520. The voltage input terminal 510 is electrically connected to the power supply voltage 530, and the voltage output terminal 520 is electrically connected to the primary winding 110 of the transformer 100.

[0049] Specifically, when the voltage regulation module 500 is in the first working state, the voltage at the voltage output terminal 520 increases, and when the voltage regulation module 500 is in the second working state, the voltage at the voltage output terminal 520 decreases.

[0050] The voltage regulation module 500 also has a third working state. When the voltage regulation module 500 is in the third working state, the voltage at the voltage output terminal 520 remains unchanged.

[0051] It should be noted that the signal at the control terminal of the input voltage regulation module 500 is a PWM pulse signal. When the duty cycle of the PWM pulse signal decreases, the voltage regulation module 500 is in the first working state; when the duty cycle of the PWM pulse signal increases, the voltage regulation module 500 is in the second working state; and when the duty cycle of the PWM pulse signal remains unchanged, the voltage regulation module 500 is in the third working state.

[0052] It is understandable that the greater the proportion of time the voltage regulation module 500 is in the first working state per unit time, the greater the current in the primary winding 110; the greater the proportion of time the voltage regulation module 500 is in the second working state per unit time, the smaller the current in the primary winding 110.

[0053] It should be noted that this is a reference again. Figure 5The voltage regulation module 500 includes a control transistor Q102, a P-channel MOSFET Q3 (P-channel Metal-Oxide-Semiconductor Field-Effect Transistor), and an inductor L1, for example, referring again to Figure 5 The drain of the P-channel MOSFET Q3 is electrically connected to one end of the inductor L1, and the other end of the inductor L1 corresponds to port USP. The primary winding 110 is electrically connected to the inductor L1 through port USP. The voltage input terminal 510 of the voltage regulation module 500 corresponds to the source of the P-channel MOSFET Q3, and the voltage output terminal 520 of the voltage regulation module 500 corresponds to port USP of the inductor L1. The control terminal of the voltage regulation module 500 corresponds to port IC5_OUT. One end of the resistor R104 is port IC5_OUT, and the other end of the resistor R104 is electrically connected to the base of the control transistor Q102. The collector of the control transistor Q102 is grounded through resistor R105, and the emitter of the control transistor Q102 is electrically connected to the supply voltage 530 through resistor R6. The emitter of the control transistor Q102 is also electrically connected to the gate of the P-channel MOSFET Q3.

[0054] Specifically, when the output of the first comparator 400 is low, the control transistor Q102 is in a saturated conducting state, which pulls down the gate level of the P-channel MOSFET Q3 to a low level. The source and drain of the P-channel MOSFET Q3 are conducting, that is, the P-channel MOSFET Q3 is in a conducting state, and the inductor L1 is in a charging state. When the output of the first comparator 400 is high, the control transistor Q102 is in a cutoff state, which pulls up the emitter level of the control transistor Q102 to a high level. This is equivalent to pulling up the gate level of the P-channel MOSFET Q3 to a high level. The source and drain of the P-channel MOSFET Q3 are not conducting, that is, the P-channel MOSFET Q3 is in a cutoff state, and the inductor L1 is in a discharging state.

[0055] Therefore, when the duty cycle of the PWM pulse signal at the output of the first comparator 400 decreases, the charging time of inductor L1 increases per unit time, and the voltage at the voltage output terminal 520 increases, which is equivalent to the control module being in the first working state. When the duty cycle of the PWM pulse signal at the output of the first comparator 400 increases, the charging time of inductor L1 decreases per unit time, and the voltage at the voltage output terminal 520 decreases, and the voltage control module is in the second working state.

[0056] Based on this, by controlling the voltage control module to be in the first or second working state, the voltage applied to the primary side of the transformer 100 by the voltage regulation module 500 can be increased or decreased. This allows the power change of the primary side of the transformer 100 to be determined within a unit time based on the current working state of the voltage control module. This improves the precision of controlling the power of the primary side of the transformer 100, thereby improving the precision of controlling the power of the overall circuit, enhancing the ability to cope with power fluctuations caused by changes in the resonant point, and improving the stability of the overall circuit power.

[0057] Additionally, refer to again Figure 3 and Figure 4 In some embodiments of this application, the inverting input of the first comparator 400 is electrically connected to the tap 200 via a negative charge pump 540.

[0058] It should be noted that the negative voltage charge pump 540 includes a diode D16, a resistor R32, and a capacitor C29. The resistor R32 is grounded through the capacitor C29. The positive terminal of the diode D16 is electrically connected to the end of the resistor R32 away from the capacitor C29. The negative terminal of the diode D16 is the input terminal of the negative voltage charge pump 540. The port extending from the connection point of the resistor R32 and the capacitor C29 serves as the output terminal of the negative voltage charge pump 540.

[0059] Understandably, when the reference signal of the first comparator 400 is a sawtooth wave signal, the signal amplitude at the inverting input of the first comparator 400 is compared with the amplitude of the sawtooth wave signal to determine the width of the PWM pulse signal output by the first comparator 400. Specifically, when the signal amplitude at tap 200 increases, the voltage at the inverting input of the first comparator 400 decreases through the negative voltage charge pump 540, the high-level duty cycle of the PWM pulse signal increases, the proportion of time that the voltage regulation module 500 is in the first working state per unit time decreases, and the voltage at the voltage output terminal 520 increases. The reduced high-frequency period leads to a decrease in the current of the primary winding 110, which in turn reduces the power of the load 410. When the signal amplitude on tap 200 decreases, the negative voltage charge pump 540 increases the voltage at the inverting input of the first comparator 400, increases the low-level duty cycle of the PWM pulse signal, increases the proportion of time that the voltage regulation module 500 is in the first working state per unit time, and increases the voltage rise time of the voltage output terminal 520, which in turn increases the current of the primary winding 110, thus increasing the power of the load 410.

[0060] Based on this, the inverting input terminal of the first comparator 400 is electrically connected to the tap 200 through the negative pressure charge pump 540. Therefore, the power change direction of the load feedback signal of the tap 200 is opposite to the power change direction of the signal at the inverting input terminal of the first comparator 400. When the power of the load 410 deviates, the power can be automatically corrected, thereby improving the stability of the circuit.

[0061] Additionally, refer to again Figure 4 In some embodiments of this application, the inverting input terminal of the first comparator 400 is electrically connected to the negative pressure charge pump 540 through the second amplifier 700, and the inverting input terminal of the first comparator 400 is also electrically connected to the signal control port 420 through the second amplifier 700.

[0062] The output terminal of the second amplifier 700 is electrically connected to the inverting input terminal of the first comparator 400, the non-inverting input terminal of the second amplifier 700 is electrically connected to the negative pressure charge pump 540, the non-inverting input terminal of the second amplifier 700 is also electrically connected to the signal control port 420, and the inverting input terminal of the second amplifier 700 is also electrically connected to the output terminal of the second amplifier 700.

[0063] Specifically, the signal control port 420 is electrically connected to the non-inverting input of the second amplifier 700 through a filter composed of a filter resistor R43 and a filter capacitor C18. The tap 200 is grounded through a negative voltage charge pump 540 and a filter resistor R33. One end of the negative voltage charge pump 540 connected to the filter resistor R33 is electrically connected to the non-inverting input of the second amplifier 700.

[0064] The output terminal of the second amplifier 700 is electrically connected to the inverting input terminal of the second amplifier 700 through a parallel circuit consisting of a phase compensation capacitor C17 and a feedback resistor R48. The output terminal of the second amplifier 700 is also electrically connected to the inverting input terminal of the first comparator 400 through a diode D6.

[0065] Based on this, the power control signal of the signal control port 420 is superimposed on the load feedback signal of the tap 200 and then input to the non-inverting input of the second amplifier 700. The output of the second amplifier 700 is then electrically connected to the inverting input of the first comparator 400, which can improve the sensitivity of the first comparator 400 to the power changes of the load 410, thereby making the automatic power correction more efficient.

[0066] Additionally, refer to again Figure 3 In some embodiments of this application, the output terminal of the phase-locked loop 300 is electrically connected to the primary winding 110 via the transformer drive module 800.

[0067] The transformer drive module 800 includes a gate driver 810, a forward output circuit 820, and a reverse output circuit 830. The control terminal of the gate driver 810 is electrically connected to the output terminal of the phase-locked loop 300. The forward output terminal of the gate driver 810 is electrically connected to one end of the primary winding 110 through the forward output circuit 820, and the reverse output terminal of the gate driver 810 is electrically connected to the other end of the primary winding 110 through the reverse output circuit 830. The gate driver 810 is used to control the working states of the forward output circuit 820 and the reverse output circuit 830 to be opposite.

[0068] It should be noted that when the control terminal of the gate driver 810 is high, the positive output terminal is high and the negative output terminal is low; when the control terminal of the gate driver 810 is low, the positive output terminal is low and the negative output terminal is high.

[0069] Among them, the output terminal of the phase-locked loop 300 corresponds to the port PLL_OUT, the gate driver 810 corresponds to the chip U17, the positive output terminal corresponds to the port HO of U17, and the negative output terminal corresponds to the port LO of U17.

[0070] Specifically, when the positive output terminal is high and the negative output terminal is low, the positive output circuit 820 is in a conducting state and the negative output circuit 830 is in a non-conducting state. The positive output circuit 820 generates current, while the negative output circuit 830 does not generate current. When the positive output terminal is low and the negative output terminal is high, the positive output circuit 820 is in a non-conducting state and the negative output circuit 830 is in a conducting state. The positive output circuit 820 does not generate current, while the negative output circuit 830 generates current. Therefore, when the level of the control terminal of the gate driver 810 changes alternately, current is alternately generated between the positive output circuit 820 and the negative output circuit 830, causing the primary side of the transformer 100 to generate AC current corresponding to the output signal of the phase-locked loop 300, which in turn causes the secondary winding 120 of the transformer 100 to generate a corresponding AC signal.

[0071] It should be noted that the transformer 100 itself has a certain filtering effect, which can reduce the high-order harmonics in the output signal of the phase-locked loop 300 and make the signal waveform on the tap 200 closer to a sine wave.

[0072] Based on this, the output terminal of the phase-locked loop 300 is electrically connected to the primary winding 110 through the transformer drive module 800. The gate driver 810 in the transformer drive module 800 converts the output signal of the phase-locked loop 300 into two higher-level complementary gate drive signals. These signals, together with the in-phase output circuit 820 and the reverse output circuit 830, alternately generate current, so that the primary winding 110 generates an alternating current without dead time. Correspondingly, the alternating current generated by the secondary winding 120 also has no dead time, thereby improving the effective power of the load 410.

[0073] Additionally, refer to again Figure 3 In some embodiments of this application, the forward output circuit 820 includes a forward conducting element 821, and the reverse output circuit 830 includes a reverse conducting element 831. The forward output terminal is electrically connected to the control terminal of the forward conducting element 821, the first conducting terminal of the forward conducting element 821 is electrically connected to one end of the primary winding 110, the reverse output terminal is electrically connected to the control terminal of the reverse conducting element 831, the first conducting terminal of the reverse conducting element 831 is electrically connected to the other end of the primary winding 110, and the second conducting terminal of the forward conducting element 821 is electrically connected to the second conducting terminal of the reverse conducting element 831.

[0074] Both the forward-conducting element 821 and the reverse-conducting element 831 can be either N-channel MOSFETs or P-channel MOSFETs. The forward-conducting element 821 and the reverse-conducting element 831 have the same model number. For example, when both the forward-conducting element 821 and the reverse-conducting element 831 are N-channel MOSFETs, the first conducting terminal of the forward-conducting element 821 corresponds to the drain of the N-channel MOSFET, the second conducting terminal of the forward-conducting element 821 corresponds to the source of the N-channel MOSFET, and the control terminal of the forward-conducting element 821 corresponds to the gate of the N-channel MOSFET. The forward output terminal is connected to a resistor via a rectifier diode D5. The parallel circuit composed of R8 is electrically connected to the control terminal of the forward conducting element 821. The first conducting terminal of the forward conducting element 821 is electrically connected to one end of the primary winding 110. The first conducting terminal of the forward conducting element 821 is grounded through capacitor C5. Similarly, the first conducting terminal of the reverse conducting element 831 corresponds to the drain of the N-channel MOSFET, the second conducting terminal of the reverse conducting element 831 corresponds to the source of the N-channel MOSFET, and the control terminal of the reverse conducting element 831 corresponds to the gate of the N-channel MOSFET. The connection method of the reverse output circuit 830 is the same as that of the forward output circuit 820. The embodiments disclosed herein will not be described in detail here.

[0075] Among them, resistor R8 and resistor R7 of the reverse output circuit 830 are both used to suppress grid oscillation, and capacitor C5 is used to provide a discharge path for the spike voltage generated after the primary winding of the transformer is cut off.

[0076] The connection point between the second conducting terminal of the forward conducting element 821 and the second conducting terminal of the reverse conducting element 831 is Q1-3. Both the second conducting terminal of the forward conducting element 821 and the second conducting terminal of the reverse conducting element 831 are grounded to resistor R1 through the connection point Q1-3.

[0077] Based on this, the positive output terminal can control the working state of the positive conduction circuit through the positive conduction element 821, and the negative output terminal can control the working state of the negative conduction circuit through the negative conduction element 831. The alternating change of the level of the positive output terminal and the level of the negative output terminal can realize the alternating generation of current between the positive output circuit 820 and the negative output circuit 830. Since the structure of the positive conduction element 821 and the negative conduction element 831 is simple, the response speed of the circuit can be improved, so that the alternating current on the primary side of the transformer 100 can more accurately track the output signal of the phase-locked loop 300.

[0078] Additionally, refer to again Figure 3 and Figure 4 In some embodiments of this application, a power protection module 900 is also included. The input terminal of the power protection module 900 is electrically connected to the second conducting terminal of the forward conducting element 821, and the input terminal of the power protection module 900 is also electrically connected to the second conducting terminal of the reverse conducting element 831. The output terminal of the power protection module 900 is electrically connected to the inverting input terminal of the first comparator 400.

[0079] The power protection module 900 includes a conducting transistor Q4, a current-limiting resistor R12, a sampling resistor R1, a current-limiting resistor R14, and a filter capacitor C15. For example, refer again... Figure 4 The base of the conducting transistor Q4 is electrically connected to one end of the current-limiting resistor R12. The other end of the current-limiting resistor R12 is the input terminal Q1-3 of the power protection module 900. Q1-3 is the non-grounded end of the sampling resistor R1. The sampling resistor R1 is used to sample the current of the power protection module. The emitter of the conducting transistor Q4 is grounded. The collector of the conducting transistor Q4 is electrically connected to one end of the current-limiting resistor R14. The other end of the current-limiting resistor R14 is grounded through the filter capacitor C15. The other end of the current-limiting resistor R14 is the output terminal of the power protection module 900, that is, the other end of the current-limiting resistor R14 is electrically connected to the inverting input terminal of the first comparator 400.

[0080] It should be noted that when the power of the transformer drive module 800 is greater than the pre-designed safe power, that is, when the voltage at the input terminal of the power protection module 900 is greater than the pre-designed safe voltage, the conducting transistor Q4 is in a saturated state, the emitter and collector of the conducting transistor Q4 are connected, and the level at the inverting input terminal of the first comparator 400 is pulled low.

[0081] Based on this, when the circuit power of the power protection module 900 is too high, the output of the first comparator 400 can continuously output a high level, thereby keeping the voltage regulation module 500 in the second working state, so that the current in the circuit continues to decrease, thus preventing the circuit from being burned out.

[0082] Additionally, refer to again Figure 2 and Figure 4 In some embodiments of this application, the phase-locked loop 300 is electrically connected to the non-inverting input of the first comparator 400 via a second shaper 910.

[0083] The second shaper 910 is composed of a resistor R15 and a capacitor C16. One end of the resistor R15 is electrically connected to the output of the phase-locked loop 300 as the input of the second shaper 910. The other end of the resistor R15 is grounded through the capacitor C16. The other end of the resistor R15 is also electrically connected to the non-inverting input of the first comparator 400 as the output of the second shaper 910.

[0084] It should be noted that the second shaper 910 is used to enable the output signal of the phase-locked loop 300 to be compared with the signal at the inverting input of the first comparator 400. For example, when the output signal of the phase-locked loop 300 is a square wave, the square wave signal output by the phase-locked loop 300 is converted into a sawtooth wave signal. When the signal amplitude at the inverting input of the first comparator 400 decreases, the high-level duty cycle of the comparator's output signal increases; when the signal amplitude at the inverting input of the first comparator 400 increases, the low-level duty cycle of the comparator's output signal increases.

[0085] Based on this, the second shaper 910 converts the square wave signal output by the phase-locked loop 300 into a sawtooth wave signal, and then inputs it to the non-inverting input of the first comparator 400. The signal at the inverting input of the first comparator 400 is a superposition of the power control signal and the load feedback signal, so that the first comparator 400 can output signals with different duty cycles according to the change of the superposition signal at the inverting input to control the current of the primary winding 110, thereby stabilizing the power of the load 410 and improving the stability of the circuit power.

[0086] Additionally, refer to again Figure 2 In some embodiments of this application, the phase-locked loop 300 includes a phase detector 310, a loop filter 320, and a voltage-controlled oscillator 330. The output terminal of the phase detector 310 is connected to the control terminal of the voltage-controlled oscillator 330 through the loop filter 320. The output terminal of the voltage-controlled oscillator 330 is electrically connected to the first input terminal of the phase detector 310. The second input terminal of the phase detector 310 is the input terminal of the phase-locked loop 300, and the output terminal of the voltage-controlled oscillator 330 is the output terminal of the phase-locked loop 300.

[0087] The loop filter 320 consists of a filter resistor R20 and a filter capacitor C31. One end of the filter resistor R20 is the input terminal of the loop filter 320, and the other end of the filter resistor R20 is grounded through the filter capacitor C31. The other end of the filter resistor R20 is the output terminal of the loop filter 320.

[0088] It should be noted that the circuit's tracking process for the resonant point is as follows: When the phase of the signal output by the voltage-controlled oscillator 330 leads the phase of the load feedback signal from tap 200, the phase detector 310 outputs a negative pulse, which is applied to the voltage-controlled oscillator 330 through the loop filter 320, causing the voltage-controlled oscillator 330 to decrease its output frequency; when the phase of the signal output by the voltage-controlled oscillator 330 lags behind the phase of the signal from tap 200, the phase detector 310 outputs a positive pulse, which is applied to the voltage-controlled oscillator 330 through the loop filter 320, causing the voltage-controlled oscillator 330 to increase its output frequency. The greater the phase difference between the load feedback signal and the signal output by the voltage-controlled oscillator 330, the larger the duty cycle of the pulse signal output by the phase detector 330, and the more significant the adjustment effect on the voltage-controlled oscillator 330, thus rapidly approaching and locking the resonant frequency of the load 410.

[0089] Based on this, the pulse output by the phase detector 310 is input to the control terminal of the voltage-controlled oscillator 330 after passing through the loop filter 320. This allows the voltage-controlled oscillator 330 to control the frequency or phase of the output signal, thereby tracking the resonant point, correcting power fluctuations, and enabling the load 410 to continuously operate in the optimal state, thus improving the effective power of the load 410.

[0090] The embodiments of this application have been described in detail above with reference to the accompanying drawings. However, this application is not limited to the above embodiments. Within the scope of knowledge possessed by those skilled in the art, various changes can be made without departing from the spirit of this application.

Claims

1. A power stabilizing circuit, characterized by comprising: The utility model relates to a voltage regulation module and a transformer, and belongs to the technical field of power supply. The utility model relates to a voltage regulation module and a transformer, and belongs to the technical field of power supply. The utility model relates to a voltage regulation module and a transformer, and belongs to the technical field of power supply. The utility model relates to a voltage regulation module and a transformer, and belongs to the technical field of power supply.

2. A power stabilizing circuit according to claim 1, wherein The utility model relates to a voltage regulation module and a transformer, and belongs to the technical field of power supply.

3. A power stabilizing circuit according to claim 1, wherein The utility model relates to a voltage regulation module and a transformer, and belongs to the technical field of power supply.

4. A power stabilizing circuit according to claim 3, wherein The utility model relates to a voltage regulation module and a transformer, and belongs to the technical field of power supply.

5. A power stabilizing circuit according to claim 4, wherein The utility model relates to a voltage regulation module and a transformer, and belongs to the technical field of power supply. The utility model relates to a voltage regulation module and a transformer, and belongs to the technical field of power supply.

6. A power stabilizing circuit according to claim 1, wherein The output end of the phase-locked loop is electrically connected with the primary side winding through a voltage transformation driving module, wherein the voltage transformation driving module comprises a gate driver, a forward output loop and a reverse output loop, the control end of the gate driver is electrically connected with the output end of the phase-locked loop, the forward output end of the gate driver is electrically connected with one end of the primary side winding through the forward output loop, the reverse output end of the gate driver is electrically connected with the other end of the primary side winding through the reverse output loop, and the gate driver is used for controlling the working states of the forward output loop and the reverse output loop to be opposite.

7. A power stabilizing circuit according to claim 6, wherein The forward output loop comprises a forward conducting element, the reverse output loop comprises a reverse conducting element, the forward output end is electrically connected with the control end of the forward conducting element, the first conducting end of the forward conducting element is electrically connected with one end of the primary side winding, the reverse output end is electrically connected with the control end of the reverse conducting element, the first conducting end of the reverse conducting element is electrically connected with the other end of the primary side winding, and the second conducting end of the forward conducting element is electrically connected with the second conducting end of the reverse conducting element.

8. A power stabilizing circuit according to claim 7, wherein Further comprising a power protection module, the input end of the power protection module is electrically connected with the second conducting end of the forward conducting element, the input end of the power protection module is also electrically connected with the second conducting end of the reverse conducting element, and the output end of the power protection module is electrically connected with the inverting input end of the first comparator.

9. A power stabilizing circuit according to claim 1, wherein The phase-locked loop is electrically connected with the non-inverting input end of the first comparator through a second shaper.

10. The power stabilizing circuit according to claim 1, wherein The phase-locked loop comprises a phase detector, a loop filter and a voltage controlled oscillator, the output end of the phase detector is electrically connected with the control end of the voltage controlled oscillator through the loop filter, the output end of the voltage controlled oscillator is electrically connected with the first input end of the phase detector, the second input end of the phase detector is the input end of the phase-locked loop, and the output end of the voltage controlled oscillator is the output end of the phase-locked loop.

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