Selectively switchable wideband RF summer

Abstract

The RF summing circuit (20) comprises first and second ports (P1, P2) coupled to a junction (22) by first and second resistors (R1, R2), respectively. The RF summing circuit further comprises a series combination of a third resistor (R3) and a switch (S3), and an amplifier (UI), the series combination coupled across the amplifier between the junction (22) and the third port (P3). Furthermore, when the switch (S3) is moved to a closed position and the amplifier (UI) is switched off, a passive mode of operation is implemented, and when the switch is moved to an open position and the amplifier (UI) is switched on, an active mode of operation is implemented. The RF summing circuit generates a summed signal at the third port (P3) equal to the sum of the signals at the first and second ports (P1, P2).

Description

[Technical Field]

[0001] The present subject matter relates to radio frequency (RF) devices, and more particularly to selectively switchable RF summers. [Background technology]

[0002] Sometimes, it is necessary to control gain in RF circuits. For example, an H-tree network may be used as an antenna feed for a phased-array RF device or an RF transversal filter. Signals in an H-tree network can sum coherently, producing a large signal at the antenna output port, which can lead to nonlinear distortion in the device (e.g., input amplifier) ​​coupled to the output port, or they can sum incoherently, resulting in a reduced gain but a reduced signal-to-noise ratio (SNR) at another output port. Circuit designers can provide one or more signals generated at a corresponding number of H-tree network output ports to downstream devices. Such ports often require selective balancing of noise and linearity performance, but gain control without sacrificing matching and bandwidth is difficult to achieve.

[0003] Conventional approaches to solving the aforementioned problems may include a resistor combiner with switched resistors or a general variable gain amplifier topology. However, these conventional approaches can only achieve relatively low dynamic range improvement in the H-tree adder. Summary of the Invention [Means for solving the problem]

[0004] According to one aspect, a radio frequency (RF) summing circuit having an impedance characteristic Z0 includes first and second ports coupled to a junction by respective first and second resistors. The circuit further includes a series combination of a third resistor, a switch movable between an open position and a closed position, and an amplifier having an input terminal and an output terminal and operable in an off state and an on state, the series combination coupled across the input terminal and the output terminal of the amplifier between the junction and the third port. The first resistor, the second resistor, and the third resistor are all substantially equal to Z0 / 3. Furthermore, when the switch is moved to the closed position and the amplifier is switched to an off state, a passive mode of operation is implemented, and when the switch is moved to the open position and the amplifier is switched to an on state, an active mode of operation is implemented. The RF summing circuit generates a summed signal at the third port equal to the sum of the signals at the first and second ports modified by one of the first and second gain values.

[0005] Other aspects and advantages will become apparent by consideration of the following detailed description and the accompanying drawings, in which like numbers refer to like structure throughout. [Brief explanation of the drawings]

[0006] [Figure 1] FIG. 1 is a simplified circuit diagram of one embodiment of a selectively switchable RF summer. [Figure 2] FIG. 2 is a simplified circuit diagram of an embodiment of the selectively switchable RF summer of FIG. 1 in a passive operating state. [Figure 3] FIG. 2 is a simplified circuit diagram of an embodiment of the selectively switchable RF summer of FIG. 1 in an active operating state. [Figure 4] 2A-2C are schematic diagrams of two implementations of the amplifier of FIG. 1; [Figure 5] 2A-2C are schematic diagrams of two implementations of the amplifier of FIG. 1; [Figure 6] 2A-2C are simplified schematic diagrams of the embodiment of FIG. 1 in passive and active modes of operation, showing the parasitic impedances of the amplifier. [Figure 7]7 is a graph showing S-parameters as a function of frequency for the passive operating mode of FIG. 6; [Figure 8] 7 is a graph showing S-parameters as a function of frequency for the passive operating mode of FIG. 6; [Figure 9] 2A-2C are simplified schematic diagrams of the embodiment of FIG. 1 in passive and active modes of operation, showing the parasitic impedances of the amplifier. [Figure 10] 10 is a graph showing S-parameters as a function of frequency for the active mode of operation of FIG. 9; [Figure 11] 10 is a graph showing S-parameters as a function of frequency for the active mode of operation of FIG. 9; DETAILED DESCRIPTION OF THE INVENTION

[0007] Referring initially to FIG. 1, selectively switchable wideband RF summing circuit 20 comprises a multiport device having first, second, and third ports P1, P2, and P3, respectively. First and second ports P1 and P2 are coupled to junction 22 by resistors R1 and R2, respectively. Buffer amplifier U1 includes an input terminal coupled to junction 22 and an output terminal coupled to third port P3. Amplifier U1 includes power terminals coupled to supply voltage V+ and ground by first and second switches S1 and S2, respectively. A series combination of a third switch S3 and a third resistor R3 crosses amplifier U1 between junction 22 and third port P3.

[0008] Each of the first, second, and third switches S1, S2, and S3 is selectively operable between an open position and a closed position and may comprise a manually and / or mechanically operable device, an electronically operable device (e.g., a transistor), or any other suitable device. The first, second, and third resistors have resistances corresponding to the characteristic impedance Z of the summing circuit 20. Specifically, in a preferred embodiment, the resistances of resistors R1, R2, and R3 are the same and each equal to Z / 3. Thus, in a specific embodiment where Z equals 50 ohms, the resistances of R1, R2, and R3 are all equal to 50 / 3 (i.e., approximately 16.67) ohms.

[0009] FIG. 2 shows summing circuit 20 operable in a passive mode of operation. Such a mode of operation is implemented by opening one or both of first and second switches S1 and S2 and closing third switch S3. First and second input signals, supplied to first and second ports P1 and P2, respectively, are summed at junction 22, and the summed signal is supplied to third port P3 via third switch S3 and resistor R3. At this time, amplifier U1 is OFF, so amplifier U1 presents very high impedance (e.g., more than three times the impedance Z0) at its input and output terminals. Circuit 20 is impedance-matched at all three ports P1, P2, and P3 and exhibits a signal transmission gain of approximately -6 dB between all three ports P1, P2, and P3. Furthermore, because the components in the transmission path are substantially purely resistive, the signal is substantially linear over a very wide frequency range (e.g., 0-40 GHz), particularly when switch S3 in passive mode is manually or mechanically operable (thus eliminating the parasitic impedance of the transistor). S-parameters for circuit 20 operating in passive mode are shown in FIGS. 7 and 8. FIG. 6 illustrates circuit 20 of FIG. 2 with the parasitic impedance of buffer amplifier U1 represented by capacitor C1 and resistor R4. The S-parameters in FIGS. 7 and 8 are shown for an example where the impedance characteristic Z0 is 50 ohms, the capacitance of parasitic capacitor C1 is 20 femtofarads, and the parasitic resistance is 500 ohms. Of course, as will be apparent to those skilled in the art, the nature and value of the parasitic impedance will vary with the selection of components, particularly buffer amplifier U1, and the scope of the claims appended hereto is not limited to the nature and value of the parasitic impedance or the component values ​​disclosed herein.

[0010] As can be seen in Figure 7, the input port voltage reflection coefficient S 11 and S 22 and the output port voltage reflection coefficient S 33 rises at frequencies between 0 and 40 GHz due to parasitic impedances. As can be seen in Figure 8, the forward voltage gain S 31 , and parameter S 21and S 12 remains constant at about -6db as before.

[0011] Referring now to FIG. 3, the active mode of operation is initiated by closing switches S1 and S2 and opening switch S3. This energizes (turns on) amplifier U1 and removes resistor R3 from the circuit. As in the passive mode of operation, first and second input signals provided at first and second ports P1 and P2, respectively, are summed at junction 22. In the active mode of operation, the summed signal is amplified by amplifier U1 and provided to third port P3, with output impedance matching provided by amplifier U1. FIG. 9 shows exemplary parasitic impedances of amplifier U1, including capacitor C1 and resistor R4, which may have values ​​the same as or different from the parasitic impedances shown in FIG. 6. Ports P1 and P2 remain partially matched to Z0 because each input signal at ports P1 and P2 sees the impedance of the opposite port.

[0012] 10 and 11 show the S-parameters during operation of the circuit 20 in the active mode. The input port voltage reflection coefficient S 11 and S 22 remains at approximately equal levels across the 0-40 GHz bandwidth, and the input port voltage reflection coefficient S 11 and S 22 The output port voltage reflection coefficient is similar, albeit at a reduced level compared to the S-parameter S 31 (Although not shown in Figure 11, the parameter S 32 is the parameter S 31 The S-parameter S remains essentially constant at approximately 8 dB over the bandwidth (which is identical to 21 and S 12 remains constant at about -3db over the bandwidth.

[0013] 4 and 5 show a particular implementation of amplifier U1 and associated switches S1 and S2, it being understood that other implementations may be used instead. The exemplary embodiment of Figure 4 includes P-channel and N-channel MOSFETs Q1 and Q2 having source and drain terminals connected in series between switches S1 and S2 and interconnected gate terminals. Resistor R5 is connected between the amplifier input terminal at the interconnected gate terminals and the output terminal at the junction between the drains of transistors Q1 and Q2 to provide bias for proper operation.

[0014] The exemplary embodiment of FIG. 5 includes an N-channel MOSFET Q3 and a resistor R7 coupled to the drain terminal of transistor Q3 at the amplifier output terminal. The series combination of transistor Q3 and resistor R7 is coupled to switch S1. The source terminal of transistor Q3 is optionally coupled to ground by switch S2. Switch S2 serves as a redundant method of turning off amplifier U1. The small parasitic series resistance that switch S2 exhibits when closed may be desirable to control the gain and linearity of the amplifier. If switch S2 is omitted, the source terminal of transistor Q3 is coupled directly to ground, thereby eliminating the small parasitic impedance. The gate terminal of transistor Q3 is coupled to the junction between the series-connected combination of capacitor C2 and resistor R6. The series combination of capacitor C2 and resistor R6 provides a voltage differential between the amplifier input and voltage V bias Capacitor C2 and resistor R6 provide an appropriate fixed DC gate voltage for biasing transistor Q3. [Industrial Applicability]

[0015] The embodiments disclosed herein can be used as a wideband gain control function in H-tree RF signal summing networks. Specific applications include antenna feeds for phased arrays and RF transversal filters. Signals in an H-tree network coherently sum, generating large signals at the summed output ports, which can result in amplifier nonlinear distortion at the summed output, or are not summed, causing a reduction in the signal-to-noise ratio (SNR) at the output. The use of the switchable active-passive two-way RF signal summers disclosed herein at each H-tree or other antenna feed output allows circuit designers to select a passive mode of operation, in which signals are coherently summed at the ports, or an active mode, in which signals are incoherently summed at the ports. Thus, each signal level can be individually controlled at different summing layers to balance noise and linear performance.

[0016] All references, including publications, patent applications, and patents, cited in this specification are herein incorporated by reference to the same extent as if each reference was individually and specifically indicated to be incorporated by reference and set forth in its entirety herein.

[0017] The use of the terms "a," "an," and "The," as well as like reference numerals in the context of describing the present invention (particularly in the context of the claims that follow), should be construed to encompass both the singular and the plural unless otherwise indicated herein or clearly contradicted by context. The recitation of numerical ranges herein is merely intended to serve as a shorthand method for referring individually to each value falling within the range, unless otherwise indicated herein, and each value is incorporated into the specification as if it were individually recited herein. All methods described herein can be performed in any suitable order unless otherwise indicated herein or clearly contradicted by context. The use of any and all examples, or exemplary language (e.g., "etc.") provided herein is intended merely to further clarify the disclosure and does not limit the scope of the disclosure unless specifically claimed. No language in the specification should be construed as indicating any non-claimed element as essential to the practice of the disclosure.

[0018] Numerous modifications to the present disclosure will be apparent to those skilled in the art in light of the foregoing description. It should be understood that the illustrated embodiments are illustrative only and should not be construed as limiting the scope of the present disclosure.

Claims

1. Impedance characteristic Z ０ 1. A radio frequency (RF) summing circuit having: a first port and a second port coupled to the junction by a first resistor and a second resistor, respectively; a series combination connected between the junction and a third port, the series combination including a third resistor and a switch movable between an open position and a closed position; an amplifier having an input terminal and an output terminal, operable in an off state and an on state, the amplifier being disposed in parallel with the series combination between the junction and the third port, the input terminal being connected to the junction and the output terminal being connected to the third port; Equipped with The first resistor, the second resistor, and the third resistor are all substantially Z ０ / 3, a passive mode of operation is implemented when the switch is moved to a closed position and the amplifier is switched off; an active mode of operation is implemented when the switch is moved to an open position and the amplifier is switched on; the RF summing circuit generates a summed signal at a third port equal to the sum of the signals at the first port and the second port modified by one of a first gain value and a second gain value. RF summing circuit.

2. 2. The RF summing circuit of claim 1, wherein the summing circuit is impedance matched at all ports and has substantially equal gain between all ports when the passive mode of operation is implemented.

3. 2. The RF summing circuit of claim 1, wherein when the passive mode of operation is implemented, the magnitude of the signal sum is modified by the first gain value.

4. 2. The RF summing circuit of claim 1, wherein when the active mode of operation is implemented, the magnitude of the sum of the signals is modified by the second gain value.

5. the first gain value comprises a negative value; When the passive mode of operation is implemented, the magnitude of the sum of the signals is modified by the first gain value; the second gain value comprises a positive value; When the active mode of operation is implemented, the magnitude of the sum of the signals is modified by the second gain value.

2. The RF summing circuit of claim 1.

6. 2. The RF summing circuit of claim 1, wherein the amplifier is connected to a power terminal coupled to a supply voltage via at least one additional switch, and is switched between the off state and the on state by the additional switch.

7. The amplifier is switched between the off state and the on state by at least one additional switch; the at least one additional switch includes two additional switches; the amplifier comprises a first MOSFET and a second MOSFET having source and drain terminals coupled between the two additional switches and gate terminals interconnected to the input terminal of the amplifier; a junction between the first MOSFET and the second MOSFET comprising the output terminal of the amplifier and a resistor coupled between the input terminal and the output terminal.

2. The RF summing circuit of claim 1.

8. The amplifier is switched between the off state and the on state by at least one additional switch; The amplifier a MOSFET having a drain terminal coupled to the output terminal of the amplifier; a first resistor coupled between the at least one additional switch and the output terminal of the amplifier; Equipped with a combination of a capacitor and a second resistor coupled between the input terminal of the amplifier and a voltage, the junction between the capacitor and the second resistor being coupled to a gate terminal of the MOSFET; 2. The RF summing circuit of claim 1.

9. 9. The RF summing circuit of claim 8, further comprising a further switch coupled between the source terminal of the MOSFET and ground potential.

Images