Model parameterization-based time drift compensation method of pulsed electric field measurement system

Abstract

The invention relates to the technical field of pulse electric field measurement, and discloses a time drift compensation method of a pulse electric field measurement system based on model parameterization. According to the method, a parameterized model is constructed in simulation software, and the parameterized model is additionally provided with two servo zeroing compensation circuits on the basis of an original measurement system, and the two servo zeroing compensation circuits are connected to the output ends of two in-phase operational amplification circuits respectively to form a negative feedback loop used for dynamically suppressing low-frequency baseline drift; acquiring electric field time domain waveform data of the output end of the third in-phase operational amplifier circuit; calculating a transfer function of a pulsed electric field measurement system in the parameterized model, converting the transfer function from a frequency domain state to a time domain state through inverse Fourier transform, and then performing deconvolution on the transfer function of the time domain state and electric field time domain waveform data to obtain real electric field intensity; according to the invention, time drift caused by operational amplifier input imbalance, power supply fluctuation and temperature change is automatically compensated in real time, and the stability and precision of system measurement are improved.

Description

Technical Field

[0001] This invention relates to the field of pulsed electric field measurement technology, specifically a time drift compensation method for a model-parameterized pulsed electric field measurement system. Background Technology

[0002] Electromagnetic safety, as a crucial component of information infrastructure and critical equipment operation assurance, is receiving increasing attention. Strong electromagnetic interference sources such as high-altitude electromagnetic pulse (HEMP), high-power microwave (HPM), ultra-wideband electromagnetic pulse (UWB), and lightning electromagnetic pulse (LEMP) frequently occur around aerospace, power systems, and high-value electronic equipment. These interference signals typically possess characteristics of high amplitude, wide spectrum, and strong transients, posing a serious threat to various electronic systems. Therefore, pulsed electric field measurement, as a core means of assessing electromagnetic environment strength, protection effectiveness, and electromagnetic compatibility performance, holds an irreplaceable and vital position in the field of electromagnetic pulse (EMP) protection and research.

[0003] Pulsed electric field signals typically exhibit aperiodic, non-stationary transient waveforms, characterized by steep rise times, extremely short durations, and dramatic amplitude variations. Their spectral coverage is broad, generally extending from tens of megahertz to several gigahertz. Frequency-selective distortion is easily generated during their propagation, radiation, and scattering, posing a significant challenge to the time and frequency domain response stability of the measurement system. Therefore, pulsed electric field measurement systems not only require high bandwidth response capabilities but also must maintain zero-drift stability for long-term operation in harsh environments.

[0004] Currently, active pulse electric field measurement systems based on the electro-optic conversion principle have become the mainstream solution. In particular, compact fiber optic remote transmission measurement systems that integrate laser modulation and photoelectric detection technologies are widely used in complex and strong electromagnetic environments due to their strong anti-interference capabilities and good insulation. However, in practical applications, these systems still suffer from significant "time drift" problems, which manifest as a slow drift of the system output baseline over time. This is especially problematic under conditions of long-term operation, low-frequency measurement, or high-repetition-rate testing, easily introducing voltage baseline offset, which can mask the true signal characteristics and even mislead the judgment of results.

[0005] The causes of time drift are complex, mainly including system-level coupling factors such as changes in laser luminous efficiency with temperature, unstable photodetector response, input bias drift in amplifier circuits, and power supply voltage fluctuations. Common suppression methods include introducing automatic power control (APC) circuits into the laser module or using laser devices with built-in thermoelectric cooling (TEC) to achieve temperature stability control of output optical power. However, the former still has feedback bandwidth limitations, while the latter is power-intensive, bulky, and costly, making it unsuitable for battery-powered portable systems. Traditional measurement system designs generally adopt a modular approach, making it difficult to trace and model the system link path that causes time drift as a whole, and also lacking quantitative compensation mechanisms for low-frequency baseline offsets. Summary of the Invention

[0006] To address the low-frequency baseline drift (time drift) problem in existing pulse electric field measurement systems caused by factors such as DC drift of operational amplifiers, power supply voltage fluctuations, and temperature changes during long-term operation, this invention provides a time drift compensation method for pulse electric field measurement systems based on model parameterization.

[0007] To achieve the above objectives, the present invention provides the following technical solution:

[0008] This invention discloses a time drift compensation method for a pulsed electric field measurement system based on model parameterization. The pulsed electric field measurement system includes an antenna, an electric field probe, and an optical receiver connected in sequence. The electric field probe amplifies and modulates the electrical signal collected by the antenna in the pulsed electric field into an optical signal. The optical receiver includes a photodetector, a transimpedance operational amplifier circuit, a third in-phase operational amplifier circuit, and a fourth in-phase operational amplifier circuit. The transimpedance operational amplifier circuit converts the photoresponse current output by the photodetector into a voltage signal. The third and fourth in-phase operational amplifier circuits are used to extract the AC and DC components of the voltage signal, respectively. The time drift compensation method includes:

[0009] S1. Construct a parameterized model in the simulation software. This parameterized model adds two servo zero-adjustment compensation circuits to the pulse electric field measurement system. The two servo zero-adjustment compensation circuits are respectively connected to the output terminals of the third and fourth in-phase operational amplifier circuits and form a negative feedback loop to dynamically suppress low-frequency baseline drift.

[0010] S2. Acquire the time-domain waveform data of the electric field at the output of the third in-phase operational amplifier circuit;

[0011] S3. Calculate the transfer function of the pulse electric field measurement system in the parameterized model, transform the transfer function from the frequency domain state to the time domain state through inverse Fourier transform, and then deconvolve the transfer function in the time domain state with the electric field time domain waveform data to obtain the true electric field intensity.

[0012] As a further improvement to the above scheme, in step S3, the expression of the transfer function is:

[0013]

[0014] In the formula, H(ω) is the transfer function; ω is the independent variable of the frequency domain function; A OL (ω) is the open-loop gain of the operational amplifier in the third in-phase operational amplifier circuit, U OP3 (ω) is the AC voltage signal output by the operational amplifier, H servo (ω) is the transfer function of the servo zero-adjustment compensation circuit connected to the third in-phase operational amplifier circuit; U oc (ω) represents the equivalent open-circuit output voltage signal of the electric field probe.

[0015] As a further improvement to the above scheme, the time drift compensation method further includes:

[0016] S4. When the state of the device in the pulse electric field measurement system changes, the parameterized model is updated in the simulation software according to the corresponding device characteristics after the change, and the updated real electric field intensity is obtained in accordance with the method of steps S2 to S3.

[0017] As a further improvement to the above scheme, the optical receiver includes a photodiode PD, an operational amplifier OP2, a feedback resistor R4, an isolation capacitor C2, operational amplifiers OP3 and OP4, resistors R5, R6, R7, and R8, and an isolation inductor L. The negative terminal of the photodiode PD is connected to the operating voltage VCC; the positive terminal of the photodiode PD is connected to the inverting input of operational amplifier OP2, and simultaneously connected to the output of operational amplifier OP2 through the feedback resistor R4, forming a transimpedance operational amplifier circuit. The output signal of operational amplifier OP2 is divided into two paths: one path is input to the non-inverting input of operational amplifier OP3 through the isolation capacitor C2, and after passing through the third non-inverting operational amplifier circuit composed of resistors R5, R6, and operational amplifier OP3, the signal is output to the first output port Port1 for the AC component of the output signal; the other path is input to the non-inverting input of operational amplifier OP4 through the isolation inductor L, and after passing through the fourth non-inverting operational amplifier circuit composed of resistors R7, R8, and operational amplifier OP4, the signal is output to the second output port Port2 for the DC component of the output signal.

[0018] As a further improvement to the above scheme, the two servo zero-adjustment compensation circuits include: operational amplifier OP5, operational amplifier OP6, resistor R9, and resistor R. 10 Resistance R 11 Resistance R 12 Resistance R13 Resistance R 14 Resistance R fb1 Resistance R fb2 Feedback capacitor C3 and feedback capacitor C4;

[0019] One end of resistor R9 is connected to the inverting input terminal of operational amplifier OP5, and the other end is connected to the output terminal of operational amplifier OP3; resistor R 10 One end is connected to the operating voltage VCC, and the other end is connected to the non-inverting input of operational amplifier OP5; the output of operational amplifier OP5 is connected through resistor R. fb1 Connect to the inverting input of operational amplifier OP2; resistor R 13 One end of the capacitor is connected to the inverting input of the operational amplifier OP5, and the other end is connected to the output of the operational amplifier OP5; one end of the feedback capacitor C3 is connected to the inverting input of the operational amplifier OP5, and the other end is connected to the output of the operational amplifier OP5.

[0020] resistor R 11 One end of the resistor is connected to the inverting input of operational amplifier OP6, and the other end is connected to the output of operational amplifier OP4; resistor R 12 One end is connected to the operating voltage VCC, and the other end is connected to the non-inverting input of operational amplifier OP6; the output of operational amplifier OP6 is connected to resistor R. fb2 Connect to the inverting input of operational amplifier OP3; resistor R 14 One end of the capacitor is connected to the inverting input of the operational amplifier OP6, and the other end is connected to the output of the operational amplifier OP6; one end of the feedback capacitor C4 is connected to the inverting input of the operational amplifier OP6, and the other end is connected to the output of the operational amplifier OP6.

[0021] As a further improvement to the above solution, the electric field probe includes an antenna capacitor C and a voltage divider capacitor C. in Operational amplifier OP1, resistor R1, resistor R2, isolation resistor R3, capacitor C1, current limiting resistor R bias And a laser diode (LD); wherein, one end of the antenna capacitor C is connected to the voltage divider capacitor C in One end of the capacitor is connected to the non-inverting input of the operational amplifier OP1; the other end of the antenna capacitor C is connected to the positive terminal of the pulse electric field voltage signal collected by the antenna, and the negative terminal of the pulse electric field voltage signal is connected to the voltage divider capacitor C. inThe other end is grounded; the inverting input of operational amplifier OP1 is grounded through resistor R1 and connected to the output of operational amplifier OP1 through resistor R2, thus forming the first non-inverting operational amplifier circuit; the output of operational amplifier OP1 is connected in sequence to isolation resistor R3, capacitor C1 and the positive terminal of laser diode LD; the positive terminal of laser diode LD is also connected to current limiting resistor R bias With DC voltage source U d The laser diode (LD) is connected in series; the negative terminal of the LD is grounded, and the emitted optical signal is transmitted to the optical receiver through an optical fiber.

[0022] As a further improvement to the above scheme, feedback capacitors C3 and C4 can both be selected from any one of tantalum capacitors, C0G type capacitors, and NPO capacitors.

[0023] As a further improvement to the above scheme, both operational amplifiers OP5 and OP6 use the OPA2188.

[0024] Compared with the prior art, the beneficial effects of the present invention are:

[0025] 1. The time drift compensation method for a model-parameterized pulse electric field measurement system disclosed in this invention, through parametric modeling in simulation software, introduces a DC servo loop at the end of the pulse measurement system to achieve real-time automatic compensation for low-frequency baseline drift (time drift) caused by operational amplifier input offset, power supply fluctuations, and temperature changes, significantly improving the stability and accuracy of the system measurement. This compensation circuit only operates on extremely low-frequency components and does not affect the high-frequency characteristics of the broadband pulse electric field signal, thus effectively suppressing zero-point drift while preserving the system's fast response performance.

[0026] 2. After parametric modeling in simulation software, and considering the influence of system device replacement, fiber insertion loss changes, temperature changes and time drift, the present invention can quickly obtain the true electric field strength of the measured electric field after only one calibration in the laboratory.

[0027] 3. This invention incorporates the electrical parameters of key components in the measurement system (such as antennas, preamplifiers, operational amplifiers, lasers, and photodetectors) into a unified mathematical modeling framework. Combined with the system's drift response characteristics, a dynamic model of the entire "electric field signal-system response-output result" chain is constructed. This model allows for real-time analysis and estimation of the system's zero-point drift trend. Furthermore, servo feedback compensation and filtering self-stabilization techniques are employed to stabilize the output baseline, significantly improving the system's temporal stability and measurement repeatability without increasing power consumption or size. Attached Figure Description

[0028] Figure 1 This is a flowchart of the time drift compensation method for the pulse electric field measurement system based on model parameterization in Embodiment 1 of the present invention.

[0029] Figure 2 This is a circuit diagram of the parameterized model in Embodiment 1 of the present invention.

[0030] Figure 3 This is a comparison between the real electric field waveform reconstructed after substituting the measured waveform into the model in this embodiment of the invention and the actual electric field waveform. Detailed Implementation

[0031] The following will clearly and completely describe the technical solutions in the embodiments of the present invention in conjunction with the accompanying drawings. Obviously, the described embodiments are only part of the embodiments of the present invention, not all of the embodiments. All other embodiments obtained by ordinary technicians in this field based on the embodiments of the present invention without making any creative efforts shall fall within the scope of protection of the present invention.

[0032] Example 1

[0033] Please see Figure 1 This embodiment provides a time drift compensation method for a pulsed electric field measurement system based on model parameterization. The pulsed electric field measurement system includes an antenna, an electric field probe, and an optical receiver connected in sequence. The electric field probe is used to amplify and modulate the electrical signal collected by the antenna in the pulsed electric field into an optical signal. The optical receiver includes a photodetector, a transimpedance operational amplifier circuit, a third in-phase operational amplifier circuit, and a fourth in-phase operational amplifier circuit. The transimpedance operational amplifier circuit is used to convert the photoresponse current output by the photodetector into a voltage signal. The third in-phase operational amplifier circuit and the fourth in-phase operational amplifier circuit are used to extract the AC and DC components of the voltage signal, respectively.

[0034] The time drift compensation method includes steps S1 to S4.

[0035] S1. Construct a parameterized model in MATLAB simulation software. This parameterized model adds two servo zero-adjustment compensation circuits to the pulse electric field measurement system. The two servo zero-adjustment compensation circuits are connected to the output terminals of the third and fourth in-phase operational amplifier circuits, respectively, and form a negative feedback loop to dynamically suppress low-frequency baseline drift.

[0036] The construction of the parameterized model specifically refers to the parameterized modeling of the antenna's size and structure, the modeling of the operational amplifier parameters in the electric field probe, and the modeling of the operational amplifier in the optical receiver. After the entire model is established, multiple measurements of the real electric field strength can be achieved with only one calibration.

[0037] S2. Acquire the time-domain waveform data of the electric field at the output of the third in-phase operational amplifier circuit.

[0038] S3. Calculate the transfer function of the pulse electric field measurement system in the parameterized model, transform the transfer function from the frequency domain state to the time domain state through inverse Fourier transform, and then deconvolve the transfer function in the time domain state with the electric field time domain waveform data to obtain the true electric field intensity.

[0039] In step S3, the expression for the transfer function is:

[0040]

[0041] In the formula, H(ω) is the transfer function; ω is the independent variable of the frequency domain function; A OL (ω) is the open-loop gain of the operational amplifier in the third in-phase operational amplifier circuit, U OP3 (ω) is the AC voltage signal output by the operational amplifier, H servo (ω) is the transfer function of the servo zero-adjustment compensation circuit connected to the third in-phase operational amplifier circuit; U oc (ω) represents the equivalent open-circuit output voltage signal of the electric field probe.

[0042] like Figure 2 As shown, the pulse electric field measurement system in the parameterized model can be divided into a monopole antenna 1, a high-impedance input operational amplifier circuit 2 (i.e., the first in-phase operational amplifier circuit), a semiconductor laser 3, a photodetector 4, a transimpedance operational amplifier circuit 5, an in-phase operational amplifier circuit 6 (i.e., the third in-phase operational amplifier circuit), an in-phase operational amplifier circuit 7 (i.e., the fourth in-phase operational amplifier circuit), a servo zero-adjustment compensation circuit 8, and a servo zero-adjustment compensation circuit 9. Figure 2 In the figure, E(ω) is the electric field strength to be measured, and h e Let U be the equivalent height of the antenna. In the transfer function of the above system, U... OP3 (ω) / U oc (ω) can be calculated in the following way:

[0043] U OP3 (ω) / U oc (ω)=G1(ω)·G2(ω)·G3(ω)·G4(ω)·G5(ω)·G6(ω)

[0044] Wherein, G1(ω) corresponds to the transfer function of monopole antenna 1, specifically relating to the probe load voltage division ratio; G2(ω) corresponds to the high-impedance input operational amplifier circuit 2, specifically relating to the frequency response of the first-stage operational amplifier; G3(ω) corresponds to the transfer function of semiconductor laser 3, specifically relating to LD current conversion; G4(ω) corresponds to the transfer function of photodetector 4, specifically relating to photoelectric conversion and scaling factor; G5(ω) corresponds to the transfer function of transimpedance operational amplifier circuit 5, specifically relating to photocurrent pre-amplification; and G6(ω) corresponds to the transfer function of in-phase operational amplifier circuit 6, specifically relating to Port1 output amplification.

[0045] S4. When the state of the device in the pulse electric field measurement system changes (such as device replacement, fiber insertion loss change, temperature change), the parameterized model is updated in the simulation software according to the corresponding device characteristics after the change, and the updated real electric field intensity is obtained in accordance with the method of steps S2 to S3.

[0046] The electric field probe includes an antenna capacitor C and a voltage divider capacitor C. in Operational amplifier OP1, resistor R1, resistor R2, isolation resistor R3, capacitor C1, current limiting resistor R bias And a laser diode (LD); wherein, one end of the antenna capacitor C is connected to the voltage divider capacitor C in One end of the capacitor is connected to the non-inverting input of the operational amplifier OP1; the other end of the antenna capacitor C is connected to the positive terminal of the pulse electric field voltage signal collected by the antenna, and the negative terminal of the pulse electric field voltage signal is connected to the voltage divider capacitor C. in The other end is grounded; the inverting input of operational amplifier OP1 is grounded through resistor R1 and connected to the output of operational amplifier OP1 through resistor R2, thus forming the first non-inverting operational amplifier circuit; the output of operational amplifier OP1 is connected in sequence to isolation resistor R3, capacitor C1 and the positive terminal of laser diode LD, realizing dynamic modulation of LD current by pulse signal; at the same time, the positive terminal of laser diode LD is also connected to current limiting resistor R bias With DC voltage source U d The laser diode (LD) is connected in series to provide bias current to keep it at a suitable operating point; the negative terminal of the LD is grounded, and the emitted optical signal is transmitted to the optical receiver through an optical fiber.

[0047] The optical receiver includes a photodiode PD, an operational amplifier OP2, a feedback resistor R4, an isolation capacitor C2, operational amplifiers OP3 and OP4, resistors R5, R6, R7, and R8, and an isolation inductor L. The negative terminal of the photodiode PD is connected to the operating voltage VCC. The positive terminal of the photodiode PD is connected to the inverting input of operational amplifier OP2 and, through the feedback resistor R4, to the output of operational amplifier OP2, forming a transimpedance operational amplifier circuit. The output signal of operational amplifier OP2 is divided into two paths: one path is input to the non-inverting input of operational amplifier OP3 through isolation capacitor C2, and after passing through the third non-inverting operational amplifier circuit formed by resistors R5, R6, and operational amplifier OP3, the signal is output to the first output port Port1, used for the AC component of the output signal; the other path is input to the non-inverting input of operational amplifier OP4 through isolation inductor L, and after passing through the fourth non-inverting operational amplifier circuit formed by resistors R7, R8, and operational amplifier OP4, the signal is output to the second output port Port2, used for the DC component of the output signal.

[0048] The two servo zero-adjustment compensation circuits include: operational amplifier OP5, operational amplifier OP6, resistor R9, and resistor R. 10 Resistance R 11 Resistance R 12 Resistance R 13 Resistance R 14 Resistance R fb1 Resistance R fb2 Feedback capacitor C3 and feedback capacitor C4;

[0049] One end of resistor R9 is connected to the inverting input terminal of operational amplifier OP5, and the other end is connected to the output terminal of operational amplifier OP3; resistor R 10 One end is connected to the operating voltage VCC, and the other end is connected to the non-inverting input of operational amplifier OP5; the output of operational amplifier OP5 is connected through resistor R. fb1 Connected to the inverting input of operational amplifier OP2, it forms a transimpedance amplifier circuit; resistor R 13 One end of the capacitor is connected to the inverting input of the operational amplifier OP5, and the other end is connected to the output of the operational amplifier OP5; one end of the feedback capacitor C3 is connected to the inverting input of the operational amplifier OP5, and the other end is connected to the output of the operational amplifier OP5.

[0050] resistor R 11 One end of the resistor is connected to the inverting input of operational amplifier OP6, and the other end is connected to the output of operational amplifier OP4; resistor R 12One end is connected to the operating voltage VCC, and the other end is connected to the non-inverting input of operational amplifier OP6; the output of operational amplifier OP6 is connected to resistor R. fb2 Connected to the inverting input of operational amplifier OP3, it forms a transimpedance amplifier circuit; resistor R 14 One end of the capacitor is connected to the inverting input of the operational amplifier OP6, and the other end is connected to the output of the operational amplifier OP6; one end of the feedback capacitor C4 is connected to the inverting input of the operational amplifier OP6, and the other end is connected to the output of the operational amplifier OP6.

[0051] In this embodiment, the pulse electric field measurement circuit uses a monopole antenna 1 to couple the spatial electric field, and amplifies the electrical signal through a high-impedance input operational amplifier circuit 2 before inputting it into a semiconductor laser 3. The semiconductor laser 3 converts the electrical signal into an optical signal and transmits it to the back-end optical receiver. The electric field signal collected by the optical receiver is substituted into the established parameterized model, and the true electric field intensity is obtained in one step without repeated calibration.

[0052] The pulsed electric field measurement circuit uses a monopole antenna to couple the spatial electric field. The electrical signal is amplified by a high-impedance input operational amplifier circuit and then input to a semiconductor laser. The semiconductor laser converts the electrical signal into an optical signal and transmits it to the downstream optical receiver. The output of operational amplifier OP3 (Port1) and a high-resistance resistor R9 = 10MΩ are connected to the inverting input of operational amplifier OP5. An integrating capacitor C3 = 1.6μF and an anti-saturation resistor R are used. 13 =100MΩ is connected in parallel in the feedback loop of amplifier OP5. The output of operational amplifier OP5 passes through the feedback resistor R. fb1 =10MΩ is injected into the inverting input of the preamplifier OP2, setting the cutoff frequency to f. c =1 / 2πR9C3 = 0.01Hz;

[0053] The output signal of Port2 is input to the servo control operational amplifier OP6, and the output of operational amplifier OP4 (i.e., the output of Port2) is connected to the high-resistance resistor R. 11 A 10MΩ resistor is connected to the inverting input of operational amplifier OP6. An integrating capacitor C4 of 1.6μF and an anti-saturation resistor R are used. 14 =100MΩ is connected in parallel in the feedback loop of amplifier OP6. The output of amplifier OP6 passes through the feedback resistor R. fb2 =10MΩ is injected into the inverting input of the preamplifier OP3, setting the cutoff frequency to f. c =1 / 2πR 11C4 = 0.01Hz is used to filter out DC and low-frequency drift components in the pulse signal; the output of OP6 is connected back to the inverting input of the main output amplifier OP3 to achieve negative feedback compensation control. This structure forms a low-frequency dynamic compensation loop, so that when a low-frequency DC offset occurs at the system output Port2 (e.g., caused by operational amplifier input offset, temperature drift, power supply changes, etc.), the offset signal is low-pass filtered and amplified, and fed back to the input of the previous stage with a negative adjustment effect, thereby automatically canceling the offset component, and finally achieving DC stability and constant baseline at the main output Port2.

[0054] In particular, the operational amplifiers OP5 and OP6 in the two servo zero-adjustment compensation circuits can both be selected from the low input bias current and low offset drift device OPA2188, and the feedback capacitors can be tantalum capacitors or C0G / NP0 type high stability capacitors to ensure low time drift.

[0055] This embodiment also verifies the above-mentioned time drift compensation method by placing the electric field measurement system with the added servo zero-adjustment compensation circuit into a uniform square wave electric field for electric field measurement, and comparing the experimental results with the actual square wave signal waveform.

[0056] The results are as follows Figure 3 As shown, it can be seen that the square wave electric field measured by the electric field measurement system after adding the servo zero-adjustment compensation circuit is in good agreement with the actual square wave electric field waveform, effectively realizing the "time drift" compensation of the original electric field measurement system.

[0057] The above description is only a preferred embodiment of the present invention, but the scope of protection of the present invention is not limited thereto. Any equivalent substitutions or modifications made by those skilled in the art within the scope of the technology disclosed in the present invention, based on the technical solution and inventive concept of the present invention, should be covered within the scope of protection of the present invention.

Claims

1. A time drift compensation method for a pulsed electric field measurement system based on model parameterization, wherein the pulsed electric field measurement system comprises an antenna, an electric field probe, and an optical receiver connected in sequence; the electric field probe is used to amplify and modulate the electrical signal collected by the antenna in the pulsed electric field into an optical signal; the optical receiver comprises a photodetector, a transimpedance operational amplifier circuit, a third in-phase operational amplifier circuit, and a fourth in-phase operational amplifier circuit; the transimpedance operational amplifier circuit is used to convert the photoresponse current output by the photodetector into a voltage signal, and the third in-phase operational amplifier circuit and the fourth in-phase operational amplifier circuit are respectively used to extract the AC and DC components of the voltage signal; characterized in that, The time drift compensation method includes: S1. Construct a parameterized model in the simulation software. This parameterized model adds two servo zero-adjustment compensation circuits to the pulse electric field measurement system. The two servo zero-adjustment compensation circuits are respectively connected to the output terminals of the third and fourth in-phase operational amplifier circuits and form a negative feedback loop to dynamically suppress low-frequency baseline drift. S2. Acquire the time-domain waveform data of the electric field at the output of the third in-phase operational amplifier circuit; S3. Calculate the transfer function of the pulse electric field measurement system in the parameterized model, transform the transfer function from the frequency domain state to the time domain state through inverse Fourier transform, and then deconvolve the transfer function in the time domain state with the electric field time domain waveform data to obtain the true electric field intensity.

2. The time drift compensation method for a pulse electric field measurement system based on model parameterization according to claim 1, characterized in that, In step S3, the expression for the transfer function is: In the formula, H(ω) is the transfer function; ω is the independent variable of the frequency domain function; A OL (ω) is the open-loop gain of the operational amplifier in the third in-phase operational amplifier circuit, U OP3 (ω) is the AC voltage signal output by the operational amplifier, H servo (ω) is the transfer function of the servo zero-adjustment compensation circuit connected to the third in-phase operational amplifier circuit; U oc (ω) represents the equivalent open-circuit output voltage signal of the electric field probe.

3. The time drift compensation method for a pulse electric field measurement system based on model parameterization according to claim 1, characterized in that, The time drift compensation method further includes: S4. When the state of the device in the pulse electric field measurement system changes, the parameterized model is updated in the simulation software according to the corresponding device characteristics after the change, and the updated real electric field intensity is obtained in accordance with the method of steps S2 to S3.

4. The time drift compensation method for a pulse electric field measurement system based on model parameterization according to claim 1, characterized in that, The optical receiver includes a photodiode PD, an operational amplifier OP2, a feedback resistor R4, an isolation capacitor C2, operational amplifiers OP3 and OP4, resistors R5, R6, R7, and R8, and an isolation inductor L. The negative terminal of the photodiode PD is connected to the operating voltage VCC. The positive terminal of the photodiode PD is connected to the inverting input of operational amplifier OP2 and, through the feedback resistor R4, to the output of operational amplifier OP2, forming a transimpedance operational amplifier circuit. The output signal of operational amplifier OP2 is divided into two paths: one path is input to the non-inverting input of operational amplifier OP3 through isolation capacitor C2, and after passing through the third non-inverting operational amplifier circuit formed by resistors R5, R6, and operational amplifier OP3, the signal is output to the first output port Port1, used for the AC component of the output signal; the other path is input to the non-inverting input of operational amplifier OP4 through isolation inductor L, and after passing through the fourth non-inverting operational amplifier circuit formed by resistors R7, R8, and operational amplifier OP4, the signal is output to the second output port Port2, used for the DC component of the output signal.

5. The time drift compensation method for a pulse electric field measurement system based on model parameterization according to claim 4, characterized in that, The two servo zero-adjustment compensation circuits include: operational amplifier OP5, operational amplifier OP6, resistor R9, and resistor R. 10 Resistance R 11 Resistance R 12 Resistance R 13 Resistance R 14 Resistance R fb1 Resistance R fb2 Feedback capacitor C3 and feedback capacitor C4; One end of resistor R9 is connected to the inverting input terminal of operational amplifier OP5, and the other end is connected to the output terminal of operational amplifier OP3; resistor R 10 One end is connected to the operating voltage VCC, and the other end is connected to the non-inverting input of operational amplifier OP5; the output of operational amplifier OP5 is connected through resistor R. fb1 Connect to the inverting input of operational amplifier OP2; resistor R 13 One end of the capacitor is connected to the inverting input of the operational amplifier OP5, and the other end is connected to the output of the operational amplifier OP5; one end of the feedback capacitor C3 is connected to the inverting input of the operational amplifier OP5, and the other end is connected to the output of the operational amplifier OP5. resistor R 11 One end of the resistor is connected to the inverting input of operational amplifier OP6, and the other end is connected to the output of operational amplifier OP4; resistor R 12 One end is connected to the operating voltage VCC, and the other end is connected to the non-inverting input of operational amplifier OP6; the output of operational amplifier OP6 is connected to resistor R. fb2 Connect to the inverting input of operational amplifier OP3; resistor R 14 One end of the capacitor is connected to the inverting input of the operational amplifier OP6, and the other end is connected to the output of the operational amplifier OP6; one end of the feedback capacitor C4 is connected to the inverting input of the operational amplifier OP6, and the other end is connected to the output of the operational amplifier OP6.

6. The time drift compensation method for a pulse electric field measurement system based on model parameterization according to claim 4 or 5, characterized in that, The electric field probe includes an antenna capacitor C and a voltage divider capacitor C. in Operational amplifier OP1, resistor R1, resistor R2, isolation resistor R3, capacitor C1, current limiting resistor R bias And a laser diode (LD); wherein, one end of the antenna capacitor C is connected to the voltage divider capacitor C in One end of the capacitor is connected to the non-inverting input of the operational amplifier OP1; the other end of the antenna capacitor C is connected to the positive terminal of the pulse electric field voltage signal collected by the antenna, and the negative terminal of the pulse electric field voltage signal is connected to the voltage divider capacitor C. in The other end is grounded; the inverting input of operational amplifier OP1 is grounded through resistor R1 and connected to the output of operational amplifier OP1 through resistor R2, thus forming the first non-inverting operational amplifier circuit; the output of operational amplifier OP1 is connected in sequence to isolation resistor R3, capacitor C1 and the positive terminal of laser diode LD; the positive terminal of laser diode LD is also connected to current limiting resistor R bias With DC voltage source U d The laser diode (LD) is connected in series; the negative terminal of the LD is grounded, and the emitted optical signal is transmitted to the optical receiver through an optical fiber.

7. The time drift compensation method for a pulse electric field measurement system based on model parameterization according to claim 5, characterized in that, Both feedback capacitors C3 and C4 can be selected from tantalum capacitors, C0G type capacitors, and NP0 capacitors.

8. The time drift compensation method for a pulse electric field measurement system based on model parameterization according to claim 7, characterized in that, Both operational amplifiers OP5 and OP6 use the OPA2188.

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