Signal transmitting link and method, integrated circuit, electromagnetic wave device and equipment

Abstract

A signal transmission link and method, an integrated circuit, an electromagnetic wave device and equipment, the signal transmission link comprising: a waveform generator and a plurality of transmission channels connected with the waveform generator, at least two of the transmission channels having different signal transmission delays, at least one of the transmission channels comprising a direct digital frequency synthesizer, and the direct digital frequency synthesizer is configured to generate a compensation signal according to the delay inequality of the signal transmission delay of the corresponding transmission channel relative to the reference transmission delay, and compensate the transmission signal of the corresponding transmission channel by using the compensation signal.

Description

Technical Field

[0001] The embodiments of the present disclosure relate to, but are not limited to, the technical field of electromagnetic wave devices, and in particular to a signal transmission link and method, an integrated circuit, an electromagnetic wave device and equipment. Background Art

[0002] At present, in order to improve the measurement accuracy, the frequency modulated continuous wave (FMCW) radar system adopts multi-antenna transmission technology. In order to achieve better isolation between the transmitting antennas, it is increasingly difficult to design the same antenna feeder length for different transmitting antennas.

[0003] Unequal length transmit antenna feeders can solve the above antenna design problems. Unequal length transmit antenna feeders can achieve better link budget, simpler antenna design and routing, lower antenna coupling, better target angle resolution performance, smaller modules and costs, etc. However, different transmit antenna feeder lengths will cause different relative delays of RF signals passing through different transmit antennas, which will affect the quality of the transmit signal and the accuracy of the radar system detection results. Summary of the invention

[0004] The following is a summary of the subject matter described in detail herein. This summary is not intended to limit the scope of the claims.

[0005] An embodiment of the present disclosure provides a signal transmission link, comprising: a waveform generator and multiple transmission channels connected to the waveform generator, at least two of the transmission channels have different signal transmission delays from the waveform generator to the transmission antenna, and at least one of the transmission channels comprises a direct digital frequency synthesizer; the direct digital frequency synthesizer is configured to generate a compensation signal according to a delay difference of the signal transmission delay of the corresponding transmission channel relative to a reference transmission delay, and use the compensation signal to compensate the transmission signal of the corresponding transmission channel.

[0006] An embodiment of the present disclosure further provides an integrated circuit, comprising a signal transceiver link as described in any embodiment of the present disclosure.

[0007] An embodiment of the present disclosure further provides an electromagnetic wave device, comprising: a carrier; an integrated circuit as described in any one of the present disclosure, arranged on the carrier; an antenna, arranged on the carrier, or the antenna and the integrated circuit are integrated into a single device and arranged on the carrier; the antenna comprises a transmitting antenna and a receiving antenna; wherein the integrated circuit is connected to the antenna for transmitting the radio frequency transmitting signal and / or receiving the radio frequency receiving signal.

[0008] An embodiment of the present disclosure also provides a device, comprising: a device body; and an electromagnetic wave device as described in any embodiment of the present disclosure, which is arranged on the device body; wherein the electromagnetic wave device is used for target detection and / or communication to provide reference information for the operation of the device body.

[0009] An embodiment of the present disclosure also provides a signal transmission method, which is applied to an antenna array of an electromagnetic wave device having at least two signal transmission links. The signal transmission method includes: determining a reference transmission delay and a delay difference between the signal transmission delay of each of the transmission channels and the reference transmission delay; generating a compensation signal corresponding to each of the transmission channels according to the delay difference; and using the compensation signal to compensate for the transmission signal of the corresponding transmission channel.

[0010] The embodiments of the present disclosure also provide a non-transitory computer-readable storage medium on which computer-readable instructions are stored. When the instructions are executed by a processor, the processor executes the signal sending and receiving method as described in any embodiment of the present disclosure.

[0011] The signal transmission link and method, integrated circuit, electromagnetic wave device and equipment of the embodiments of the present disclosure generate a compensation signal through a direct digital frequency synthesizer according to the delay difference of the signal transmission delay of the transmission channel relative to the reference transmission delay, and use the compensation signal to compensate the transmission signal of the corresponding transmission channel, thereby solving the problem of different relative delays of radio frequency signals passing through different transmission antennas due to inconsistent transmission antenna feeder lengths, improving the quality of the transmission signal, and then improving the quality of the received signal, and ultimately improving the detection accuracy and detection range of the radar system.

[0012] Other aspects will become apparent upon reading and understanding the drawings and detailed description. BRIEF DESCRIPTION OF THE DRAWINGS

[0013] The accompanying drawings are used to provide a further understanding of the technical solution of the present disclosure and constitute a part of the specification. Together with the embodiments of the present disclosure, they are used to explain the technical solution of the present disclosure and do not constitute a limitation on the technical solution of the present disclosure. The shapes and sizes of the components in the accompanying drawings do not reflect the actual proportions and are only intended to illustrate the contents of the present disclosure.

[0014] Figure 1 A schematic diagram of the structure of a signal transmission link provided for an exemplary embodiment of the present disclosure;

[0015] Figure 2 A schematic diagram of an FMCW transmission signal using sawtooth wave modulation;

[0016] Figure 3A and Figure 3B Schematic diagram of FMCW transmission signals and their echo signals from two different transmitting antennas;

[0017] Figure 4A A schematic diagram of the structure of a transmission channel provided for an exemplary embodiment of the present disclosure;

[0018] Figure 4B A simplified schematic diagram of a signal transmission link of a digital phase shifter architecture in an embodiment of the present disclosure;

[0019] Figure 4C Based on Figure 4B A schematic diagram of a digital phase shifter architecture in a signal transmission link is shown;

[0020] Figure 4D is a schematic diagram of a transmission link including a specific compensation module in an embodiment of the present disclosure;

[0021] Figure 4E It is a schematic diagram of calibrating and compensating a transmission link using an auxiliary receiving circuit in an embodiment of the present disclosure;

[0022] Figure 5 A flowchart of a signal transmission method provided by an exemplary embodiment of the present disclosure. DETAILED DESCRIPTION

[0023] In order to make the purpose, technical solution and advantages of the present disclosure more clear, the embodiments of the present disclosure will be described in detail below with reference to the accompanying drawings. It should be noted that the embodiments and features in the embodiments of the present disclosure can be combined with each other arbitrarily without conflict.

[0024] Unless otherwise defined, the technical terms or scientific terms used in the embodiments of the present disclosure should be understood by people with ordinary skills in the field to which the present disclosure belongs. The "first", "second" and similar words used in the embodiments of the present disclosure do not indicate any order, quantity or importance, but are only used to distinguish different components. "Include" or "comprising" and similar words mean that the elements or objects before the word cover the elements or objects listed after the word and their equivalents, without excluding other elements or objects.

[0025] Radar is an electronic device that uses electromagnetic waves to detect targets. The radar chip transmits a beam through a signal transmission link. When the transmitted beam encounters an obstacle, the echo reflected by the obstacle is received by the receiving antenna and transmitted to the radar chip. The radar chip determines the position, distance, speed and other information of the target relative to the electromagnetic wave emission point. With the development of microelectronics and other technologies, radar has gradually been widely used, especially millimeter wave radar (such as automotive radar). Due to its small antenna size, it has been widely used in autonomous driving, smart home devices and industrial automation devices. At present, the miniaturization and integration of radar has become the current development trend.

[0026] Antenna feeder is a device for transmitting, controlling and distributing radio frequency electromagnetic signal energy in radar. Due to the requirements of miniaturization and integration of radar, the layout of antenna feeder has a significant impact on the quality of radar chip sensing signal. At present, the layout of antenna feeder depends on the positional relationship between the transceiver unit and the antenna in the radar chip. In the multi-input multi-output (MIMO) system, there are multiple groups of transceiver antennas. In order to ensure the accuracy of target detection, it is necessary to ensure that the relative delay generated by each transmitting antenna is the same. However, when using the design method of unequal length transmitting antenna feeder, due to the different lengths of each transmitting antenna feeder, the relative delay generated by the RF signal after passing through different transmitting antennas is not the same.

[0027] like Figure 1 As shown, an embodiment of the present disclosure provides a signal transmission link, including a waveform generator 101, a plurality of transmission channels 100 connected to the waveform generator 101, and a plurality of transmission antennas 107 connected one-to-one to the transmission channels 100, at least two transmission channels 100 have different signal transmission delays from the waveform generator 101 to the transmission antenna 107, and at least one transmission channel 100 includes: a direct digital frequency synthesizer 102.

[0028] The direct digital frequency synthesizer 102 is configured to generate a compensation signal according to a delay difference of a signal transmission delay of the corresponding transmission channel 100 relative to a reference transmission delay, and use the compensation signal to compensate for the transmission signal of the corresponding transmission channel 100 .

[0029] For example, Figure 1 The signal transmission link shown includes four transmission channels, however, the embodiment of the present disclosure is not limited to this, and the number of transmission channels can be set as needed. Figure 1 As shown, in the four transmission channels, the lengths of the transmission antenna feed lines 10, 11, 12 and 13 are different, and the relative delays generated by the transmission signals passing through the transmission antenna feed lines 10, 11, 12 and 13 are also different. In the disclosed embodiment, the direct digital frequency synthesizer 102 generates a compensation signal according to the delay difference of the signal transmission delay of the transmission channel 100 corresponding to itself relative to the reference transmission delay, and uses the compensation signal to compensate the transmission signal of the transmission channel 100 corresponding to itself, thereby solving the problem that the RF signals passing through different transmission antennas have different relative delays due to inconsistent transmission antenna feed line lengths, improving the quality of the transmission signal, thereby improving the quality of the received signal, and ultimately improving the detection accuracy and detection range of the radar system.

[0030] In some exemplary embodiments, the transmission channel further includes a digital-to-analog converter 103, a low-pass filter 104, a mixer 105, and a power amplifier 106. The signal transmission link further includes a local oscillator 108. The waveform generator 101, the direct digital frequency synthesizer 102, the digital-to-analog converter 103, the low-pass filter 104, the mixer 105, the power amplifier 106, and the transmission antenna 107 are connected in sequence. The local oscillator 108 is respectively connected to the waveform generator 101 and the mixer 105 of each transmission channel, wherein:

[0031] The waveform generator 101 is configured to generate an initial transmission signal and output it to the direct digital frequency synthesizer 102 and the local oscillator 108;

[0032] Direct digital frequency synthesizer 102, configured to perform phase compensation and / or frequency compensation on the transmission signal

[0033] A digital-to-analog converter 103 is configured to perform digital-to-analog conversion on the received signal and output the converted signal to a low-pass filter 104;

[0034] A low-pass filter 104 is configured to perform low-pass filtering on the received signal and output the signal to the mixer 105;

[0035] The mixer 105 is configured to multiply the eigensignal generated by the local oscillator 108 and the signal output by the low-pass filter 104 to generate a radio frequency signal and output the radio frequency signal to the power amplifier 106;

[0036] A power amplifier 106 is configured to amplify the power of the radio frequency signal and output the amplified signal to the transmitting antenna 107;

[0037] The local oscillator 108 is configured to generate an eigensignal according to the initial transmission signal and output the eigensignal to the mixer 105 .

[0038] In the embodiment of the present disclosure, the initial transmission signal may be a frequency-modulated continuous wave (FMCW) signal, however, the embodiment of the present disclosure is not limited to this.

[0039] In some exemplary embodiments, a direct digital frequency synthesizer 102 is provided for each transmission channel, wherein each direct digital frequency synthesizer 102 is configured to generate a compensation signal according to a delay difference of a signal transmission delay of the transmission channel in which it is located relative to a reference transmission delay, and use the compensation signal to compensate for the transmission signal of the transmission channel in which it is located.

[0040] It should be noted that although Figure 1In the signal transmission link shown, each transmission channel 100 is provided with a direct digital frequency synthesizer 102. However, in actual applications, some transmission channels 100 may not be provided with a direct digital frequency synthesizer 102. For example, when the signal transmission delay of a certain transmission channel 100 is a reference transmission delay and the signal transmission link is a fixed-frequency signal transmission link, the transmission channel 100 may not be provided with a direct digital frequency synthesizer 102. For a transmission channel without a direct digital frequency synthesizer 102, it includes a digital-to-analog converter 103, a low-pass filter 104, a mixer 105 and a power amplifier 106 connected in sequence. The waveform generator 101 generates an initial transmission signal and outputs it to the digital-to-analog converter 103 and the local oscillator 108. The digital-to-analog converter 103 performs digital-to-analog conversion on the received signal and outputs it to the low-pass filter 104. The low-pass filter 104 performs low-pass filtering on the received signal and outputs it to the mixer 105. The mixer 105 multiplies the intrinsic signal generated by the local oscillator 108 by the signal output by the low-pass filter 104 to generate a radio frequency signal and output the radio frequency signal to the power amplifier 106. The power amplifier 106 amplifies the power of the radio frequency signal and outputs the amplified signal to the transmitting antenna 107. The local oscillator 108 generates an intrinsic signal according to the initial transmission signal and outputs it to the mixer 105.

[0041] like Figure 1 As shown, since each transmission channel uses the same local oscillator 108, the length of the signal line from the local oscillator 108 to the mixer 105 of each transmission channel ( Figure 1 There are also differences in 20, 21, 22, and 23), and this difference will also cause different relative delays in different transmission channels.

[0042] In some exemplary embodiments, the signal transmission delays of at least two transmitting channels are different, including different signal transmission delays generated by transmitting antenna feed lines of at least two transmitting channels, and / or different signal transmission delays generated by signal lines from local oscillators to mixers of at least two transmitting channels.

[0043] In the embodiment of the present disclosure, the direct digital frequency synthesizer 102 generates a compensation signal according to the delay difference of the signal transmission delay of the corresponding transmission channel 100 relative to the reference transmission delay, including: the direct digital frequency synthesizer 102 generates a compensation signal according to the delay difference of the signal transmission delay generated by the transmission antenna feeder of the corresponding transmission channel 100 relative to the first reference transmission delay, and / or, the delay difference of the signal transmission delay generated by the signal line from the local oscillator 108 to the mixer 105 of the corresponding transmission channel 100 relative to the second reference transmission delay. However, the embodiment of the present disclosure is not limited to this, and the direct digital frequency synthesizer 102 can also generate a compensation signal according to the delay difference of the signal transmission delay generated at other positions in the corresponding transmission channel 100 relative to the reference transmission delay, thereby solving the problem of different signal transmission delays caused by the length difference of the signal line from the local oscillator 108 to the mixer 105 of at least two transmission channels 100 or the difference at any other position.

[0044] In some exemplary embodiments, when the delay difference of the signal transmission delay of the transmission channel relative to the reference transmission delay includes the delay difference of the signal transmission delay of the transmission antenna feeder of the transmission channel relative to the first reference transmission delay, the first reference transmission delay may be the signal transmission delay generated by the transmission antenna feeder of any one of the multiple transmission channels. When the delay difference of the signal transmission delay of the transmission channel relative to the reference transmission delay includes the delay difference of the signal transmission delay from the local oscillator to the mixer of the transmission channel relative to the second reference transmission delay, the second reference transmission delay may be the signal transmission delay generated by the signal line from the local oscillator to the mixer of any one of the multiple transmission channels.

[0045] In some exemplary embodiments, when the delay difference of the signal transmission delay of the transmission channel relative to the reference transmission delay includes the delay difference of the signal transmission delay of the transmission antenna feeder of the transmission channel relative to the first reference transmission delay, the first reference transmission delay may be the signal transmission delay generated by the shortest transmission antenna feeder among the multiple transmission channels. When the delay difference of the signal transmission delay of the transmission channel relative to the reference transmission delay includes the delay difference of the signal transmission delay from the local oscillator to the mixer of the transmission channel relative to the second reference transmission delay, the second reference transmission delay may be the signal transmission delay generated by the shortest signal line from the local oscillator to the mixers among the multiple transmission channels.

[0046] Figure 2 FIG. 1 is a schematic diagram of an FMCW transmission signal using sawtooth wave modulation, such as Figure 2 As shown, a sawtooth is usually called a chirp. In some exemplary embodiments, the mathematical expression corresponding to the initial transmission signal generated by the waveform generator is as follows:

[0047]

[0048] Where t is time, f c is the starting frequency of a chirp during the frequency sweep process, β is the frequency variation range of a chirp during the frequency sweep process, T is the scanning duration of a chirp during the frequency sweep process, and θ is the initial phase.

[0049] Figure 3A and Figure 3B Schematic diagram of FMCW transmission signals and their echo signals of two different transmitting antennas, as shown in Figure 3A and Figure 3B As shown in the figure, due to the different relative delays of the transmission channels corresponding to the two transmitting antennas, △t1>△t0, that is, Figure 3B The relative delay of the transmitting antenna shown is greater than Figure 3A The relative time delay of the transmitting antennas shown in the figure causes a difference in the distance frequency of the target detected by the two transmitting antennas, △f1>△f0, which in turn affects the final detection result of the radar chip.

[0050] Assuming that the signal transmission delay generated by the transmission antenna feed line of any one of the multiple transmission channels is defined as the first reference delay τ1, and the signal transmission delay generated by the signal line from the local oscillator to the mixer of any one of the multiple transmission channels is defined as the second reference delay τ2, the FMCW signal after the first reference delay τ1 and the second reference delay τ2 can be expressed as follows:

[0051]

[0052] Where t≥τ=τ1+τ2.

[0053] In the embodiment of the present disclosure, the first reference delay τ1 can be defined as the signal transmission delay generated by the shortest transmitting antenna feeder, and the second reference delay τ2 can be defined as the signal transmission delay generated by the shortest signal line from the local oscillator to the mixer, however, the embodiment of the present disclosure is not limited to this. In other exemplary embodiments, the signal transmission delay generated by the transmitting antenna feeder of any transmitting channel can also be defined as the first reference delay τ1, and the signal transmission delay generated by the signal line from the local oscillator to the mixer of the transmitting channel can be defined as the second reference delay τ2.

[0054] Assuming that the additional delay of the signal transmission delay generated by the transmitting antenna feed line of any transmitting channel relative to the first reference delay τ1 is μ1, and the additional delay of the signal transmission delay generated by the signal line from the local oscillator to the mixer of the transmitting channel relative to the second reference delay τ2 is μ2, the FMCW signal passing through the transmitting channel can be expressed as follows:

[0055]

[0056] Among them, t≥τ+μ, μ=μ1+μ2.

[0057] Through direct digital frequency synthesizer, we can generate the corresponding compensation signal To compensate the transmit signal of the transmit channel.

[0058] In some exemplary embodiments, Figure 4A As shown, each transmission channel includes an I transmission channel and a Q transmission channel, the compensation signal includes a cosine compensation signal and a sine compensation signal, the cosine compensation signal and the sine compensation signal have the same frequency, the cosine compensation signal and the sine compensation signal have the same initial phase, one of the cosine compensation signal and the sine compensation signal is used to compensate for the current transmission signal of the I transmission channel, and the other is used to compensate for the current transmission signal of the Q transmission channel.

[0059] like Figure 4A As shown, the transmission channel includes an IQ digital-to-analog converter (i.e., a digital-to-analog converter 1031 and a digital-to-analog converter 1032), an IQ low-pass filter (i.e., a low-pass filter 1041 and a low-pass filter 1042), an IQ mixer (i.e., a mixer 1051 and a mixer 1052), a power amplifier 106, and a transmission antenna 107, and the signal transmission chain includes a local oscillator 108, a waveform generator 101, a direct digital frequency synthesizer 102, an IQ digital-to-analog converter, an IQ low-pass filter, an IQ mixer, a power amplifier 106, and a transmission antenna 107 are connected in sequence, and the local oscillator 108 is respectively connected to the waveform generator 101 and the IQ mixer of each transmission channel. The waveform generator 101 is configured to generate a frequency modulated continuous wave signal; the direct digital frequency synthesizer 102 is configured to perform phase compensation and / or frequency compensation on the transmission signal.

[0060] In some exemplary embodiments, the cosine compensation signal may be The sinusoidal compensation signal can be Where n is the digital signal sampling point, f c is the starting frequency of the initial transmission signal generated by the waveform generator, β is the frequency variation range of the initial transmission signal generated by the waveform generator, T is the scanning duration of a chirp in the initial transmission signal generated by the waveform generator, and μ is the delay difference of the signal transmission delay of the transmission channel relative to the reference transmission delay.

[0061] The signal transmission link of the disclosed embodiment generates a compensation signal according to the delay difference μ of the signal transmission delay of the transmission channel relative to the reference transmission delay, and uses the compensation signal to compensate the transmission signal of the corresponding transmission channel, thereby solving the problem of different relative delays of RF signals passing through different transmission antennas caused by inconsistent transmission antenna feed line lengths and / or inconsistent signal line lengths from the local oscillator to the mixers of multiple transmission channels, thereby improving the quality of the transmission signal, thereby improving the quality of the received signal, and ultimately improving the detection accuracy and detection range of the radar system.

[0062] Since the mixer is a very important and key device for frequency conversion in the transceiver link, it is widely used in radio devices such as communications and radars, such as a single-sideband mixer with good suppression effect on image signals, and an IQ mixer in the transceiver link in the embodiment of the present disclosure. Among them, the IQ mixer (such as a single-sideband mixer) includes two branches, an I branch and a Q branch, with a phase difference of 90° to transmit signals.

[0063] For application scenarios with relatively compact layout areas, such as high-frequency sensor applications in the millimeter wave frequency band, the physical distance between the I branch and the Q branch, and between the input branch and the output branch before mixing are short. As a result, the transmitted signal may be leaked between branches, between input and output ports, between the IQ matching network and the mixer output through methods such as magnetic coupling, substrate coupling, and electrical coupling, thereby causing serious deterioration of the mixer's image suppression ratio and local oscillator leakage.

[0064] Figure 4B This is a simplified schematic diagram of a signal transmission link of a digital phase shifter architecture in an embodiment of the present disclosure. Figure 4C Based on Figure 4B A schematic diagram of a digital phase shifter architecture in a signal transmission link is shown; Figure 4D It is a schematic diagram of a transmission link including a specific compensation module in an embodiment of the present disclosure.

[0065] An embodiment of the present disclosure provides a signal transmission link that can be applied to electromagnetic wave devices. The transmission link may include an analog signal source and a digital phase shifter. The analog signal source may be configured to provide an initial analog signal (such as an LO signal), and the digital phase shifter may be configured to provide a phase-shifted signal generated in a digital domain. The digital phase shifter may also phase-shift the initial analog signal based on the generated phase-shifted signal to perform a preset phase shift operation on the initial analog signal.

[0066] like Figure 4BAs shown, in some optional embodiments, a signal transmission link of a digital phase shifter architecture may include an analog signal source 41, a digital phase shifter (Digital PS) 42 and a transmitting antenna 43, that is, the analog signal source 41 may be configured to provide an LO signal, and the digital phase shifter 42 may be configured to perform a preset phase shift operation on the received LO signal, so that the phase-shifted LO signal is radiated to a preset spatial area through the transmitting antenna 43. The analog signal source 41 may also be an architecture including a phase-locked loop PLL, which may provide an electromagnetic wave (such as a laser, microwave, etc.) signal. The analog signal source 41, the digital phase shifter 42 and the transmitting antenna 43 may be integrated into an integrated device, or may be separate components; for example, the analog signal source 41 and the digital phase shifter 42 may be integrated into a package to form a SoC chip, and the transmitting antenna 43 may be connected through the peripheral port of the chip to form a carrier such as a PCB board. At the same time, in some optional embodiments, the transmitting antenna 43 can also be integrated on the chip package to form AiP or AoP, having a chip structure with a packaged antenna.

[0067] like Figure 4B As shown, the digital phase shifter 42 in the embodiment of the present disclosure may include a mixer (Mixer) 421, a digital-to-analog converter (i.e., DAC) 422 and a phase-shifted signal source (such as a digital baseband signal source Baseband) 423, etc., that is, the phase-shifted signal source 423 may be configured to provide a digital phase-shifted signal; the digital-to-analog converter 422 may be configured to perform analog-to-digital conversion on the received digital phase-shifted signal to convert the digital phase-shifted signal into an analog phase-shifted signal; the mixer 421 may be configured to perform a mixing operation on the received analog phase-shifted signal with the received transmission signal from the analog signal source 41, so as to achieve a phase-shifted operation of setting the above-mentioned transmission signal using the digital phase-shifted signal. Optionally, when the above-mentioned signal transmission link provides a swept frequency signal, such as providing an FMCW laser signal or an FMCW microwave signal, a swept frequency transmission signal can be provided based on the analog signal source 41, and / or a swept frequency digital phase shift signal can be provided based on the phase shift signal source 423, so that after mixing by the mixer 421, a swept frequency continuous wave signal is output.

[0068] In some optional embodiments, based on Figure 4BIn the structure shown, the analog signal source 41 can be configured to provide FMCW signals in the centimeter wave band or millimeter wave band (such as 3.1 GHz, 24 GHz, 60 GHz, 77 GHz, etc.) of microwaves, and the phase-shifted signal source 423 can be configured to provide a digital phase-shifted signal at the MHz level (for example, 3 MHz to 5 MHz, such as 3 MHz, 4 MHz, 5 MHz, etc.), that is, the digital-to-analog converter 422 performs digital-to-analog conversion on the digital phase-shifted signal at the MHz level to obtain an analog phase-shifted signal in the corresponding frequency range, and the mixer 421 can be configured to perform up-mixing or down-mixing operations on the received millimeter wave band FMCW signal based on the received analog phase-shifted signal of the fixed frequency band, so as to realize the operation of preset phase shifting of the FMCW signal.

[0069] In some optional embodiments, the centimeter wave signal in the 3.1 GHz frequency band may include 3.1 GHz to 10.6 GHz, for example, 3.1 GHz, 5 GHz, 5 GHz, 6 GHz, 8 GHz, 10.6 GHz, etc.; the millimeter wave signal in the 77 GHz frequency band may include 76 GHz to 81 GHz signals, for example, swept frequency signals such as 76 GHz to 77 GHz, 77 GHz to 79 GHz, 79 GHz to 81 GHz, or fixed frequency band signals such as 76 GHz, 77 GHz, 78 GHz, 79 GHz, 80 GHz, 81 GHz, etc.

[0070] based on Figure 4B In the structure shown, since the phase-shift signal source 423 provides a digital signal, in order to further adapt the signal characteristics, the mixer 421 can be set as an IQ Mixer, and the digital-to-analog converter 422 is an IQ DAC. At the same time, the phase-shift signal source 423 can be configured to provide a digital baseband signal source (DDFS) for phase shifting and / or provide a corresponding source signal as a waveform controller (WaveformControl).

[0071] For example, Figure 4CAs shown, the signal transmission link (TX digital phase shifter architecture) of the digital phase shifter architecture may include a digital baseband signal source (Baseband), a direct digital frequency synthesizer (Direct Digital Frequency Synthesizer, DDFS for short), an IQ digital to analog converter (Digital to Analog Convertor, DAC for short), a low-pass filter (Low-Pass Filter, LPF for short), an IQ modulator (IQ modulator / IQ Mixer), a power amplifier (Power Amplifier, PA), etc., that is, the baseband signal source is configured to provide a digital phase shift source signal, and the direct digital frequency synthesizer may be configured to implement CDM (Code-Division Multiplexing), DDM (Doppler Division Multiplexing), TDM (Time-Division Multiplexing), SDM (Space Division Multiplexing), CSD (Circuit Switch Data), Digital IF (Digital Intermediate Multiplexing) based on the received source signal. Frequency, digital intermediate frequency) and other signal waveforms and wave transmission methods to achieve flexible configuration of signal transmission form and transmission waveform. Among them, the signal amplified by the power amplifier can be radiated to a preset space area through a transmitting antenna packaged as an integral unit or externally.

[0072] With respect to the signal transmission link of the digital phase shifter architecture in the embodiment of the present disclosure, since the digital phase shifter architecture is configured to generate a baseband signal sequence in the digital domain, and can generate an analog baseband signal through a DAC, and then modulate the transmission signal to a high frequency through an orthogonal mixer, that is, because the baseband signal of the architecture is generated in the digital domain, it has better orthogonality and lower sidelobes, and therefore its phase shift phase can be generated very accurately, resulting in higher phase modulation accuracy.

[0073] In some optional embodiments, for the signal transmission link of the digital phase shifter architecture, when the RF LO frequency sweep is used to realize the transmitted signal as an FMCW signal, a compensation module can be added to the signal transmission link to solve the problems of TX IQ imbalance (Imbalance), signal leakage (such as TX LO Leakage) and harmonic distortion (HD) caused by IQ mismatch (Mismatch). Figure 4CAs shown, a compensation module (TX compensation) can be set between the TX DDFS and the IQ DAC to perform calibration and compensation operations on the signal transmission link of the digital phase shifter architecture to achieve an operation to solve at least one of the above problems. Among them, the HD caused by the third-order nonlinearity of the baseband can be referred to as HD3.

[0074] In some optional embodiments, such as Figures 4C to 4D As shown, the compensation module (TX compensation) may include at least one of an LO compensation unit (TX LO leakage compensation), an IQ compensation unit (TX IQ Imbalance compensation) and an HD3 compensation unit (TX HD3 compensation), that is, the LO compensation unit may be configured to perform compensation operations for signal leakage, the IQ compensation unit may be configured to perform compensation operations for IQ imbalance, and the HD3 compensation unit may be configured to perform compensation operations for the above-mentioned HD3. The LO compensation unit is configured to be used to perform compensation operations for at least one of an IQ modulator imbalance (TX IQ Modulator imbalance) and an IQ channel imbalance (IQchannel imbalance). In addition, when the compensation module includes at least two of the LO compensation unit, the IQ compensation unit and the HD3 compensation unit, compensation may be performed synchronously (such as in parallel) or sequentially (such as in series) according to actual needs and signal characteristics. Figure 4D As shown, IQ compensation may be performed first, then LO compensation, and finally HD3 compensation.

[0075] In some optional embodiments, for the signal transmission link of the digital phase shifter architecture, an error correction module (TX DAC Board Error Correction) for DAC and an AWGN (additive white gaussian noise) module for Gaussian white noise may also be included, which are not shown in the figure and may be added or deleted according to actual needs. Among them, I in IQ mentioned in the embodiments of the present disclosure can be expressed as the abbreviation of In-Phase (i.e., in-phase), Q can be expressed as the abbreviation of Quadrature (i.e., orthogonal), and RF can be expressed as the abbreviation of Radio Frequency (i.e., radio frequency).

[0076] In an optional embodiment, the compensation operation for IQ Imbalance can be achieved by compensating the conjugate signal of the BB (baseband) signal to reversely cancel the image component, and this compensation operation method is not affected by the calibration method of IQ Imbalance. The compensation for LO Leakage can be achieved by adjusting the DC component (i.e., DC bias) of the two IQ paths, and the calibration method of LO Leakage has no effect on its compensation scheme. For HD3, since the third-order harmonic distortion of the orthogonal mixer V / IConverter is the main source of HD3, and the harmonic distortion will be affected by the DC bias, when both the LO Leakage and HD3 of the transmission link need to be calibrated, it is necessary to calibrate HD3 after calibrating LO Leakage to ensure the accurate performance of HD3 calibration.

[0077] In addition, the compensation methods of HD3 based on the digital pre-compensation architecture of the digital cubic module and the digital pre-compensation architecture based on the frequency doubling waveform generator module will directly affect the subsequent calibration scheme and subsequent compensation process. Specifically:

[0078] In an optional embodiment, for a digital pre-compensation architecture based on a digital cubic module, LO Leakage may be calibrated and compensated first, and then the root cause of the HD3 problem, i.e., the compensation coefficient of HD3, may be calibrated under a stable DC bias; then, IQ Imbalance may be calibrated, and after IQ Imbalance is further compensated, the third harmonic distortion may be compensated for the two IQ paths based on the results of IQ Imbalance pre-compensation.

[0079] In an optional embodiment, for a digital pre-compensation architecture based on a frequency doubling waveform generator module, after calibrating and compensating for LO Leakage, the compensation coefficient of HD3 can be calibrated, and IQImbalance can be calibrated and IQ Imbalance can be compensated under a stable DC bias; subsequently, the actual waveforms of the IQ and Q signals and the compensation coefficient of HD3 are calculated respectively through the compensation results, and the waveform information of 3x and 5x that need to be pre-compensated is calculated in reverse.

[0080] In another optional embodiment, for the digital pre-compensation architecture based on the frequency-multiplier waveform generator module, LO Leakage can be calibrated and compensated first, and then the pre-compensation coefficients of HD3 and IQ Imbalance can be calibrated simultaneously through multiple (such as three) observations, and then the pre-compensation coefficients at the HD3 mirror position can be calibrated again through observations (such as two times); finally, the 3-fold and 5-fold frequency coefficients that need to be pre-compensated are calculated back through the pre-compensation coefficients at the HD3 and HD3 mirror positions. It should be noted that the observations in the embodiments of the present disclosure are used to represent operations such as testing and comparison and analysis of different test results.

[0081] Figure 4E It is a schematic diagram of using an auxiliary receiving circuit to calibrate and compensate a transmission link in an embodiment of the present disclosure.

[0082] like Figure 4E As shown, the transmitting path (Transmitter) may include a phase shift module PS, an amplifier PA, a power detector PD, etc. For example, the transmitting path may adopt the transmitting link of the digital phase shifter architecture (Digital Phase Shifter) described in any embodiment of the present disclosure. For details, please refer to the relevant figures and text descriptions, which will not be repeated here. Since the transmitting path adopts a digital phase shifter architecture, while achieving more accurate phase shifting operations, the transmitting channel can simultaneously support multiple modes such as DDM and FDM (Frequency Division Multiplexing) of multiple antennas, and can also save the calibration operation of the RF phase shifter (Phase Shifter), reduce the isolation and coupling degree in the phase shifting system, and reduce the link loss and production cost. In addition, in response to the possible problems of TX IQ mismatch (Mismatch) and LO leakage (leakage), the transmitting path of the digital phase shifter architecture can also support RF frequency response (Frequency Response) compensation, IQ imbalance and LO leakage calibration operations in the digital domain.

[0083] For problems such as TX IQ mismatch, LO leakage, and frequency response in the transmission path, the auxiliary receiver (ARX) can be set up to perform relevant calibration and compensation operations. Figure 4EAs shown, the ARX may include a mixer, TIA, LPF, HPF, IQ ADC, adder and RF calibration module (RF Calib) connected in sequence, that is, by receiving the ARX IQ LO signal at one input end of the mixer, the other input end is connected to the node before the transmission path PD along the signal transmission direction (i.e. the direction of the arrow shown in the figure), or any node after the phase shifter (module). For example, it is connected to the output end of the PA (synchronously realizing the calibration of the PA), the input end of the PA, etc., so as to perform a calibration operation on the transmission path through the ARX. There is a set difference frequency between the LO signal frequency in the transmission path and the ARX IQ LO signal frequency, so that there is a frequency error between the two signals to simulate a real transceiver signal loop.

[0084] In an optional embodiment, in order to further improve the calibration accuracy, a corresponding calibration circuit (ie, calibration receiving unit) may be provided for the ARX (ie, auxiliary receiving unit), for example Figure 4E The RF single tone signal generating circuit (RF ToneGenerator) shown in the figure may include a TX DDFS, an adder, a Real DAC, an LPF, an amplifier, a multiplier and a band pass filter (BPF) connected in sequence, wherein the adder may be configured to calibrate and compensate for the TX LO leakage (TX LO leakage Waveform), the multiplier may be configured to compensate for the RF Tone Gen LO leakage (leakage), and the BPF may be configured to filter out the DC signal generated by the LO leakage of the RF Tone Generator. That is, the RF Tone Generator may be configured to generate a plurality of stable single tone signals of different frequencies to implement the calibration operation of the ARX.

[0085] In some optional embodiments, such as Figure 4E As shown, the ARX can be calibrated using the RF Tone Generator first, and then the calibrated ARX can be used to calibrate the transmitting channel (Transmitter) including PA, for example, the PD at the PA output, the phase shifter in the transmitting channel, the total gain from DAC to PA output, and the frequency response and other devices and circuits.

[0086] Specifically, Figure 4E As shown, the RF Tone Generator can be used to generate multiple stable single-tone signals with different frequencies to assist in calibrating the ARX, and then the calibrated ARX can be used to assist in calibrating the IQ imbalance, local oscillator leakage, frequency response inconsistency and other issues of the transmission path TX.

[0087] like Figure 5 As shown, the embodiment of the present disclosure further provides a signal transmission method, which is applied to an antenna array of an electromagnetic wave device having at least two signal transmission links, wherein the signal transmission link is a phase shifter including a digital phase shift architecture, and the signal transmission method includes:

[0088] Step 501: Determine a reference transmission delay and a delay difference of a signal transmission delay of each transmission channel relative to the reference transmission delay;

[0089] In some exemplary embodiments, the reference transmit delay includes a first reference transmit delay and / or a second reference transmit delay, wherein the first reference transmit delay may be a signal transmit delay of a transmit antenna feeder of any transmit channel, and the second reference transmit delay may be a signal transmit delay of a signal line from a local oscillator to a mixer of any transmit channel.

[0090] In other exemplary embodiments, the reference transmit delay includes a first reference transmit delay and / or a second reference transmit delay, wherein the first reference transmit delay may be a signal transmit delay of the shortest transmit antenna feed line in a plurality of transmit channels, and the second reference transmit delay may be a signal transmit delay of the shortest signal line from a local oscillator to mixers in a plurality of transmit channels.

[0091] In the embodiments of the present disclosure, the distance between the transmitting antenna feed line and / or the signal line from the local oscillator to the mixer in each transmitting channel may be measured, and the distance measurement may include model simulation measurement or actual measurement.

[0092] Step 502: Generate a compensation signal corresponding to each transmission channel according to the delay difference;

[0093] In the embodiment of the present disclosure, the frequency control parameter of the compensation signal Phase control parameters Among them, f c is the starting frequency of the initial transmission signal generated by the waveform generator, β is the frequency variation range of the initial transmission signal generated by the waveform generator, T is the scanning duration of a chirp in the initial transmission signal generated by the waveform generator, and μ is the delay difference of the signal transmission delay of the transmission channel relative to the reference transmission delay.

[0094] Step 504: Use the compensation signal to compensate the transmission signal of the corresponding transmission channel.

[0095] In the embodiment of the present disclosure, the transmitting channel includes an I transmitting channel and a Q transmitting channel, and the compensation signal includes a cosine compensation signal and sinusoidal compensation signal One of the cosine compensation signal and the sine compensation signal is used to compensate the transmission signal of the I transmission channel, and the other is used to compensate the transmission signal of the Q transmission channel.

[0096] The signal transmission method of the embodiment of the present disclosure generates a compensation signal according to the delay difference of the signal transmission delay of each transmission channel relative to the reference transmission delay, and uses the compensation signal to compensate the transmission signal of the corresponding transmission channel, thereby solving the problem of different relative delays of the RF signal passing through different transmission antennas due to inconsistent transmission antenna feed line lengths and / or inconsistent signal line lengths from the local oscillator to the mixers of multiple transmission channels, thereby improving the quality of the transmission signal, thereby improving the quality of the received signal, and ultimately improving the detection accuracy and detection range of the radar system.

[0097] The present disclosure also provides an integrated circuit, which may include any of the above signal transceiver links. Optionally, the integrated circuit may also include a data processing module, which is used to process digital signals to achieve target detection and / or wireless communication. For example, the integrated circuit may be a millimeter wave radar chip (chip or die).

[0098] In some optional embodiments, the integrated circuit may be an AiP (Antenna-In-Package) chip structure, an AoP (Antenna-On-Package) chip structure, or an AoC (Antenna-On-Chip) chip structure.

[0099] According to other embodiments of the present disclosure, an electromagnetic wave device is also proposed. The electromagnetic wave device may include an antenna, and an integrated circuit as described above. The integrated circuit is electrically connected to the antenna for receiving and sending signals. For example, the electromagnetic wave device may include: a carrier, an integrated circuit and an antenna as described in any of the above embodiments, and the integrated circuit may be arranged on the carrier; the antenna may be arranged on the carrier, or the integrated device may be integrated with the integrated circuit and arranged on the carrier (that is, the antenna may be an antenna provided in an AiP, AoP or AoC structure at this time); the integrated circuit is connected to the antenna (that is, the sensor chip or the integrated circuit is not integrated with an antenna at this time, such as a conventional SoC, etc.), for receiving and sending signals. The carrier may be a printed circuit board PCB, and the first transmission line may be a PCB trace.

[0100] An embodiment of the present disclosure provides a device, which may include: a device body; and an electromagnetic wave device as described above, which is arranged on the device body; wherein the electromagnetic wave device is used for target detection and / or communication to provide reference information for the operation of the device body.

[0101] The present disclosure also provides an electronic device, which can be expressed in the form of a general-purpose computing device. The components of the electronic device may include, but are not limited to: at least one processing unit, at least one storage unit, a bus connecting different system components (including a storage unit and a processing unit), a display unit, etc. Among them, the storage unit stores a program code, and the program code can be executed by the processing unit so that the processing unit executes the method described in this specification according to various exemplary embodiments of the present disclosure. The storage unit may include a readable medium in the form of a volatile storage unit, such as a random access memory unit (RAM) and / or a cache memory unit, and may further include a read-only memory unit (ROM).

[0102] The storage unit may also include a program / utility having a set (at least one) of program modules, such program modules including but not limited to: an operating system, one or more application programs, other program modules, and program data, each of which or some combination may include an implementation of a network environment.

[0103] The bus may represent one or more of several types of bus structures, including a memory unit bus or memory unit controller, a peripheral bus, an accelerated graphics port, a processing unit, or a local bus using any of a variety of bus architectures.

[0104] The electronic device may also communicate with one or more external devices (e.g., keyboards, pointing devices, Bluetooth devices, etc.), may communicate with one or more devices that enable a user to interact with the electronic device, and / or may communicate with any device that enables the electronic device to communicate with one or more other computing devices (e.g., routers, modems, etc.). This communication may be performed through an input / output (I / O) interface. In addition, the electronic device may also communicate with one or more networks (e.g., local area networks (LANs), wide area networks (WANs), and / or public networks, such as the Internet) through a network adapter. The network adapter may communicate with other modules of the electronic device through a bus. It should be understood that, although not shown in the figure, other hardware and / or software modules may be used in conjunction with the electronic device, including but not limited to: microcode, device drivers, redundant processing units, external disk drive arrays, RAID systems, tape drives, and data backup storage systems, etc.

[0105] For example, the electronic device in the embodiment of the present disclosure may also include: a device body; and an electromagnetic wave device as described in any of the above embodiments arranged on the device body; wherein the electromagnetic wave device can be used to realize functions such as target detection and / or wireless communication.

[0106] Specifically, based on the above embodiments, in an optional embodiment of the present disclosure, the electromagnetic wave device can be arranged outside the device body, or arranged inside the device body, and in other optional embodiments of the present disclosure, the electromagnetic wave device can also be arranged partially inside the device body and partially outside the device body. The embodiments of the present disclosure are not limited to this, and the specific situation may be determined.

[0107] In an optional embodiment, the device body can be a component or product used in fields such as smart cities, smart homes, transportation, smart homes, consumer electronics, security monitoring, industrial automation, in-cabin detection (such as smart cockpits), medical devices, and health care. For example, the device body can be intelligent transportation equipment (such as cars, bicycles, motorcycles, ships, subways, trains, etc.), security equipment (such as cameras), liquid level / flow rate detection equipment, smart wearable devices (such as bracelets, glasses, etc.), smart home devices (such as sweeping robots, door locks, televisions, air conditioners, smart lights, etc.), various communication devices (such as mobile phones, tablet computers, etc.), and gates, smart traffic lights, smart signs, traffic cameras, and various industrialized robotic arms (or robots), etc. It can also be various instruments for detecting life characteristic parameters and various devices equipped with the instruments, such as life characteristic detection in car cabins, indoor personnel monitoring, smart medical equipment, consumer electronic equipment, etc.

[0108] The embodiment of the present disclosure also provides a non-transitory computer-readable storage medium having computer-readable instructions stored thereon. When the instructions are executed by a processor, the processor executes the feeder unequal length compensation method as described above.

[0109] Through the description of the above implementation methods, it is easy for those skilled in the art to understand that the example implementation methods described here can be implemented by software, or by combining software with necessary hardware. The technical solution according to the implementation methods of the present disclosure can be embodied in the form of a software product, which can be stored in a non-volatile storage medium (which can be a CD-ROM, a USB flash drive, a mobile hard disk, etc.) or on a network, including several instructions to enable a computing device (which can be a personal computer, a server, or a network device, etc.) to execute the above method according to the implementation methods of the present disclosure.

[0110] The software product may use any combination of one or more readable media. The readable medium may be a readable signal medium or a readable storage medium. The readable storage medium may be, for example, but not limited to, a system, device or device of electricity, magnetism, light, electromagnetic, infrared, or semiconductor, or any combination thereof. More specific examples (non-exhaustive list) of readable storage media include: an electrical connection with one or more wires, a portable disk, a hard disk, a random access memory (RAM), a read-only memory (ROM), an erasable programmable read-only memory (EPROM or flash memory), an optical fiber, a portable compact disk read-only memory (CD-ROM), an optical storage device, a magnetic storage device, or any suitable combination thereof.

[0111] Computer readable storage media may include data signals propagated in baseband or as part of a carrier wave, wherein readable program codes are carried. Such propagated data signals may take various forms, including but not limited to electromagnetic signals, optical signals, or any suitable combination thereof. The readable storage medium may also be any readable medium other than a readable storage medium, which may send, propagate, or transmit a program for use by or in conjunction with an instruction execution system, device, or device. The program codes contained on the readable storage medium may be transmitted using any suitable medium, including but not limited to wireless, wired, optical cable, RF, etc., or any suitable combination thereof.

[0112] Program code for performing the operations of the present disclosure may be written in any combination of one or more programming languages, including object-oriented programming languages ​​such as Java, C++, etc., and conventional procedural programming languages ​​such as "C" or similar programming languages. The program code may be executed entirely on the user computing device, partially on the user device, as a separate software package, partially on the user computing device and partially on a remote computing device, or entirely on a remote computing device or server. In cases involving a remote computing device, the remote computing device may be connected to the user computing device through any type of network, including a local area network (LAN) or a wide area network (WAN), or may be connected to an external computing device (e.g., through the Internet using an Internet service provider).

[0113] The computer-readable medium carries one or more programs. When the one or more programs are executed by a device, the computer-readable medium implements the aforementioned functions.

[0114] Those skilled in the art will appreciate that the above modules can be distributed in the device according to the description of the embodiment, or can be changed accordingly and only used in one or more devices different from the embodiment. The modules of the above embodiments can be combined into one module, or further divided into multiple sub-modules.

[0115] According to an embodiment of the present disclosure, a computer program is proposed, including a computer program or an instruction, which, when executed by a processor, can execute the method described above. In an optional embodiment, the above-mentioned integrated circuit can be a millimeter wave radar chip. The type of digital function module in the integrated circuit can be determined according to actual needs. For example, in a millimeter wave radar chip, a data processing module can be used for functions such as distance-dimensional Doppler transform, velocity-dimensional Doppler transform, constant false alarm detection, direction of arrival detection, point cloud processing, etc., to obtain information such as the distance, horizontal angle, pitch angle, speed, height, micro-Doppler motion characteristics, shape, size, surface roughness and dielectric properties of the target.

[0116] It should be noted that radio devices can achieve functions such as target detection and / or communication by transmitting and receiving radio signals to provide the device body with detection target information and / or communication information, thereby assisting or even controlling the operation of the device body.

[0117] For example, when the above-mentioned device body is applied to an advanced driver assistance system (i.e., ADAS), the radio device (such as millimeter-wave radar) as a vehicle-mounted sensor can assist the ADAS system to realize application scenarios such as adaptive cruise control, automatic braking assistance (i.e., AEB), blind spot detection warning (i.e., BSD), assisted lane change warning (i.e., LCA), reversing assistance warning (i.e., RCTA), parking assistance, rear vehicle warning, collision avoidance, pedestrian detection, etc.

[0118] The technical features of the above-described embodiments may be arbitrarily combined. To make the description concise, not all possible combinations of the technical features in the above-described embodiments are described. However, as long as there is no contradiction in the combination of these technical features, they should be considered to be within the scope of this specification.

[0119] The above-described embodiments only express the preferred embodiments of the present disclosure and the technical principles used. The description is relatively specific and detailed, but it cannot be understood as limiting the scope of the invention patent. It is possible for those skilled in the art to make various obvious changes, readjustments and substitutions without departing from the protection scope of the present disclosure. Therefore, although the present disclosure is described in more detail through the above embodiments, the present disclosure is not limited to the above embodiments, and may also include more other equivalent embodiments without departing from the concept of the present disclosure, and the protection scope of the patent of the present disclosure is determined by the scope of the attached claims.

Claims

1. A signal transmission link, characterized in that: include: A waveform generator and a plurality of transmission channels connected to the waveform generator, at least two of the transmission channels having different signal transmission delays, and at least one of the transmission channels comprising a direct digital frequency synthesizer; The direct digital frequency synthesizer is configured to generate a compensation signal according to a delay difference of a signal transmission delay of the corresponding transmission channel relative to a reference transmission delay, and use the compensation signal to compensate for a transmission signal of the corresponding transmission channel.

2. The signal transmission link according to claim 1, characterized in that: The delay difference of the signal transmission delay of the transmitting channel relative to the reference transmission delay includes the delay difference of the signal transmission delay of the transmitting antenna feeder of the transmitting channel relative to the first reference transmission delay, and / or the delay difference of the signal transmission delay from the local oscillator to the mixer of the transmitting channel relative to the second reference transmission delay.

3. The signal transmission link according to claim 2, characterized in that: When the delay difference of the signal transmission delay of the transmission channel relative to the reference transmission delay includes the delay difference of the signal transmission delay of the transmission antenna feeder of the transmission channel relative to the first reference transmission delay, the first reference transmission delay is the signal transmission delay of the transmission antenna feeder of any one of the transmission channels; as well as, When the delay difference of the signal transmission delay of the transmitting channel relative to the reference transmission delay includes the delay difference of the signal transmission delay from the local oscillator to the mixer of the transmitting channel relative to the second reference transmission delay, the second reference transmission delay is the signal transmission delay of the signal line from the local oscillator to any one of the mixers of the transmitting channel.

4. The signal transmission link according to claim 2, characterized in that: When the delay difference of the signal transmission delay of the transmission channel relative to the reference transmission delay includes the delay difference of the signal transmission delay of the transmission antenna feeder of the transmission channel relative to the first reference transmission delay, the first reference transmission delay is the signal transmission delay of the shortest transmission antenna feeder among the multiple transmission channels; as well as, When the delay difference of the signal transmission delay of the transmitting channel relative to the reference transmission delay includes the delay difference of the signal transmission delay from the local oscillator to the mixer of the transmitting channel relative to the second reference transmission delay, the second reference transmission delay is the signal transmission delay of the shortest signal line from the local oscillator to the mixers in the multiple transmitting channels.

5. The signal transmission link according to claim 1, characterized in that: The transmission channel includes an IQ digital-to-analog converter, an IQ low-pass filter, an IQ mixer, a power amplifier and a transmission antenna, the signal transmission link includes a local oscillator, the waveform generator, the direct digital frequency synthesizer, the IQ digital-to-analog converter, the IQ low-pass filter, the IQ mixer, the power amplifier and the transmission antenna are connected in sequence, and the local oscillator is respectively connected to the waveform generator and the IQ mixer of each of the transmission channels, wherein: The waveform generator is configured to generate a frequency modulated continuous wave signal; The direct digital frequency synthesizer is configured to perform phase compensation and / or frequency compensation on the transmit signal.

6. The signal transmission link according to claim 1, characterized in that: The transmission channel includes an I transmission channel and a Q transmission channel, the compensation signal includes a cosine compensation signal and a sine compensation signal, the cosine compensation signal and the sine compensation signal have the same frequency, the cosine compensation signal and the sine compensation signal have the same initial phase, one of the cosine compensation signal and the sine compensation signal is used to compensate for the current transmission signal of the I transmission channel, and the other is used to compensate for the current transmission signal of the Q transmission channel.

7. The signal transmission link according to claim 6, characterized in that: The cosine compensation signal is The sinusoidal compensation signal is Where n is the digital signal sampling point, f c is the starting frequency of the signal generated by the waveform generator, β is the frequency variation range of the signal generated by the waveform generator, T is the scanning duration of a chirp in the signal generated by the waveform generator, and μ is the delay difference of the signal transmission delay of the transmission channel relative to the reference transmission delay.

8. The signal transmission link according to claim 1, characterized in that: Each of the transmitting channels is provided with a direct digital frequency synthesizer; and, Each of the direct digital frequency synthesizers is configured to generate a compensation signal according to the delay difference of the signal transmission delay of the transmission channel in which it is located relative to the reference transmission delay, and use the compensation signal to compensate the transmission signal of the transmission channel in which it is located.

9. The signal transmission link according to claim 1, characterized in that: The signal transmission link further includes a compensation module, which can be configured to compensate for at least one of IQ mismatch, IQ imbalance, signal leakage, and harmonic distortion defects of the signal transmission link.

10. An integrated circuit, characterized in that: Comprising the signal transmission link as claimed in any one of claims 1 to 9.

11. The integrated circuit according to claim 10, characterized in that It also includes a data processing module, which is used to process the compensated signal to achieve target detection and / or wireless communication.

12. The integrated circuit according to claim 10, characterized in that The integrated circuit is a millimeter wave chip.

13. The integrated circuit according to claim 10, characterized in that The currently received signal is an echo signal formed by the radio frequency transmission signal being transmitted and / or scattered by the target, and the integrated circuit is a sensor chip.

14. An electromagnetic wave device, characterized in that: include: Carrier; An integrated circuit as claimed in any one of claims 10 to 13, arranged on a carrier; An antenna is arranged on the carrier, or the antenna and the integrated circuit are integrated into a single device and arranged on the carrier; the antenna includes a transmitting antenna and a receiving antenna; Wherein, the integrated circuit is connected to the antenna and is used for transmitting electromagnetic wave signals and / or receiving electromagnetic wave signals.

15. A device, characterized in that include: Equipment body; as well as The electromagnetic wave device as claimed in claim 14 is disposed on the device body; Wherein, the electromagnetic wave device is used for target detection and / or communication to provide reference information for the operation of the device body.

16. A signal transmission method, characterized in that: Applied to an antenna array of an electromagnetic wave device having at least two signal transmission links, the signal transmission link being a phase shifter including a digital phase shift architecture, the signal transmission method comprising: Determine a reference transmission delay and a delay difference of a signal transmission delay of each of the transmission channels relative to the reference transmission delay; Generate a compensation signal corresponding to each of the transmitting channels according to the time delay difference; The compensation signal is used to compensate the transmission signal of the corresponding transmission channel. 17 . A non-transitory computer-readable storage medium having computer-readable instructions stored thereon, which, when executed by a processor, causes the processor to execute the signal transmission method according to claim 16 .

Images