Dual-band amplitude-phase consistent frequency conversion assembly

Abstract

The invention relates to the technical field of frequency conversion components, in particular to a dual-band amplitude-phase consistent frequency conversion component which comprises a first amplitude limiter, a first switch and a first frequency mixer, the first amplitude limiter is connected with the first switch, the first switch is connected with the first frequency mixer through a switch filter bank, and the first frequency mixer is connected with a fifth switch; the switch filter bank comprises a second switch and a third switch, the second switch is connected with a first band-pass filter, a third band-pass filter and a fifth band-pass filter, the first band-pass filter is connected with the third switch through a first amplifier and a second band-pass filter, and the third band-pass filter is connected with the third switch through a second amplifier and a fourth band-pass filter. The fifth band-pass filter is connected with a third switch through a third amplifier and a sixth band-pass filter; the four-way frequency conversion part is powered on and powered off through the power switch, the frequency conversion part which does not need to be used can be independently powered off through external control according to the actual use condition, and unnecessary power consumption is avoided.

Description

Technical Field

[0001] The invention belongs to the technical field of frequency conversion components, and in particular relates to a dual-band amplitude-consistent frequency conversion component. Background Art

[0002] Dual-band amplitude-phase-coherent frequency conversion components are usually used to process signals in two different frequency bands and ensure that the amplitude and phase of the signals remain consistent during the frequency conversion process. Such components are particularly important in wireless communication systems, such as phased array radar, satellite communications, and radio testing. In these applications, the amplitude and phase accuracy of the signal is critical to the overall performance of the system. However, there are some problems with the existing technology:

[0003] Power loss: During the frequency conversion process, a certain amount of power loss will occur due to the impedance of electronic components and parts. This loss will reduce the working efficiency of the frequency conversion component, especially in high-power application scenarios.

[0004] Electromagnetic interference: The frequency conversion components will generate high-frequency electromagnetic waves when working, which may cause electromagnetic interference problems. In some occasions that require high sensitivity, such as medical equipment, aerospace equipment, etc., electromagnetic interference may seriously affect the performance of the system.

[0005] High cost: Since dual-band phase-coherent frequency conversion components require high-performance electronic components and complex circuit structures, their manufacturing costs are relatively high, which limits the promotion of this technology in some low-cost applications. Summary of the invention

[0006] The purpose of this section is to summarize some aspects of embodiments of the present invention and briefly introduce some preferred embodiments. Some simplifications or omissions may be made in this section and the specification abstract and the invention title of this application to avoid blurring the purpose of this section, the specification abstract and the invention title, and such simplifications or omissions cannot be used to limit the scope of the present invention.

[0007] In view of the following technical problems existing in the prior art: the prior art suffers from excessive loss.

[0008] In order to solve the above technical problems, the present invention provides the following technical solutions: a dual-band amplitude-consistent frequency conversion component, comprising:

[0009] A limiter 1, a switch 1, and a mixer 1, wherein the limiter 1 is connected to the switch 1, the switch 1 and the mixer 1 are connected via a switch filter group, and the mixer 1 is connected to the switch 5;

[0010] The switch filter group includes switch 2 and switch 3, wherein switch 2 is connected to bandpass filter 1, bandpass filter 3, and bandpass filter 5, bandpass filter 1 is connected to switch 3 through amplifier 1 and bandpass filter 2, bandpass filter 3 is connected to switch 3 through amplifier 2 and bandpass filter 4, and bandpass filter 5 is connected to switch 3 through amplifier 3 and bandpass filter 6;

[0011] It also includes a limiter 2, which is connected to a switch 5 via a switch 4, a bandpass filter 7, and an amplifier 4 in sequence.

[0012] As a preferred technical solution for a dual-band amplitude-consistent frequency conversion component, the switch five is connected to the mixer two in sequence through the bandpass filter eight, the digitally controlled attenuator, and the amplifier five, and the mixer two is output through the bandpass filter nine.

[0013] As an optimal technical solution for a dual-band amplitude-consistent frequency conversion component, it also includes a frequency source generator, which includes a 100MHz crystal oscillator. The 100MHz crystal oscillator generates a first self-calibration frequency source, a second self-calibration frequency source, a local oscillator frequency source 1 and a local oscillator frequency source 2 through a four-power divider.

[0014] As a preferred technical solution for a dual-band amplitude-consistent frequency conversion component, the first self-calibration frequency source generates a frequency of 2 to 18 GHz, the second self-calibration frequency source generates a frequency of 32 to 38 GHz, the local oscillator one frequency source generates a frequency of 20 GHz, 25 GHz, and 30 GHz, and the local oscillator two frequency source generates a frequency of 30 GHz.

[0015] As a preferred technical solution for a dual-band amplitude-consistent frequency conversion component, the first self-calibration frequency source is connected to the input of switch one, and the second self-calibration frequency source is connected to the input of switch four.

[0016] As a preferred technical solution for a dual-band amplitude-consistent frequency conversion component, the local oscillator 1 frequency source is connected to the input of the mixer 1, and the local oscillator 2 frequency source is connected to the input of the mixer 2 via a digitally controlled phase shifter.

[0017] As a preferred technical solution for a dual-band amplitude-consistent frequency conversion component, the input frequency of the limiter 1 is 2 to 18 GHz, and the input frequency of the limiter 2 is 32 to 38 GHz.

[0018] As a preferred technical solution for a dual-band amplitude-consistent frequency conversion component, the amplifiers 1 to 4 are all controlled by a power switch.

[0019] Beneficial effects of the present invention: The four-way frequency conversion part of the present invention is powered on and off through a power switch, and the frequency conversion part that is not needed can be independently powered off according to actual usage through external control to avoid unnecessary power consumption. BRIEF DESCRIPTION OF THE DRAWINGS

[0020] In order to more clearly illustrate the technical solutions of the embodiments of the present invention, the following briefly introduces the drawings required for describing the embodiments. Obviously, the drawings described below are only some embodiments of the present invention. For ordinary technicians in this field, other drawings can be obtained based on these drawings without creative labor. Among them:

[0021] Figure 1 This is a schematic diagram of the design of the first frequency conversion part in the present invention;

[0022] Figure 2 It is a schematic diagram of the design of the self-calibration source and the local oscillator part in the present invention;

[0023] Figure 3 This is a schematic diagram of the power supply design in the present invention;

[0024] Figure 4 The present invention provides a block diagram of the power-on design of amplifiers 1 to 4 of the four-way frequency conversion part.

[0025] Figure numerals: switch filter group 100, switch three K3, switch two K2, band pass filter one D1, band pass filter two D2, band pass filter three D3, amplifier two F2, band pass filter four D4, band pass filter five D5, amplifier three F3, band pass filter six D6, band pass filter seven D7, amplifier four F4, switch five K5, band pass filter eight D8, digitally controlled attenuator S1, amplifier five F5, band pass filter nine D9, frequency source generating element 200, 100MHz crystal oscillator 201, four power divider 202, first self-calibration frequency source 203, switch one K1, second self-calibration frequency source 204, switch four K4, local oscillator one frequency source 205, mixer one H1, local oscillator two frequency source 206, digitally controlled phase shifter S2, mixer two H2, limiter one X1, limiter two X2, amplifier one F1. DETAILED DESCRIPTION

[0026] In order to make the above-mentioned objects, features and advantages of the present invention more obvious and easy to understand, the specific implementation methods of the present invention are described in detail below in conjunction with the accompanying drawings.

[0027] In the following description, many specific details are set forth to facilitate a full understanding of the present invention, but the present invention may also be implemented in other ways different from those described herein, and those skilled in the art may make similar generalizations without violating the connotation of the present invention. Therefore, the present invention is not limited to the specific embodiments disclosed below.

[0028] Secondly, the term "one embodiment" or "embodiment" as used herein refers to a specific feature, structure, or characteristic that may be included in at least one implementation of the present invention. The term "in one embodiment" that appears in different places in this specification does not necessarily refer to the same embodiment, nor does it refer to a separate or selective embodiment that is mutually exclusive with other embodiments.

[0029] Secondly, the present invention is described in detail with reference to the schematic diagram. When describing the embodiments of the present invention in detail, for the sake of convenience, the cross-sectional diagrams showing the device structure will not be partially enlarged according to the general scale, and the schematic diagrams are only examples, which should not limit the scope of protection of the present invention. In addition, in actual production, the three-dimensional dimensions of length, width and depth should be included.

[0030] Example 1

[0031] Reference Figure 1 to Figure 4 This embodiment provides a dual-band amplitude-phase consistent frequency conversion component which mainly includes a four-way frequency conversion part, a self-calibration source and a local oscillator part, and is mainly composed of a limiter, a digitally controlled attenuator, a switch, a filter group, an amplifier, a mixer, a digitally controlled phase shifter, a crystal oscillator and other devices.

[0032] The four frequency conversion parts are represented by the first frequency conversion part, the second frequency conversion part, the third frequency conversion part, and the fourth frequency conversion part respectively. The structures of the four frequency conversion parts are exactly the same. Figure 1 As shown, including:

[0033] A limiter X1, a switch K1, and a mixer H1, wherein the limiter X1 is connected to the switch K1, the switch K1 and the mixer H1 are connected through a switch filter bank 100, and the mixer H1 is connected to the switch K5;

[0034] The switch filter group 100 includes a switch 2 K2 and a switch 3 K3, wherein the switch 2 K2 is connected to a bandpass filter 1 D1, a bandpass filter 3 D3, and a bandpass filter 5 D5, wherein the bandpass filter 1 D1 is connected to the switch 3 K3 via an amplifier 1 F1 and a bandpass filter 2 D2, wherein the bandpass filter 3 D3 is connected to the switch 3 K3 via an amplifier 2 F2 and a bandpass filter 4 D4, and wherein the bandpass filter 5 D5 is connected to the switch 3 K3 via an amplifier 3 F3 and a bandpass filter 6 D6;

[0035] It also includes a limiter 2 X2, which is connected to a switch 5 K5 in sequence through a switch 4 K4, a bandpass filter 7 D7, and an amplifier 4 F4.

[0036] The switch five K5 is connected to the mixer two H2 through the band pass filter eight D8, the digital controlled attenuator S1, and the amplifier five F5 in sequence, and the mixer two H2 is output through the band pass filter nine D9.

[0037] It also includes a frequency source generating element 200 , which includes a 100 MHz crystal oscillator 201 . The 100 MHz crystal oscillator 201 generates a first self-calibration frequency source 203 , a second self-calibration frequency source 204 , a local oscillator first frequency source 205 and a local oscillator second frequency source 206 through a four-power divider 202 .

[0038] The first self-calibration frequency source 203 generates a frequency of 2 to 18 GHz, the second self-calibration frequency source 204 generates a frequency of 32 to 38 GHz, the local oscillator frequency source 1 205 generates frequencies of 20 GHz, 25 GHz, and 30 GHz, and the local oscillator frequency source 206 generates a frequency of 30 GHz.

[0039] The first self-calibration frequency source 203 is connected to the input of the switch K1, and the second self-calibration frequency source 204 is connected to the input of the switch K4.

[0040] The first local oscillator frequency source 205 is connected to the input of the first mixer H1, and the second local oscillator frequency source 206 is connected to the input of the second mixer H2 through the digitally controlled phase shifter S2.

[0041] The input frequency of the limiter X1 is 2 to 18 GHz, and the input frequency of the limiter X2 is 32 to 38 GHz.

[0042] Amplifier 1 F1 to amplifier 4 F4 are all controlled by a power switch.

[0043] The main function of each frequency conversion part is to convert 2~18GHz and 32~38GHz input signals to 2~8GHz output. And make the consistency of the amplitude and phase of the four output signals within a certain range. The self-calibration source and local oscillator part mainly provide self-calibration signals and local oscillator signals for each frequency conversion part.

[0044] Frequency conversion part: Limiter X1 limits the input 2~18GHz signal to prevent the input signal power from being too high and burning subsequent devices. Switch K1 selects external 2~18GHz signal input or self-calibration 2~18GHz signal input by switching. Switch K2, switch K3, bandpass filter D1~bandpass filter D6, amplifier F1~amplifier F3 form a switch filter group 100, which divides the input signal into three frequency bands of 2~8GHz, 7~13GHz, and 12~18GHz, and suppresses out-of-band signals. The three amplifiers amplify the signals of the three frequency bands respectively. Mixer H1 mixes the three input frequency bands of 2~8GHz, 7~13GHz, and 12~18GHz with the three point frequencies of 20GHz, 25GHz, and 30GHz of the local oscillator frequency source, and converts all three input frequency bands to 32~38GHz.

[0045] Limiter 2 X2 limits the input 32~38GHz signal to prevent the input signal power from being too large and burning subsequent devices. Switch 4 K4 switches to select external 32~38GHz signal input or 32~38GHz self-calibration frequency source signal input. Bandpass filter 7 D7 suppresses the out-of-band signal of 32~38GHz. Amplifier 4 F4 amplifies the input 32~38GHz signal. Switch 5 K5 switches to select 2~18GHz frequency conversion 32~38GHz or external input 32~38GHz. Bandpass filter 8 D8 amplifies the out-of-band signal of 32~38GHz. The digitally controlled attenuator S1 attenuates the external 2-18 GHz and 32-38 GHz input signals when their power is too large, so that the amplifier F5 always remains in a linear state. The amplifier F5 amplifies the input 32-38 GHz signal. The mixer H2 mixes the input 32-38 GHz and the local oscillator frequency source 30 GHz. The digitally controlled phase shifter S2 is used to adjust the phase of the component output signal. The bandpass filter D9 suppresses the 2-8 GHz out-of-band signal. Finally, the component converts all the input 2-18 GHz and 32-38 GHz signals to 2-8 GHz output.

[0046] Self-calibration source and local oscillator part: 100MHz crystal oscillator 201 generates 100MHz output, four-power divider 202 divides 100MHz into four outputs to each frequency source, the first self-calibration frequency source 203 is a 2-18GHz self-calibration frequency source, the first self-calibration frequency source 203 is a 32-38GHz self-calibration frequency source, and outputs 2-18GHz and 32-38GHz signals to the frequency conversion part for self-calibration, local oscillator frequency source 1 205 outputs three point frequencies of 20GHz, 25GHz, and 30GHz to mixer 1 H1 for use as a local oscillator, and local oscillator frequency source 206 outputs 30GHz point frequency to mixer 2 H2 for use as a local oscillator.

[0047] Figure 3 As shown, the enable terminals of the voltage regulators 1 to 7 can be controlled by TTL1 to TTL7, so that the first to fourth frequency conversion parts, the 2 to 18 GHz self-calibration frequency source, the 32 to 38 GHz self-calibration frequency source, and the local oscillator frequency source can be powered on or off independently. Figure 4 The TTL8, TTL9 ... TTL14, and TTL15 shown can respectively control the power on and off of amplifiers one to four of the four-way frequency conversion part.

[0048] Before the 2-18 GHz and 32-38 GHz signals are input externally to the dual-band amplitude-phase consistent frequency conversion component, the phases of the four-way frequency conversion parts are self-calibrated using the internal 2-18 GHz frequency source and 32-38 GHz frequency source respectively, and the phase shifter is used to compensate for the phase difference of the four-way output signals.

[0049] When a 2-18 GHz signal is input externally, switch K1 switches to a state where limiter X1 and subsequent circuits are turned on, switch K5 switches to a state where mixer H1 and subsequent circuits are turned on, and TTL5 and TTL6 control the 2-18 GHz self-calibration frequency source and the 32-38 GHz self-calibration frequency source to be powered off and have no output signal, thereby reducing component power consumption and preventing the generated signal from affecting the external input 2-18 GHz signal.

[0050] Switch 2 K2, switch 3 K3, bandpass filter 1 D1 to bandpass filter 6 D6, amplifier 1 F1 to amplifier 3 F3 form a switch filter group to divide the input 2-18 GHz into three frequency bands of 2-8 GHz, 7-13 GHz, and 12-18 GHz, and amplify them respectively.

[0051] When switch 2 K2 and switch 3 K3 are switched to 2-8 GHz, TTL8 and TTL9 control the power switch to power on amplifier 1 F1 and power off amplifier 2 F2 to amplifier 4 F4. At this time, the corresponding output of the local oscillator frequency source is 30 GHz, which is mixed with 2-8 GHz to generate a 32-38 GHz signal.

[0052] When switch 2 K2 and switch 3 K3 are switched to 7-13 GHz, TTL8 and TTL9 control the power switch to power on amplifier 3 F3, while amplifier 1 F1, amplifier 2 F2 and amplifier 4 F4 are powered off. At this time, the corresponding output of the local oscillator frequency source is 25 GHz, which is mixed with 7-13 GHz to generate a 32-38 GHz signal.

[0053] When switch 2 K2 and switch 3 K3 are switched to 12-18 GHz, TTL8 and TTL9 control the power switch to power on amplifier 2 F2, while amplifier 1 F1, amplifier 3 F3 and amplifier 4 F4 are powered off. At this time, the corresponding output of the local oscillator frequency source is 20 GHz, which is mixed with 12-18 GHz to generate a 32-38 GHz signal.

[0054] When the external 32-38 GHz input is applied, the switch 4 K4 switches to the state where the limiter 2 X2 and the subsequent circuit are turned on, the switch 5 K5 switches to the state where the amplifier 4 F4 and the subsequent circuit are turned on, and TTL8 and TTL9 control the power switch to power on the amplifier 4 F4, and power off the amplifier 1 F1 to amplifier 3 F3. TTL7 controls the local oscillator 1 frequency source to power off and output no signal, thereby reducing the power consumption of the components and preventing the generated signal from affecting the external input 32-38 GHz signal.

[0055] The bandpass filter eight D8 suppresses the 32-38 GHz out-of-band signal input from the front.

[0056] The digitally controlled attenuator S1 attenuates the external input signal when the power is too large, thereby preventing the saturation of the amplifier F5 and improving the dynamic range of the component input.

[0057] Each amplifier amplifies the signal input from the front.

[0058] Mixer 2 H2 mixes 32-38 GHz with local oscillator 2 30 GHz to generate 2-8 GHz. Since bandpass filter 9 D9 cannot suppress the harmonics of the low-end frequency of 2-8 GHz, the spurious suppression of the mixer is used to suppress the harmonics of the low-end frequency of 2-8 GHz.

[0059] The bandpass filter D8 suppresses the out-of-band signals of 2 to 8 GHz.

[0060] The digitally controlled phase shifter S2 is used to compensate the phase difference between the four output signals through external control.

[0061] The implementation of the four-way frequency conversion part is consistent with the above. According to the actual use situation, the power supply of the unused frequency conversion part can be turned off through TTL1~TTL4 to reduce the power consumption of the components.

[0062] The present invention designs a reasonable frequency conversion scheme for 2-18 GHz and 32-38 GHz, shares the subsequent part of switch five K5, saves the use of some devices, reduces power consumption, component cost, and reduces the volume and weight of components.

[0063] Since the low-end frequency harmonics cannot be suppressed in the band D9 of the bandpass filter when the final output is 2 to 8 GHz, the scheme of the present invention does not place an amplifier after the secondary frequency conversion, and suppresses the low-end frequency harmonics through the mixer's own spurious suppression, thereby avoiding the influence of the low-end frequency harmonics on subsequent digital processing.

[0064] The four-way frequency conversion part of the component is powered on and off through the power switch. The frequency conversion part that is not needed can be powered off independently through external control according to actual usage to avoid unnecessary power consumption.

[0065] The power supply and control part of the four-way frequency conversion part of the component are independent of each other, and the four-way is divided into separate cavities, which avoids crosstalk between the four-way and improves the isolation between the four-way.

[0066] The power on and off of amplifiers F1 to F4 are synchronized with switch K2, switch K3, and switch K5. When the switch is switched to the corresponding frequency band, the amplifier of the corresponding frequency band is powered on, and the amplifiers of the other frequency bands are powered off. When an external signal is input, the 2-18 GHz frequency source and the 32-38 GHz frequency source are powered off and do not work. When the 2-18 GHz self-calibration is in progress, the 32-38 GHz frequency source is powered off. When the 32-38 GHz self-calibration is in progress, the 2-18 GHz frequency source is powered off. The above scheme further reduces the power consumption of components and the crosstalk between frequency bands.

[0067] The application scenarios of dual-band amplitude-coherent frequency conversion components mainly include:

[0068] Radar system: In the radar system, the dual-band phase-coherent frequency conversion component can realize the segmented selection and frequency shifting of broadband signals, which has a direct impact on the key performance of the system and is the core component of the radar system.

[0069] Electronic countermeasures: Dual-band phase-coherent frequency conversion components are also widely used in the field of electronic countermeasures. They can be used to interfere with enemy radar and communication systems and achieve electronic reconnaissance and intelligence collection.

[0070] Missile guidance: In the missile guidance system, the dual-band phase-coherent frequency conversion component is used for precise guidance and control of the missile to ensure that the missile can accurately hit the target.

[0071] Wireless communication: In the field of wireless communication, dual-band phase-coherent frequency conversion components can be used to achieve signal conversion and transmission between different frequency bands, improving the flexibility and reliability of communication systems.

[0072] It will be appreciated that in the development of any actual implementation, as in any engineering or design project, numerous implementation-specific decisions may be made. Such a development effort may be complex and time-consuming, but will be a routine task of design, fabrication, and production for those of ordinary skill having the benefit of this disclosure without undue experimentation.

[0073] It should be noted that the above embodiments are only used to illustrate the technical solutions of the present invention rather than to limit it. Although the present invention has been described in detail with reference to the preferred embodiments, those skilled in the art should understand that the technical solutions of the present invention may be modified or replaced by equivalents without departing from the spirit and scope of the technical solutions of the present invention, which should all be included in the scope of the claims of the present invention.

Claims

1. A dual-band amplitude-consistent frequency conversion component, characterized in that: include, A limiter 1 (X1), a switch 1 (K1), and a mixer 1 (H1), wherein the limiter 1 (X1) is connected to the switch 1 (K1), the switch 1 (K1) and the mixer 1 (H1) are connected via a switch filter group (100), and the mixer 1 (H1) is connected to a switch 5 (K5); The switch filter group (100) comprises a switch 2 (K2) and a switch 3 (K3); the switch 2 (K2) is connected to a band pass filter 1 (D1), a band pass filter 3 (D3), and a band pass filter 5 (D5); the band pass filter 1 (D1) is connected to the switch 3 (K3) via an amplifier 1 (F1) and a band pass filter 2 (D2); the band pass filter 3 (D3) is connected to the switch 3 (K3) via an amplifier 2 (F2) and a band pass filter 4 (D4); the band pass filter 5 (D5) is connected to the switch 3 (K3) via an amplifier 3 (F3) and a band pass filter 6 (D6); It also includes a limiter 2 (X2), which is connected to a switch 5 (K5) in sequence through a switch 4 (K4), a bandpass filter 7 (D7), and an amplifier 4 (F4).

2. The dual-band amplitude-consistent frequency conversion component according to claim 1, characterized in that: The switch five (K5) is connected to the mixer two (H2) in sequence through the bandpass filter eight (D8), the digitally controlled attenuator (S1), and the amplifier five (F5), and the mixer two (H2) is output through the bandpass filter nine (D9).

3. The dual-band amplitude-consistent frequency conversion component according to claim 2, characterized in that: The invention also comprises a frequency source generating element (200), wherein the frequency source generating element (200) comprises a 100 MHz crystal oscillator (201), and the 100 MHz crystal oscillator (201) generates a first self-calibration frequency source (203), a second self-calibration frequency source (204), a local oscillator first frequency source (205), and a local oscillator second frequency source (206) through a four-power divider (202).

4. The dual-band amplitude-consistent frequency conversion component according to claim 3, characterized in that: The first self-calibration frequency source (203) generates a frequency of 2 to 18 GHz, the second self-calibration frequency source (204) generates a frequency of 32 to 38 GHz, the local oscillator frequency source (205) generates frequencies of 20 GHz, 25 GHz, and 30 GHz, and the local oscillator frequency source (206) generates a frequency of 30 GHz.

5. The dual-band amplitude-consistent frequency conversion component according to claim 4, characterized in that: The first self-calibration frequency source (203) is connected to the input of switch one (K1), and the second self-calibration frequency source (204) is connected to the input of switch four (K4).

6. The dual-band amplitude-consistent frequency conversion component according to claim 5, characterized in that: The local oscillator frequency source (205) is connected to the input of the mixer (H1), and the local oscillator frequency source (206) is connected to the input of the mixer (H2) via a digitally controlled phase shifter (S2).

7. The dual-band amplitude-consistent frequency conversion component according to claim 6, characterized in that: The input frequency of the limiter 1 (X1) is 2 to 18 GHz, and the input frequency of the limiter 2 (X2) is 32 to 38 GHz.

8. The dual-band amplitude-consistent frequency conversion component according to claim 7, characterized in that: The amplifiers 1 (F1) to 4 (F4) are all controlled by a power switch.

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