Rotating electrical machine and control program

Abstract

A rotating electrical machine (10) is provided with: a current command unit (101) that determines current command values (Id *, Iq *) in a first dq coordinate system in which a current phase difference (beta) is corrected and coordinates are converted from a three-phase coordinate system; and a weak magnetic flux control unit (110) that determines a weak excitation current ([Delta] Id) for weak magnetic flux control on the basis of a command voltage (Vq ') on the q axis in a second dq coordinate system obtained by correcting the voltage phase difference ([Delta] v) and performing coordinate conversion from the three-phase coordinate system. The current command unit determines a d-axis current command value by considering the weak excitation current input from the weak magnetic flux control unit.

Description

[0001] Cross-reference to related applications

[0002] This application is based on Japanese application No. 2023-017138 filed on February 7, 2023, and the contents thereof are incorporated herein by reference. Technical Field

[0003] The present disclosure relates to a rotating electric machine and a control program. Background Art

[0004] Conventionally, a rotary electric machine is known that includes a first armature winding supplied with three-phase current from a first inverter and a second armature winding supplied with three-phase current from a second inverter (e.g., Patent Document 1). The rotary electric machine described in Patent Document 1 includes coil bodies Ua, Va, and Wa formed by winding the first armature winding around a first tooth; coil bodies Ub, Vb, and Wb formed by winding the second armature winding around a second tooth; and coil bodies Uc, Vc, and Wc formed by winding the first and second armature windings around a third tooth. Furthermore, the phase difference between the current flowing through the first armature winding wound around the third tooth and the current flowing through the second armature winding wound around the third tooth is set so that the phase difference between the magnetomotive force of the coil bodies Ub, Vb, and Wb of each phase relative to the magnetomotive force of the coil bodies Ua, Va, and Wa of each phase, and the phase difference between the magnetomotive force of the coil bodies Uc, Vc, and Wc of each phase relative to the magnetomotive force of the coil bodies Ub, Vb, and Wb of each phase, form an electrical angle of 20 degrees. This eliminates sixth and twelfth order harmonic components and suppresses torque ripple.

[0005] Prior art literature

[0006] Patent Literature

[0007] Patent Document 1: Japanese Patent No. 7103299

[0008] It has been found that, in the rotating electrical machine described in Patent Document 1, field-weakening control cannot be appropriately performed even if it is attempted to be performed using the conventional method. Summary of the Invention

[0009] The present disclosure has been made in view of the above circumstances, and an object of the present disclosure is to provide a rotating electrical machine and a control program capable of appropriately performing field-weakening control.

[0010] The first technical means for solving the above-mentioned problems is to

[0011] A rotating electric machine comprises: a rotor having a plurality of magnetic poles whose polarities alternate in a circumferential direction; and a stator having a stator core and a multi-phase stator winding, wherein the stator core has a plurality of teeth arranged at predetermined intervals in the circumferential direction and the stator winding is wound around the teeth, wherein:

[0012] The stator winding includes a first stator winding supplied with three-phase current from a first inverter and a second stator winding supplied with three-phase current from a second inverter.

[0013] The three-phase currents supplied from the first inverter and the three-phase currents supplied from the second inverter have a predetermined current phase difference.

[0014] The rotating electrical machine comprises:

[0015] a U-phase coil body Ua formed by winding the first stator winding of the U-phase among the three phases around the first tooth;

[0016] a V-phase coil body Va, wherein the V-phase coil body Va is formed by winding the first stator winding of the V-phase among the three phases around the first tooth;

[0017] a W-phase coil body Wa, wherein the W-phase coil body Wa is formed by winding the first stator winding of the W-phase among the three phases around the first tooth;

[0018] a U-phase coil body Ub formed by winding the second stator winding of the U-phase around the second tooth;

[0019] a V-phase coil body Vb formed by winding the second stator winding of the V-phase around the second tooth;

[0020] a W-phase coil body Wb formed by winding the second W-phase stator winding around a second tooth;

[0021] a U-phase coil body Uc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth;

[0022] a V-phase coil body Vc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth; and

[0023] a W-phase coil body Wc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth;

[0024] The rotating electrical machine comprises:

[0025] a current command unit that determines a current command value in a first dq coordinate system that corrects the current phase difference and performs coordinate conversion from a three-phase coordinate system; and

[0026] a flux-weakening control unit that determines a field-weakening excitation current in flux-weakening control based on a q-axis command voltage in a second dq coordinate system obtained by coordinate conversion from a three-phase coordinate system by correcting a voltage phase difference between a voltage of each phase in the first stator winding and a voltage of each phase in the second stator winding;

[0027] The current command unit determines a d-axis current command value in consideration of the field weakening current input from the flux weakening control unit.

[0028] The second technical means for solving the above-mentioned problems is to

[0029] A rotating electric machine comprises: a rotor having a plurality of magnetic poles whose polarities alternate in a circumferential direction; and a stator having a stator core and a multi-phase stator winding, wherein the stator core has a plurality of teeth arranged at predetermined intervals in the circumferential direction and the stator winding is wound around the teeth, wherein:

[0030] The stator winding includes a first stator winding supplied with three-phase current from a first inverter and a second stator winding supplied with three-phase current from a second inverter.

[0031] The three-phase currents supplied from the first inverter and the three-phase currents supplied from the second inverter have a predetermined current phase difference.

[0032] The rotating electrical machine comprises:

[0033] a U-phase coil body Ua formed by winding the first stator winding of the U-phase among the three phases around the first tooth;

[0034] a V-phase coil body Va, wherein the V-phase coil body Va is formed by winding the first stator winding of the V-phase among the three phases around the first tooth;

[0035] a W-phase coil body Wa, wherein the W-phase coil body Wa is formed by winding the first stator winding of the W-phase among the three phases around the first tooth;

[0036] a U-phase coil body Ub formed by winding the second stator winding of the U-phase around the second tooth;

[0037] a V-phase coil body Vb formed by winding the second stator winding of the V-phase around the second tooth;

[0038] a W-phase coil body Wb formed by winding the second W-phase stator winding around a second tooth;

[0039] a U-phase coil body Uc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth;

[0040] a V-phase coil body Vc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth; and

[0041] a W-phase coil body Wc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth;

[0042] The rotating electrical machine comprises:

[0043] a current command unit that determines a current command value in a first dq coordinate system that corrects the current phase difference and performs coordinate conversion from a three-phase coordinate system;

[0044] an absolute value calculation unit that calculates an absolute value of the induced voltage of the stator winding based on the sum of squares of a d-axis command voltage and a q-axis command voltage in the first dq coordinate system; and

[0045] a flux-weakening control unit that determines a field-weakening excitation current in flux-weakening control based on the absolute value;

[0046] The current command unit determines a current command value of a d-axis current in consideration of the field weakening current input from the flux weakening control unit.

[0047] The third technical means for solving the above-mentioned problems is:

[0048] A control program is implemented by a control device of a rotating electrical machine, the rotating electrical machine comprising: a rotor having a plurality of magnetic poles whose polarities alternate in a circumferential direction; and a stator having a stator core and a multi-phase stator winding, the stator core having a plurality of teeth arranged at predetermined intervals in the circumferential direction, the stator winding being wound around the teeth, wherein:

[0049] The stator winding includes a first stator winding supplied with three-phase current from a first inverter and a second stator winding supplied with three-phase current from a second inverter.

[0050] The three-phase currents supplied from the first inverter and the three-phase currents supplied from the second inverter have a predetermined current phase difference.

[0051] The rotating electrical machine comprises:

[0052] a U-phase coil body Ua formed by winding the first stator winding of the U-phase among the three phases around the first tooth;

[0053] a V-phase coil body Va, wherein the V-phase coil body Va is formed by winding the first stator winding of the V-phase among the three phases around the first tooth;

[0054] a W-phase coil body Wa, wherein the W-phase coil body Wa is formed by winding the first stator winding of the W-phase among the three phases around the first tooth;

[0055] a U-phase coil body Ub formed by winding the second stator winding of the U-phase around the second tooth;

[0056] a V-phase coil body Vb formed by winding the second stator winding of the V-phase around the second tooth;

[0057] a W-phase coil body Wb formed by winding the second W-phase stator winding around a second tooth;

[0058] a U-phase coil body Uc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth;

[0059] a V-phase coil body Vc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth; and

[0060] a W-phase coil body Wc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth;

[0061] The control device is caused to implement:

[0062] Current command processing, which determines a current command value in a first dq coordinate system that corrects the current phase difference and performs coordinate conversion from a three-phase coordinate system; and

[0063] a flux-weakening control process that corrects the voltage phase difference between the voltage of each phase in the first stator winding and the voltage of each phase in the second stator winding and determines the field-weakening excitation current in the flux-weakening control based on the command voltage of the q-axis in the second dq coordinate system converted from the three-phase coordinate system;

[0064] In the current command processing, a d-axis current command value is determined in consideration of the field weakening current input from the flux weakening control unit.

[0065] The fourth technical means for solving the above-mentioned problems is:

[0066] A control program is implemented by a control device of a rotating electrical machine, the rotating electrical machine comprising: a rotor having a plurality of magnetic poles whose polarities alternate in a circumferential direction; and a stator having a stator core and a multi-phase stator winding, the stator core having a plurality of teeth arranged at predetermined intervals in the circumferential direction, the stator winding being wound around the teeth, wherein:

[0067] The stator winding includes a first stator winding supplied with three-phase current from a first inverter and a second stator winding supplied with three-phase current from a second inverter.

[0068] The three-phase currents supplied from the first inverter and the three-phase currents supplied from the second inverter have a predetermined current phase difference.

[0069] The control device comprises:

[0070] a U-phase coil body Ua formed by winding the first stator winding of the U-phase among the three phases around the first tooth;

[0071] a V-phase coil body Va, wherein the V-phase coil body Va is formed by winding the first stator winding of the V-phase among the three phases around the first tooth;

[0072] a W-phase coil body Wa, wherein the W-phase coil body Wa is formed by winding the first stator winding of the W-phase among the three phases around the first tooth;

[0073] a U-phase coil body Ub formed by winding the second stator winding of the U-phase around the second tooth;

[0074] a V-phase coil body Vb formed by winding the second stator winding of the V-phase around the second tooth;

[0075] a W-phase coil body Wb formed by winding the second W-phase stator winding around a second tooth;

[0076] a U-phase coil body Uc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth;

[0077] a V-phase coil body Vc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth; and

[0078] a W-phase coil body Wc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth;

[0079] The control device is caused to implement:

[0080] Current command processing, which determines a current command value in a first dq coordinate system that corrects the current phase difference and performs coordinate transformation from a three-phase coordinate system;

[0081] an absolute value calculation process of calculating the absolute value of the induced voltage based on the square sum of the d-axis voltage and the q-axis voltage in the first dq coordinate system; and

[0082] a flux-weakening control process for determining a field-weakening excitation current in flux-weakening control based on the absolute value;

[0083] In the current command process, a current command value of the d-axis current is determined in consideration of the field weakening current determined in the flux weakening control process.

[0084] According to the above technical means, it is possible to appropriately implement the weak magnetic field control. BRIEF DESCRIPTION OF THE DRAWINGS

[0085] The above-mentioned object and other objects, features and advantages of the present disclosure will become more apparent from the following detailed description with reference to the accompanying drawings.

[0086] Figure 1 It is a longitudinal sectional view showing the electric motor.

[0087] Figure 2 It is a cross-sectional view showing the motor.

[0088] Figure 3 This is a diagram showing the electrical configuration of a control device.

[0089] Figure 4 It is a diagram showing the arrangement of some windings.

[0090] Figure 5 is a diagram showing the stator winding.

[0091] Figure 6 It is a diagram showing the arrangement of lead wires.

[0092] Figure 7This is a diagram showing the higher harmonic components of torque.

[0093] Figure 8 It is a vector diagram showing the total magnetomotive force.

[0094] Figure 9 This is a diagram showing the changes in electromagnetic force.

[0095] Figure 10 This is a diagram showing the control process of the first embodiment.

[0096] Figure 11 (a) is a diagram showing the phase of each phase current, Figure 11 (b) is a diagram showing the phase of each phase voltage.

[0097] Figure 12 This is a diagram showing the relationship between the current phase difference and the voltage phase difference.

[0098] Figure 13 This is a diagram showing the deviation between the current axis and the voltage axis.

[0099] Figure 14 It is a diagram showing the control process of the second embodiment.

[0100] Figure 15 It is a diagram showing the control process of the third embodiment.

[0101] Figure 16 It is a diagram showing the arrangement of partial windings in the second embodiment.

[0102] Figure 17 It is a cross-sectional view showing the motor.

[0103] Figure 18 This is a vector diagram showing the total magnetomotive force according to the second embodiment.

[0104] Figure 19 It is a diagram showing the arrangement of partial windings in the third embodiment.

[0105] Figure 20 It is a diagram showing the arrangement of partial windings in the fourth embodiment.

[0106] Figure 21 It is a diagram showing the arrangement of part of the winding in another example.

[0107] Figure 22 It is a diagram showing the arrangement of part of the winding in another example.

[0108] Figure 23 It is a diagram showing the arrangement of part of the winding in another example. DETAILED DESCRIPTION

[0109] (First embodiment)

[0110] Hereinafter, each embodiment will be described with reference to the accompanying drawings. In the following embodiments, identical or equivalent parts are given the same reference numerals in the drawings, and the descriptions of the parts with the same reference numerals are incorporated herein by reference. In the first embodiment, an electric motor 10 is illustrated as a rotating electrical machine.

[0111] Figure 1 The motor 10 shown is a permanent magnet excitation type motor, specifically, a permanent magnet excitation type synchronous motor having a three-phase winding. In other words, the motor 10 is a brushless motor. This three-phase winding has a dual system. The motor 10 includes a housing 20, a stator 30 fixed to the housing 20, a rotor 40 that rotates relative to the stator 30, and a rotating shaft 11 to which the rotor 40 is fixed. Hereinafter, in this embodiment, the axial direction represents the axial direction of the rotating shaft 11 (indicated by arrow Y1 in the figure). The radial direction represents the radial direction of the rotating shaft 11 (indicated by arrow Y2 in the figure). The circumferential direction represents the circumferential direction of the rotating shaft 11 (indicated by arrow Y3 in the figure).

[0112] The housing 20 is cylindrical and houses the stator 30, rotor 40, and other components. Bearings 23 and 24 are provided in the housing 20, rotatably supporting the rotating shaft 11. The axis of the inner circumference of the housing 20 is coaxial with the rotating shaft 11. An angle sensor 12 is provided at the distal end of the rotating shaft 11. The angle sensor 12 can be either a magnetic sensor or a resolver.

[0113] The stator 30 is cylindrically shaped and arranged approximately in the axial center of the housing 20 along the inner circumference of the housing 20. Furthermore, the stator 30 is fixed to the inner circumferential surface of the housing 20, centered about the axis O of the rotating shaft 11. The stator 30 is a component that constitutes a portion of the magnetic circuit. It is annular and includes a stator core 31 (armature core, stator core) radially disposed on the outer circumference of the rotor 40, and stator windings 32 (armature windings, rotor windings) wound around the stator core 31.

[0114] like Figure 2 As shown, the stator core 31 has an annular back yoke 33 and a plurality of teeth T1 to T18 that protrude radially from the back yoke 33 toward the rotating shaft 11 and are arranged at a predetermined distance in the circumferential direction. Slots 35 (stator slots) are formed between adjacent teeth T1 to T18. In the stator core 31, the slots 35 are arranged at equal intervals in the circumferential direction, and the stator winding 32 is wound around the slots 35. In this embodiment, the number of teeth T1 to T18 is "18", and the number of slots 35 is "18". For ease of explanation, the teeth T1 to T18 are assigned symbols T1 to 18 in a counterclockwise order in the circumferential direction. The stator winding 32 is accommodated and retained in the slots 35. In addition, the stator winding 32 generates magnetic flux by being supplied with electric power (AC power).

[0115] The stator core 31 is an integral component formed by laminating a plurality of thin, annular magnetic steel plates (core sheets) in the axial direction of the stator core 31. The steel plates are formed by punching out a strip of electromagnetic steel sheet material.

[0116] The rotor 40 forms part of the magnetic circuit and has one or more pairs of magnetic poles along the circumferential direction, which are arranged radially opposite to the stator 30. In this embodiment, the rotor 40 has 14 magnetic poles (i.e., the number of magnetic poles is 7). The rotor 40 includes a rotor core 41 made of a magnetic body and permanent magnets 42 fixed to the rotor core 41. Specifically, Figure 2 As shown, the rotor 40 includes 14 permanent magnets 42 as magnet portions whose polarities alternate in the circumferential direction. The permanent magnets 42 are embedded in receiving holes provided in the rotor core 41 in the axial direction.

[0117] The rotor 40 has a well-known structure and can be, for example, an IPM (Interior Permanent Magnet) rotor or an SPM (Surface Permanent Magnet) rotor. Furthermore, a field winding rotor can also be used as the rotor 40. In this embodiment, an IPM rotor is used. The rotor 40 is inserted through the rotating shaft 11 and is fixed to the rotating shaft 11 so as to rotate integrally with the rotating shaft 11 about the rotating shaft 11.

[0118] The motor 10 is connected to a control device 50. The control device 50 is primarily composed of a well-known microcomputer equipped with a CPU, ROM, RAM, and I / O. The CPU implements various functions by executing programs stored in the ROM. Furthermore, various functions may be implemented by electronic circuits as hardware, or at least partially by software, i.e., by processing executed on a computer.

[0119] The control device 50 includes, for example, a function of converting electric power from an external source (e.g., a battery) and supplying the power to the motor 10 to generate driving force. Furthermore, the control device 50 includes, for example, a function of controlling the motor 10 (e.g., controlling current) using information related to the rotation angle input from the angle sensor 12.

[0120] Moreover, if Figure 3 As shown, the control device 50 is provided with a first inverter circuit 51 and a second inverter circuit 52. The first inverter circuit 51 is configured as a full-bridge circuit having upper and lower branches, each of which has the same number of phases. The control device 50 controls the current in each phase by switching the switching elements provided in each branch.

[0121] Describe in detail, such as Figure 3 As shown, the first inverter circuit 51 includes a series connection of an upper branch switch Sp and a lower branch switch Sn as switching elements in each of the three phases (U, V, and W). In this embodiment, voltage-controlled semiconductor switching elements, specifically IGBTs, are used as the upper branch switch Sp and the lower branch switch Sn in each phase. MOSFETs may also be used. Freewheeling diodes (reflux diodes) Dp and Dn are connected in anti-parallel to the upper branch switch Sp and the lower branch switch Sn in each phase, respectively.

[0122] The high-potential terminal (collector) of each phase's upper branch switch Sp is connected to the positive terminal of the battery. Furthermore, the low-potential terminal (emitter) of each phase's lower branch switch Sn is connected to the negative terminal (ground) of the battery. The intermediate connection point between each phase's upper branch switch Sp and lower branch switch Sn is connected to one end of the stator winding 32 (lead wires A1, B1, and C1). The second inverter circuit 52 is similar to the first inverter circuit 51, so a detailed description will be omitted.

[0123] In such rotating electrical machines, noise and vibration caused by torque ripple are problematic. Torque ripple is primarily composed of sixth-order harmonic components and twelfth-order harmonic components, and it is desirable to suppress these. Therefore, a configuration is employed as follows.

[0124] The stator winding 32 is classified into the stator winding 32 of the U phase, the V phase, and the W phase, which respectively represent the three phases. Figure 4 and 5 As shown, the U-phase stator winding 32 is composed of eight partial windings: +U11, +U12, -U13, -U14, -U21, +U22, +U23, and -U24. The V-phase stator winding 32 is composed of eight partial windings: -V11, +V12, +V13, -V14, +V21, -V22, -V23, and +V24. The U-phase stator winding 32 is composed of eight partial windings: +W11, -W12, -W13, +W14, +W21, -W22, -W23, and +W24.

[0125] Moreover, if Figure 2 and Figure 4 As shown, the 24 partial windings correspond to the teeth T1 to T18 and are arranged in the order of +U11, +V21, +W11 / -V22, -W12, -U21, -V11 / -U22, +V12, +W21, +U12 / -W22, -U13, -V23, -W13 / -V24, +W14, +U23, +V13 / -U24, -V14, -W23, -U14 / -W24.

[0126] In addition, the symbols "+" and "-" represent the direction of the current, that is, the polarity of the magnetic field generated by the partial winding. Figure 2 In the figure, when the flow of current from the front side to the back side of the paper is represented by "+", the flow of current from the back side to the front side is represented by "-". That is, when the current flows to the stator winding 32, the partial winding of "+" and the partial winding of "-" generate radially opposite magnetomotive forces. It can be considered that the partial winding of "+" and the partial winding of "-" have a phase difference in magnetomotive force of 180 electrical degrees. The partial winding of "+" and the partial winding of "-" can be achieved by making the winding direction opposite. The same is true for the coil body described later.

[0127] The " / " symbol indicates that two partial windings are arranged with different radial positions for the same teeth T1-T18. That is, two partial windings are arranged for teeth T3, T6, T9, T12, T15, and T18. Meanwhile, one partial winding is arranged for the remaining teeth T1, T2, T4, T5, T7, T8, T10, T11, T13, T14, T16, and T17. Furthermore, the radial positions of the partial windings for teeth T3, T6, T9, T12, T15, and T18 can also be reversed.

[0128] Then, according to Figure 5 The following describes the wiring of the stator winding 32. In this embodiment, a Y connection (star connection) is used, but a delta connection may also be used.

[0129] like Figure 5 As shown, the stator winding 32 consists of a first stator winding 32a and a second stator winding 32b. In the first stator winding 32a, the U-phase partial windings +U11, +U12, -U13, and -U14 are connected in series; the V-phase partial windings -V11, +V12, +V13, and -V14 are connected in series; and the W-phase partial windings +W11, -W12, -W13, and +W14 are connected in series. These series connections have one end connected to the neutral point Q, and the other ends connected to lead wires A1, B1, and C1, respectively, connected to the first inverter circuit 51. Furthermore, lead wire A1 is connected to the U-phase partial winding, lead wire B1 is connected to the V-phase partial winding, and lead wire C1 is connected to the W-phase partial winding.

[0130] Similarly, in the second stator winding 32b, the U-phase partial windings -U21, +U22, +U23, and -U24 are connected in series; the V-phase partial windings +V21, -V22, -V23, and +V24 are connected in series; and the W-phase partial windings +W21, -W22, -W23, and +W24 are connected in series. These series connections have one end connected to the neutral point Q, and the other ends connected to lead wires A2, B2, and C2, respectively, connected to the second inverter circuit 52. Furthermore, lead wire A2 is connected to the U-phase partial winding, lead wire B2 is connected to the V-phase partial winding, and lead wire C2 is connected to the W-phase partial winding.

[0131] like Figure 6 As shown, lead wires A1, B1, C1, A2, B2, and C2 are arranged point-symmetrically about the axis O of the rotating shaft 11. Specifically, lead wires A1 and A2 are arranged 180 degrees apart, lead wires B1 and B2 are arranged 180 degrees apart, and lead wires C1 and C2 are arranged 180 degrees apart. Furthermore, lead wires A1, B1, C1, A2, B2, and C2 are arranged linearly along the axial direction.

[0132] Here, only the first stator winding 32a is wound (wrapped) around teeth T1, T4, T7, T10, T13, and T16, thereby providing two coil bodies for each phase. The U-phase coil body is referred to as coil body Ua, the V-phase coil body as coil body Va, and the W-phase coil body as coil body Wa. Hereinafter, teeth around which only the first stator winding 32a is wound may sometimes be referred to as first teeth. In the first embodiment, teeth T1, T4, T7, T10, T13, and T16 correspond to first teeth.

[0133] Furthermore, only the second stator winding 32b is wound around teeth T2, T5, T8, T11, T14, and T17, thereby providing two coil bodies for each phase. These U-phase coil bodies are referred to as coil bodies Ub, the V-phase coil bodies as coil bodies Vb, and the W-phase coil bodies as coil bodies Wb. Hereinafter, teeth wound only with the second stator winding 32b may sometimes be referred to as second teeth. In the first embodiment, teeth T2, T5, T8, T11, T14, and T17 correspond to second teeth.

[0134] Furthermore, the first stator winding 32a and the second stator winding 32b are wound around teeth T3, T6, T9, T12, T15, and T18, thereby providing two coil bodies for each phase. These U-phase coil bodies are denoted as coil bodies Uc, the V-phase coil bodies as coil bodies Vc, and the W-phase coil bodies as coil bodies Wc. Hereinafter, the teeth around which the first stator winding 32a and the second stator winding 32b are wound may sometimes be denoted as third teeth. In the first embodiment, teeth T3, T6, T9, T12, T15, and T18 correspond to third teeth.

[0135] like Figure 2 As shown in FIG. 1 , the coil bodies Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc of each phase are arranged in a two-fold rotational symmetry with respect to the axis of the rotating shaft 11. That is, even if the coil bodies Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc are rotated 180 degrees mechanically with respect to the axis, the coil bodies Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc remain in a two-fold rotational symmetry with respect to the axis of the rotating shaft 11. c 、V c 、W c The configuration order is also the same.

[0136] Here, the magnetomotive force Fu1a of the partial windings +U11 and +U12, the magnetomotive force Fu1b of the partial windings -U13 and -U14, the magnetomotive force Fu2a of the partial windings +U22 and +U23, and the magnetomotive force Fu2b of the partial windings -U21 and -U24 can be expressed by equations (1) to (4). Furthermore, "θ" is the phase of the current flowing into the stator winding 32 (based on the phase of the U-phase current supplied from the first inverter circuit 51). "β" is the phase difference between the current supplied from the first inverter circuit 51 and the current supplied from the second inverter circuit 52 (hereinafter sometimes referred to as the current phase difference). Furthermore, "N" is the number of turns of each partial winding. "I" is the amplitude of the current.

[0137] [Number 1]

[0138] Fu1a=N×I×sin(θ)···(1)

[0139] Fu1b=N×I×sin(θ-180°)···(2)

[0140] Fu2a=N×I×sin(θ-β)···(3)

[0141] Fu2b=N×I×sin(θ-180°-β)···(4)

[0142] Similarly, the magnetomotive force Fv1a of the partial windings +V12 and +V13, the magnetomotive force Fv1b of the partial windings -V11 and -V14, the magnetomotive force Fv2a of the partial windings +V21 and +V24, and the magnetomotive force Fv2b of the partial windings -V22 and -V23 can be expressed by equations (5) to (8).

[0143] [Number 2]

[0144] Fv1a=N×I×sin(θ-120°)···(5)

[0145] Fv1b=N×I×sin(θ-300°)···(6)

[0146] Fv2a=N×I×sin(θ-120°-β)···(7)

[0147] Fv2b=N×I×sin(θ-300°-β)···(8)

[0148] Similarly, the magnetomotive force Fw1a of the partial windings +W11 and +W14, the magnetomotive force Fw1b of the partial windings -W12 and -W13, the magnetomotive force Fw2a of the partial windings +W21 and +W24, and the magnetomotive force Fw2b of the partial windings -W22 and -W23 can be expressed by equations (9) to (12).

[0149] [Number 3]

[0150] Fw1a=N×I×sin(θ-240°)···(9)

[0151] Fw1b=N×I×sin(θ-420°)=N×I×sin(θ-60°)···(10)

[0152] Fw2a=N×I×sin(θ-240°-β)···(11)

[0153] Fw2b=N×I×sin(θ-420°-β)=N×I×sin(θ-60°-β)···(12)

[0154] Furthermore, the sixth harmonic component "Tr6" of the torque in each phase can be expressed by equation (13). Furthermore, the twelfth harmonic component "Tr12" of the torque in each phase can be expressed by equation (14).

[0155] [Number 4]

[0156] Tr6=Ta×sin 6(θ+α)+Tb×sin 6(θ+α-λ1)+Tc×sin6(θ+α-λ2)···(13)

[0157] Tr12=Ta×sin12(θ+α)+Tb×sin112(θ+α-λ1)+Tc×sin12(θ+α-λ2)···(14)

[0158] In equations (13) and (14), α is a constant that depends on noise, etc. Furthermore, in the first embodiment, the first term in equations (13) and (14) corresponds to the component based on the coil bodies Ua, Va, and Wa, the second term corresponds to the component based on the coil bodies Ub, Vb, and Wb, and the third term corresponds to the component based on the coil bodies Uc, Vc, and Wc.

[0159] Moreover, "λ1" represents the phase difference between the magnetomotive force of coil body Ub and the magnetomotive force of coil body Ua in the U phase. In other words, it represents the phase lag of the magnetomotive force of coil body Ub with the magnetomotive force of coil body Ua as the reference. Similarly, "λ1" represents the phase difference between the magnetomotive force of coil body Vb and the magnetomotive force of coil body Va in the V phase, and represents the phase difference between the magnetomotive force of coil body Wb and the magnetomotive force of coil body Wa in the W phase. Similarly, "λ2" represents the phase difference between the magnetomotive force of coil body Uc and the magnetomotive force of coil body Ua in the U phase, represents the phase difference between the magnetomotive force of coil body Vc and the magnetomotive force of coil body Va in the V phase, and represents the phase difference between the magnetomotive force of coil body Wc and the magnetomotive force of coil body Wa in the W phase. Moreover, in formulas (13) and (14), "Ta" is a constant proportional to the number of turns of coil bodies Ua, Va, and Wa and the amplitude of the current. Furthermore, "Tb" is a constant proportional to the number of turns of the coil bodies Ub, Vb, and Wb and the amplitude of the current. Furthermore, "Tc" is a constant proportional to the number of turns of the coil bodies Uc, Vc, and Wc and the amplitude of the current.

[0160] Here, it can be seen that when "λ1" and "λ2" are "20 degrees" electrical angle and "40 degrees" electrical angle respectively, and "Ta", "Tb" and "Tc" are the same, as shown in formulas (15), (16) and Figure 7 As shown, the higher harmonic components of the torque are eliminated.

[0161] [Number 5]

[0162] Tr6=Ta×sin 6(θ+α)+Ta×sin 6(θ+α-20°)+Ta×sin 6(θ+α-40°)

[0163] =Ta×sin 6(θ+α)+Ta×sin{6(θ+α)-120°}+Ta×sin{6(θ+α)-240°}

[0164] =0···(15)

[0165] Tr12=Ta×sin 12(θ+α)+Ta×sin 12(θ+α-20°)+Ta×sin 12(θ+α-40°)

[0166] =Ta×sin 12(θ+α)+Ta×sin{12(θ+α)-120°}+Ta×sin{12(θ+α)-240°}

[0167] =0···(16)

[0168] Furthermore, in this embodiment, the current phase difference "β" between the first inverter circuit 51 and the second inverter circuit 52 is 20 electrical degrees. This means that the phase difference between the magnetomotive force of coils Ub, Vb, and Wb relative to the magnetomotive force of coils Ua, Va, and Wa is 20 degrees, and "λ1" is 20 degrees. Therefore, it can be considered that torque ripple can be suppressed by setting the phase difference between the magnetomotive force of coils Uc, Vc, and Wc relative to the magnetomotive force of coils Ua, Va, and Wa to 40 degrees.

[0169] In other words, the phase difference between the magnetomotive force of coil bodies Ub, Vb, and Wb relative to the magnetomotive force of coil bodies Ua, Va, and Wa, and the phase difference between the magnetomotive force of coil bodies Uc, Vc, and Wc relative to the magnetomotive force of coil bodies Ub, Vb, and Wb, respectively, are all 20 degrees. While the phase difference is preferably 20 degrees, it may be within a specified phase range encompassing 20 degrees (for example, a range of 15 to 25 degrees). In this case, the torque ripple suppression effect can also be achieved.

[0170] Therefore, in this embodiment, the phase difference between the magnetomotive force generated by the partial winding of the first stator winding 32a wound around each third tooth and the magnetomotive force generated by the partial winding of the second stator winding 32b is set within a range of 72 to 88 electrical degrees, such that the phase difference between the magnetomotive force of the coil bodies Uc, Vc, and Wc relative to the magnetomotive force of the coil bodies Ua, Va, and Wa is 40 degrees (and the phase difference between the magnetomotive force of the coil bodies Uc, Vc, and Wc relative to the magnetomotive force of the coil bodies Ub, Vb, and Wb is 20 degrees). In the following, the phase difference between the magnetomotive force of the partial winding of the second stator winding 32b wound around each third tooth and the magnetomotive force of the partial winding of the first stator winding 32a is sometimes expressed as a total phase difference.

[0171] The total phase difference is within the range of 72 to 88 electrical degrees, but is preferably 80 degrees. In this embodiment, the total phase difference is set to 80 degrees.

[0172] Taking the coil body Uc provided on the tooth T9 serving as the third tooth as an example, the total magnetomotive force will be described in detail. Figure 2 and 4 As shown in FIG. 1 , the coil body Uc provided on the tooth T9 is composed of the partial winding +U12 / -W22. The magnetomotive force Fula of the partial winding +U12 and the magnetomotive force Fw2b of the partial winding -W22 are shown in equations (1) and (12). If these magnetomotive forces are expressed in a vector diagram, they are as follows: Figure 8 Then, if the magnetomotive force Fw2b of the partial winding +U12 and the magnetomotive force Fw2b of the partial winding -W22 are added together, the result is as shown in formula (17).

[0173] [Number 6]

[0174] Fu3a=Fu1a+Fw2b

[0175] =N×I×sin(θ)+N×I×sin(θ-80°)

[0176] =1.53×N×I×sin(θ-40°)···(17)

[0177] Furthermore, in formula (17), the number of turns of the partial winding +U12 and the number of turns of the partial winding -W22 are both N. As shown in formula (17), by winding the partial winding +U12 and the partial winding -W22 around tooth T9, it is possible to achieve a magnetomotive force of the coil bodies Uc, Vc, and Wc that is 40 degrees out of phase with the magnetomotive force of the coil bodies Ua, Va, and Wa.

[0178] Then, as shown in formula (17), the magnetomotive force is proportional to the number of turns of the partial winding. Therefore, if the number of turns of each partial winding is not set appropriately, the amplitude of the magnetomotive force will not be aligned between the coil bodies Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc. In other words, in formulas (13) and (14), the constants "Ta", "Tb", and "Tc" will have deviations. When the amplitude of the magnetomotive force is not aligned, the effect of eliminating torque fluctuations will be reduced. Therefore, it is desirable to set the number of turns in such a way that the amplitude of the magnetomotive force of each coil body Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc is within the specified amplitude range.

[0179] Therefore, in this embodiment, in order to align the magnetomotive force of the coil bodies Ua, Va, Wa with the magnetomotive force of the coil bodies Ub, Vb, Wb, the number of turns of the coil bodies Ua, Va, Wa and the coil bodies Ub, Vb, Wb are the same number of turns "Na".

[0180] Moreover, the number of turns of the first stator winding 32a wound on each third tooth and the number of turns of the second stator winding 32b are set so that the magnetomotive force of the coil bodies Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc of each phase are of the same degree.

[0181] Specifically, when the number of turns of the first stator winding 32a wound around the third tooth and the number of turns of the second stator winding 32b are "Nb", the number of turns "Na" and "Nb" are set to satisfy the relationship 1.4 ≤ Na / Nb ≤ 1.6. Na / Nb is preferably a value close to 1.53. In this embodiment, the number of turns is set so that the ratio of Na:Nb is 3:2 (Na / Nb is 1.5).

[0182] Next, the control of the electric motor 10 according to the first embodiment will be described. Figure 10, which shows the control process for controlling the current of each phase U, V, and W. In addition, the current control of the first stator winding 32a (control of the first inverter circuit 51) and the current control of the second stator winding 32b (control of the second inverter circuit 52) ​​are implemented in the same manner.

[0183] The control process is performed by the control device 50 (CPU) executing the program stored in the ROM. In addition, the various functions of the control device 50 (current command unit 101, dq conversion unit 102, d-axis current feedback control unit 103, q-axis current feedback control unit 104, The operation signal generating unit 106 and the flux-weakening control unit 110 are implemented by executing a program stored in the ROM by (the CPU of) the control device 50. All or part of the various functions implemented by the control device 50 may be implemented in hardware.

[0184] The current command unit 101 uses a torque-dq conversion map to set the d-axis current command value Id* and the q-axis current command value Iq* based on the torque command value (traction torque command value or power generation torque command value) for the motor 10, the field-weakening current ΔId input from the flux-weakening control unit 110, and the rotational speed (electrical angular velocity) ω obtained by time-differentiating the electrical angle of rotation of the motor 10. The torque command value is also commanded by a higher-level control device, etc. The field-weakening current ΔId input from the flux-weakening control unit 110 will be described later.

[0185] The dq conversion unit 102 converts the current detection values ​​(phase currents Iu1, Iv1, Iw1, Iu2, Iv2, and Iw2) of each of the three phases (U, V, and W) obtained by the current sensors provided for each phase into d-axis currents (Id1 and Id2) and q-axis currents (Iq1 and Iq2), which are components of a rectangular rotating coordinate system. In the first embodiment, the dq conversion unit 102 corrects the current phase difference and performs coordinate conversion so that the d-axis current Id1 of the first stator winding 32a and the d-axis current Id2 of the second stator winding 32b coincide, and the q-axis current Iq1 of the first stator winding 32a and the q-axis current Iq2 of the second stator winding 32b coincide. Specifically, the conversion is performed as shown in the following equations (18) and (19).

[0186] [Number 7]

[0187]

[0188]

[0189] Furthermore, "Id1" represents the d-axis current of the first stator winding 32a in the first dq-axis coordinate system, and "Iq1" represents the q-axis current of the first stator winding 32a in the first dq-axis coordinate system. "Iu1" represents the U-phase current (current detection value) in the first stator winding 32a, "Iv1" represents the V-phase current (current detection value) in the first stator winding 32a, and "Iw1" represents the W-phase current (current detection value) in the first stator winding 32a. Furthermore, "Id2" represents the d-axis current of the second stator winding 32b in the first dq-axis coordinate system, and "Iq2" represents the q-axis current of the second stator winding 32b in the first dq-axis coordinate system. "Iu2" represents the U-phase current (current detection value) in the second stator winding 32b, "Iv2" represents the V-phase current (current detection value) in the second stator winding 32b, and "Iw2" represents the W-phase current (current detection value) in the second stator winding 32b. Furthermore, "β" is the current phase difference similarly to the above, and is "20°" in the first embodiment.

[0190] By converting as shown in equations (18) and (19), the current phase difference can be corrected, and in the first dq-axis coordinate system, Id1 = Id2 and Iq1 = Iq2. This allows the control device 50 to control the current in the first stator winding 32a and the current in the second stator winding 32b to be equal.

[0191] In addition, each phase current is converted to the first dq axis coordinate system, which is used to represent that each phase current is converted into d-axis current and q-axis current in a manner that corrects the current phase difference. Figure 10 In, it means The dq converter 102 corresponds to a current converter. The d-axis current Id1 and the d-axis current Id2 are sometimes collectively represented as the d-axis current Id. The q-axis current Iq1 and the q-axis current Iq2 are sometimes collectively represented as the q-axis current Iq.

[0192] The d-axis current feedback control unit 103 applies a PI (Proportional-Integral) gain to the deviation between the d-axis current Id and the d-axis current command value Id*, calculating d-axis command voltages Vd1 and Vd2 as correction command values, as the manipulated variable for feedback control of the d-axis current Id toward the d-axis current command value Id*. These d-axis command voltages Vd1 and Vd2 are values ​​in the first dq-axis coordinate system and are sometimes collectively expressed as Vd. The d-axis command voltage is sometimes also expressed as d-axis voltage.

[0193] Furthermore, the q-axis current feedback control unit 104 of the control device 50 applies a PI gain to the deviation between the q-axis current Iq and the q-axis current command value Iq* as an operation variable for feedback control of the q-axis current Iq toward the q-axis current command value Iq*, thereby calculating q-axis command voltages Vq1 and Vq2 as correction command values. These q-axis command voltages Vq1 and Vq2 are values ​​in the first dq-axis coordinate system and are sometimes collectively represented as Vq. Furthermore, the q-axis command voltage is sometimes also represented as q-axis voltage. The d-axis current feedback control unit 103 and the q-axis current feedback control unit 104 correspond to a command voltage determination unit.

[0194] The d-axis and q-axis command voltages Vd and Vq in the first dq-axis coordinate system are converted into the U-phase, V-phase, and W-phase command voltages (Vu1, Vv1, Vw1, Vu2, Vv2, and Vw2). Figure 10 In, it is expressed as Furthermore, the equations for converting the U-phase voltage, the V-phase voltage, and the W-phase voltage into the d-axis voltage and the q-axis voltage are shown in equations (20) and (21). This inverse conversion is performed to convert the d-axis and q-axis command voltages into U-phase, V-phase, and W-phase command voltages.

[0195] [Number 8]

[0196]

[0197]

[0198] Furthermore, "Vd1" is the d-axis voltage (d-axis command voltage) of the first stator winding 32a in the first dq-axis coordinate system, and "Vq1" is the q-axis voltage (q-axis command voltage) of the first stator winding 32a in the first dq-axis coordinate system. Furthermore, "Vu1" is the U-phase voltage (U-phase command voltage) of the first stator winding 32a, "Vv1" is the V-phase voltage (V-phase command voltage) of the first stator winding 32a, and "Vw1" is the W-phase voltage (W-phase command voltage) of the first stator winding 32a. Furthermore, "Vd2" is the d-axis voltage (d-axis command voltage) of the second stator winding 32b in the first dq-axis coordinate system, and "Vq2" is the q-axis voltage (q-axis command voltage) of the second stator winding 32b in the first dq-axis coordinate system. Furthermore, "Vu2" represents the U-phase voltage (U-phase command voltage) in the second stator winding 32b, "Vv2" represents the V-phase voltage (V-phase command voltage) in the second stator winding 32b, and "Vw2" represents the W-phase voltage (W-phase command voltage) in the second stator winding 32b. Furthermore, "β" represents the current phase difference, which is "20°" in the first embodiment, as described above. Furthermore, the conversion of each phase voltage to the first dq-axis coordinate system indicates the conversion of each phase voltage into the d-axis voltage and the q-axis voltage, with the current phase difference corrected.

[0199] That is, the first embodiment The command voltages of the d-axis and the q-axis in the first dq-axis coordinate system are converted into command voltages of the U-phase, V-phase, and W-phase in the three-phase coordinate system.

[0200] Furthermore, the control device 50's operation signal generator 106 generates inverter operation signals based on the three-phase command voltages using a well-known triangular wave carrier comparison method. Specifically, the operation signal generator 106 generates switching operation signals (task signals) for the upper and lower arms of each phase by performing PWM control by comparing the magnitude of a signal normalized to the power supply voltage based on the three-phase command voltages with a carrier signal (carrier) such as a triangular wave signal. The driver 107 included in the control device 50 switches the three-phase switches Sp and Sn of the first inverter circuit 51 and the second inverter circuit 52 based on the switching operation signals generated by the operation signal generator 106.

[0201] The motor 10 of the first embodiment is designed to employ flux-weakening control. Flux-weakening control uses a negative d-axis current to reduce the d-axis magnetic flux by utilizing the demagnetizing effect of the d-axis armature reaction, thereby achieving an equivalent field-weakening effect.

[0202] Here, the contents of flux weakening control are explained. The voltage equations of the motor 10 are shown in equations (22) and (23). In equations (22) and (23), "Id" is the d-axis current, "Iq" is the q-axis current, "Vd" is the d-axis voltage, and "Vq" is the q-axis voltage. Furthermore, "R" is the resistance value of the motor 10, "Id" is the d-axis inductance, "Lq" is the q-axis inductance, "ω" is the rotation speed of the motor 10, and "Φa" is the magnet flux. Furthermore, the terminal voltage "Vt" of the motor 10 is shown in equation (24).

[0203] [Number 9]

[0204] Vd=R×Id+ω×Ld×Iq···(22)

[0205] Vq=R×Iq+ω×Lq×Id+ω×Φa···(23)

[0206] Vt 2 =Vd 2 +Vq 2 ···(twenty four)

[0207] As shown in the above formulas (22) to (24), it can be seen that when the rotational speed ω of the motor 10 increases, the terminal voltage Vt of the motor 10 increases. The applied voltage of the motor 10 stipulates the upper limit value Vmax. When the terminal voltage Vt exceeds the upper limit value Vmax, the motor 10 cannot be driven. In other words, it cannot be controlled. To this end, it is necessary to make the negative d-axis current Id flow according to the rotational speed ω (operating speed) in such a way that the terminal voltage Vt does not exceed the upper limit value Vmax, thereby reducing the q-axis voltage Vq. Therefore, in the field-weakening control, the following control is implemented: the q-axis voltage Vq is monitored, and the d-axis current Id is determined in such a way that the terminal voltage Vt does not exceed the upper limit value Vmax.

[0208] In the first embodiment, the first stator winding 32a and the second stator winding 32b are wound around the third teeth (teeth T3, T6, T9, T12, T15, and T18), assumingly forming coil bodies Uc, Vc, and Wc equivalent to coil bodies Ua, Va, Wa, Ub, Vb, and Wb. With this configuration, the current phase difference and the voltage phase difference do not match, making it impossible to properly implement flux-weakening control.

[0209] Describe in detail, such as Figure 11 As shown in (a), the phase difference of the current of each phase is "20 degrees". However, it is recognized that when the coil bodies Uc, Vc, and Wc are constructed in a suspicious manner, as shown in FIG. Figure 11As shown in (b), the phase difference between the first stator winding 32a and each phase voltage (induced voltage) and the second stator winding 32b and each phase voltage (induced voltage) is different from the current phase difference. Figure 11 and Figure 12 As shown, when the current phase difference is "20°" and the total phase difference is "80°", the voltage phase difference "δv" is "-12°".

[0210] Therefore, when each phase voltage is converted to the first dq axis coordinate system, according to the difference between the current phase difference "20°" and the voltage phase difference "-12°", Figure 13 As shown in (a), in the first dq axis coordinate system, the current axis (indicated by the hollow arrow) deviates from the axis of the q axis voltage Vq1 of the first stator winding 32a. Figure 13 As shown in (b), in the first dq-axis coordinate system, the current axis is offset from the axis of the q-axis voltage Vq2 of the second stator winding 32b. Therefore, in the first dq-axis coordinate system, Vd1 and Vd2 do not coincide, and Vq1 and Vq2 do not coincide.

[0211] Due to this deviation, for example, in the first dq-axis coordinate system, the q-axis voltage Vq1 is calculated to be lower than the actual value. Furthermore, when calculated to be lower than the actual value, a negative d-axis current may not flow even when the actual q-axis voltage reaches a voltage that requires it, leading to inappropriate field-weakening control. Furthermore, when field-weakening control is not properly implemented, current oscillations can cause vibrations, and the rotational speed cannot be properly increased.

[0212] Therefore, in the motor 10 of the first embodiment, when field-weakening control is implemented, coordinate conversion is performed to correct the voltage phase difference. Specifically, the voltage coordinate conversion unit 111 receives the d-axis command voltage Vd1 and the q-axis command voltage Vq1 (command voltages of the first dq-axis coordinate system) from the d-axis current feedback control unit 103 and the q-axis current feedback control unit 104, and performs coordinate conversion to the second dq-axis coordinate system to correct the voltage phase difference. Specifically, the coordinate conversion is performed as shown in the following equation (25).

[0213] [Number 10]

[0214]

[0215]

[0216] In addition, "β" is the current phase difference, which is "20°" in the first embodiment. Also, "δv" is the voltage phase difference. In the first embodiment, Figure 12As shown, the current phase difference is "20°" and the total phase difference is "80°", so the voltage phase difference "δv" is "-12°". "Vd1'" is the d-axis voltage (d-axis instruction voltage) of the first stator winding 32a in the second dq-axis coordinate system, and "Vd2'" is the d-axis voltage (d-axis instruction voltage) of the second stator winding 32b in the second dq-axis coordinate system. "Vq1'" is the q-axis voltage (q-axis instruction voltage) of the first stator winding 32a in the second dq-axis coordinate system, and "Vq2'" is the q-axis voltage (q-axis instruction voltage) of the second stator winding 32b in the second dq-axis coordinate system. By performing this conversion, the q-axis voltage Vq1' is equal to the q-axis voltage Vq2'.

[0217] Alternatively, the d-axis command voltage Vd2 and the q-axis command voltage Vq2 (the command voltages in the first dq-axis coordinate system) can be obtained and coordinate conversion performed as shown in the following equation (26). Since the q-axis voltages in the second dq-axis coordinate system are all the same (Vq1' = Vq2'), the result will be the same regardless of which value is used.

[0218] Furthermore, the flux-weakening control unit 110 calculates the field-weakening current ΔId (negative d-axis current) based on the q-axis voltage Vq' (Vq1' or Vq2') in the second dq-axis coordinate system. Specifically, the flux-weakening control unit 110 monitors the q-axis voltage Vq' in the second dq-axis coordinate system and determines the field-weakening current ΔId so that the terminal voltage Vt does not exceed the upper limit Vmax. The field-weakening current ΔId can be determined by calculation or by mapping. Furthermore, the field-weakening current ΔId becomes the value in the first dq-axis coordinate system.

[0219] As described above, the current command unit 101 sets the d-axis current command value and the q-axis current command value based on the torque command value, the field weakening current ΔId input from the flux weakening control unit 110, the rotation speed ω, etc. The subsequent flow is omitted as it is described above.

[0220] As described above, according to the configuration of the first embodiment, the following effects are achieved.

[0221] The flux-weakening control unit 110 monitors the q-axis voltage Vq1' (or Vq2') in the second dq-axis coordinate system, used to correct the voltage phase difference, to determine the field-weakening current. Correcting the voltage phase difference eliminates the deviation between the calculated q-axis voltage Vq1' (or Vq2') and the actual value, enabling appropriate field-weakening control. This suppresses current oscillations and appropriately increases the rotational speed. Furthermore, since the field-weakening current ΔId is output based on the value in the first dq-axis coordinate system, processing by the current command unit 101 is simplified.

[0222] The phase differences between the magnetomotive force of coil bodies Ub, Vb, and Wb relative to the magnetomotive force of coil bodies Ua, Va, and Wa, and the phase differences between the magnetomotive force of coil bodies Uc, Vc, and Wc relative to the magnetomotive force of coil bodies Ub, Vb, and Wb, are set within a specified phase range including 20 degrees. Specifically, the phase difference (total phase difference) between the magnetomotive force generated by the partial winding of the second stator winding 32b wound on each third tooth relative to the magnetomotive force generated by the partial winding of the first stator winding 32a wound on the third tooth is set to be within the range of 72 to 88 electrical angles. In this embodiment, the total phase difference is set to 80 degrees. As shown in equations (15) to (17), the 6th or 12th harmonic components of the torque can be eliminated, suppressing torque ripple.

[0223] The number of turns in each winding section is set so that the magnetomotive force of the coil bodies Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc is within a specified amplitude range (equivalent in this embodiment). Specifically, if the number of turns of the first stator winding 32a wound around the first tooth is "Na," the number of turns of the second stator winding 32b wound around the second tooth is "Na." Furthermore, if the number of turns of the first stator winding 32a and the number of turns of the second stator winding 32b wound around the third tooth are both "Nb," the number of turns is set to satisfy the relationship 1.4 ≤ Na / Nb ≤ 1.6. In this embodiment, the number of turns is set so that the ratio of Na:Nb is 3:2 (Na / Nb is 1.5). This makes it possible to make the amplitudes of the magnetomotive forces of the coil bodies Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc substantially equal, thereby suppressing torque ripple.

[0224] The number of poles in the motor 10 is 14, and the number of slots 35 is 18. That is, the number of poles is (18±4)×m (m is an integer greater than or equal to 1), and the number of slots is 18×m. This ensures a balanced electromagnetic force around the axis.

[0225] according to Figure 9 Provide detailed explanation. Figure 9 (a) is a diagram showing the relationship between the electromagnetic force generated by each of the teeth T1 to T18 and the mechanical angle of the motor 10 . Figure 9 (b) is the case where the rotation axis 11 is the center and the circumferential direction is expressed Figure 9 (a) shows the change in electromagnetic force.

[0226] like Figure 4 As shown, the coil bodies Ua, Ub, and Uc of the U phase are arranged at approximately 90-degree intervals. The same applies to the coil bodies Va, Vb, and Vc of the V phase and the coil bodies Wa, Wb, and Wc of the W phase. Figure 9As shown, the balance of electromagnetic force is improved. Therefore, the electromagnetic force is not biased anywhere, which can suppress torque fluctuations, vibration, and noise.

[0227] The number of poles is 14, the number of slots is 18, and the total phase difference between the magnetomotive force generated by the partial winding of the first stator winding 32a wound around the third tooth and the magnetomotive force generated by the partial winding of the second stator winding 32b wound around the third tooth is 80 electrical degrees. Figure 2 and 4 Arrange the partial windings as shown. Figure 2 and 4 As shown, the first stator winding 32a wound around the third tooth can be connected to the first stator winding 32a wound around one of the circumferentially adjacent teeth T1 to T18. For example, the partial winding -U14 of the first stator winding 32a wound around tooth T18, which is the third tooth, can be connected to the partial winding +U11 of the first stator winding 32a wound around tooth T1, which is the first tooth adjacent to the circumferential direction.

[0228] Similarly, the second stator winding 32b wound around the third tooth can be connected to the second stator winding 32b wound around the other of the circumferentially adjacent teeth T1 to T18. For example, the partial winding +W24 of the second stator winding 32b wound around tooth T18, which is the third tooth, can be connected to the partial winding -W23 of the second stator winding 32b wound around tooth T17, which is the second circumferentially adjacent tooth. This shortens the overlap wires connecting the slots 35 at the coil ends, facilitating connections and enabling a more compact design.

[0229] like Figure 6 As shown, lead wires A1, B1, C1, A2, B2, and C2 are arranged symmetrically about the axis of rotating shaft 11. This balances and eliminates magnetic flux leakage from lead wires A1, B1, C1, A2, B2, and C2, thereby suppressing detection errors of angle sensor 12.

[0230] (Second embodiment)

[0231] A part of the control process in the first embodiment may be changed. Figure 14 A second embodiment in which a portion of the control process is modified will be described. In the second embodiment, as in the first embodiment, the control process is performed by the control device 50 (CPU) executing a program stored in the ROM. In addition, various functions of the control device 50 in the second embodiment (current command unit 201, dq conversion unit 202, d-axis current feedback control unit 203, q-axis current feedback control unit 204, The operation signal generating unit 106 and the flux-weakening control unit 110 are implemented by executing a program stored in the ROM by (the CPU of) the control device 50. All or part of the various functions implemented by the control device 50 may be implemented by hardware.

[0232] Figure 14 The control process in the second embodiment is shown. First, the dq converter 202 in the second embodiment is described.

[0233] The dq converter 202 converts the current detection values ​​(individual phase currents) of each of the three phases (U, V, and W phases) obtained by the current sensors provided for each phase into d-axis currents and q-axis currents, which are components of a rectangular rotating coordinate system. At this time, the dq converter 202 converts the individual phase currents into d-axis currents "Id1'" and "Id2'" in a second dq coordinate system, and q-axis currents "Iq1'" and "Iq2'" in a second dq coordinate system, correcting for the voltage phase difference "δv." Specifically, the conversion is performed as shown in the following equations (27) and (28).

[0234] [Number 11]

[0235]

[0236]

[0237] In addition, "Id1'" is the d-axis current (current detection value) of the first stator winding 32a in the second dq-axis coordinate system, and "Iq1'" is the q-axis current (current detection value) of the first stator winding 32a in the second dq-axis coordinate system. Moreover, "Id2'" is the d-axis current (current detection value) of the second stator winding 32b in the second dq-axis coordinate system, and "Iq2'" is the q-axis current (current detection value) of the second stator winding 32b in the second dq-axis coordinate system. Moreover, "δv" is the voltage phase difference of the second stator winding 32b relative to the first stator winding 32a. In the second embodiment, as shown in FIG. Figure 11 and Figure 12 As shown, the current phase difference is "20°", the total phase difference is "80°", and therefore the voltage phase difference "δv" is "-12°".

[0238] By converting as shown in equations (27) and (28), the voltage phase difference is corrected, so Id1'≠Id2', Iq1'≠Iq2'. In addition, each phase current is converted to the second dq axis coordinate system to express the conversion of each phase current into the d-axis current and the q-axis current in a manner that corrects the voltage phase difference. Figure 14 In, it means

[0239] like Figure 14 As shown, the current command unit 201 of the second embodiment sets the d-axis current command value Id* and the q-axis current command value Iq*, similarly to the first embodiment. Furthermore, the d-axis current command value Id* and the q-axis current command value Iq* are values ​​in the first dq-axis coordinate system.

[0240] Furthermore, the current coordinate conversion unit 211 obtains the d-axis current command value Id* and the q-axis current command value Iq* and converts them into the second dq-axis coordinate system. Specifically, the conversion is performed as shown in the following equations (29) and (30). Furthermore, in the second dq-axis coordinate system, Id1'*≠Id2'* and Iq1'*≠Iq2'*, so they are calculated separately for the first stator winding 32a and the second stator winding 32b.

[0241] [Number 12]

[0242]

[0243]

[0244] Furthermore, "Id1*" is the d-axis current command value of the first stator winding 32a in the first dq-axis coordinate system, and "Iq1*" is the q-axis current command value of the first stator winding 32a in the first dq-axis coordinate system. "Id2*" is the d-axis current command value of the second stator winding 32b in the first dq-axis coordinate system, and "Iq2*" is the q-axis current command value of the second stator winding 32b in the first dq-axis coordinate system. "Id1'*" is the d-axis current command value of the first stator winding 32a in the second dq-axis coordinate system, and "Iq1'*" is the q-axis current command value of the first stator winding 32a in the second dq-axis coordinate system. "Id2*'" is the d-axis current command value of the second stator winding 32b in the second dq-axis coordinate system, and "Iq2*'" is the q-axis current command value of the second stator winding 32b in the second dq-axis coordinate system. Furthermore, "β" is the current phase difference as described above, and is "20°" in the first embodiment. "δv" is the voltage phase difference.

[0245] The d-axis current feedback control unit 203 applies a PI (Proportional-Integral) gain to the deviations between the d-axis currents Id1', Id2' and the d-axis current command values ​​Id1'*, Id2'*, as manipulated variables for feedback control of the d-axis currents Id1', Id2' toward the d-axis current command values ​​Id1'*, Id2'*. This calculates corrected command values, namely, d-axis command voltages Vd1', Vd2'. "Vd1'" and "Vd2'" are the d-axis command voltages (d-axis voltages) in the second dq-axis coordinate system, respectively.

[0246] In the second embodiment, Id1'*≠Id2'*. Therefore, unlike the first embodiment, the d-axis current of the first stator winding 32a and the d-axis current of the second stator winding 32b need to be controlled separately. Alternatively, the sum and difference of the currents of each system may be obtained for control.

[0247] Furthermore, q-axis current feedback control unit 204, which is executed by control device 50, applies PI gains to the deviations between q-axis currents Iq1', Iq2' and q-axis current command values ​​Iq1'*, Iq2'* as manipulated variables for feedback-controlling q-axis currents Iq1', Iq2' relative to q-axis current command values ​​Iq1'*, Iq2'*, thereby calculating corrected command values, namely, q-axis command voltages Vq1', Vq2'. "Vq1'" and "Vq2'" are the q-axis command voltages (q-axis voltages) in the second dq-axis coordinate system.

[0248] In the second embodiment, Iq1′≠Iq2′, so unlike the first embodiment, the q-axis current of the first stator winding 32a and the q-axis current of the second stator winding 32b need to be controlled separately. Alternatively, the sum and difference of the currents of each system may be obtained for control.

[0249] Based on the control device 50 The d-axis and q-axis command voltages Vd1', Vq1', Vd2', and Vq2' in the second dq-axis coordinate system are converted into the U-phase, V-phase, and W-phase command voltages. Figure 14 In, it means Furthermore, the equations for converting the U-phase voltage, the V-phase voltage, and the W-phase voltage into the d-axis voltage and the q-axis voltage in the second dq-axis coordinate system are shown in equations (31) and (32). This inverse conversion is performed to convert the d-axis and q-axis command voltages Vd1', Vq1', Vd2', and Vq2' into command voltages for phases U, V, and W. In other words, the second dq-axis coordinate system is converted to the three-phase coordinate system.

[0250] [Number 13]

[0251]

[0252]

[0253] Furthermore, “δv” is a voltage phase difference. In the second embodiment, the voltage phase difference “δv” is “−12°”.

[0254] By converting as shown in equations (31) and (32), the voltage phase difference is corrected. Therefore, in the second dq-axis coordinate system, Vd1' = Vd2' and Vq1' = Vq2'. Converting each phase voltage to the second dq-axis coordinate system indicates that each phase voltage is converted into d-axis voltage and q-axis voltage in a manner that corrects the voltage phase difference.

[0255] The operation signal generating unit 106 and the driver 107 are the same as those in the first embodiment, and their subsequent description is omitted.

[0256] Next, the flux weakening control unit 110 in the second embodiment will be described. As described above, the d-axis current feedback control unit 203 and the q-axis current feedback control unit 204 perform arithmetic processing in the second dq-axis coordinate system to calculate the q-axis voltages Vq1' and Vq2'.

[0257] Therefore, in the second embodiment, the flux-weakening control unit 110 also inputs the q-axis voltage (Vq1' or Vq2') of the second dq-axis coordinate system. Therefore, similarly to the first embodiment, the q-axis voltage (Vq1' or Vq2') and the field-weakening current ΔId (negative d-axis current) are calculated. The subsequent description is the same as that of the first embodiment. This achieves the same effects as the first embodiment.

[0258] (Third embodiment)

[0259] A part of the control process in the first embodiment may be changed. Figure 15 A third embodiment in which a part of the control process is changed will be described.

[0260] In the third embodiment, an absolute value calculator 311 is provided instead of the voltage coordinate converter 111. The absolute value calculator 311 is implemented by (the CPU of) the control device 50 executing a program stored in the ROM. Alternatively, the absolute value calculator 311 may be implemented as hardware.

[0261] The absolute value calculation unit 311 of the control device 50 receives the d-axis command voltage Vd1 and the q-axis command voltage Vq1 (the command voltages in the first dq-axis coordinate system) from the d-axis current feedback control unit 103 and the q-axis current feedback control unit 104, and calculates the absolute value Vt1 of the induced voltage in the stator winding 32 according to the following equation (33). Furthermore, the d-axis command voltage Vd2 and the q-axis command voltage Vq2 (the command voltages in the first dq-axis coordinate system) are received, and the absolute value Vt2 of the induced voltage can be calculated according to the following equation (34). The absolute values ​​Vt1 and Vt2 correspond to the terminal voltage Vt of the motor 10.

[0262] [Number 14]

[0263] Vt12 =Vd1 2 +Vq1 2 ···(33)

[0264] Vt2 2 =Vd2 2 +Vq2 2 ···(34)

[0265] Furthermore, by setting it to an absolute value, phase deviation can be ignored, resulting in Vt1 = Vt2. To this end, the flux-weakening control unit 310, serving as the control device 50, determines the field-weakening current ΔId (negative d-axis current) so that the calculated absolute value Vt1 (or Vt2) does not exceed the upper limit value Vmax. Furthermore, the field-weakening current ΔId is a value in the first dq-axis coordinate system. That is, the flux-weakening control unit 310 monitors the absolute value Vt1 (or Vt2) and determines the field-weakening current ΔId in accordance with the rotational speed ω (operating rotational speed) so that the calculated absolute value Vt1 (or Vt2) does not exceed the upper limit value Vmax.

[0266] As described above, the current command unit 101 sets the d-axis and q-axis current command values ​​based on the torque command value, the field-weakening current ΔId input from the flux-weakening control unit 110, the rotational speed ω, and other parameters. The subsequent flow is omitted as it is already described above. Furthermore, the configuration of the third embodiment achieves the same advantages as the first embodiment.

[0267] (Fourth embodiment)

[0268] The configuration of each of the first to third embodiments may be partially modified as described below. A fourth embodiment in which the configuration of each of the above embodiments is partially modified will be described.

[0269] In the above embodiment, the total phase difference is 80 degrees, but in the fourth embodiment, the total phase difference is 40 degrees. Specifically, in the fourth embodiment, the phase difference between the magnetomotive force of the coil bodies Uc, Vc, and Wc and the magnetomotive force of the coil bodies Ua, Va, and Wa is set to 40 degrees. The total phase difference between the magnetomotive force generated by the partial windings of the second stator winding 32b wound around each third tooth and the magnetomotive force generated by the partial windings of the first stator winding 32a is 40 degrees. While 40 degrees is preferred, it can be varied within a range of 32 to 48 degrees.

[0270] In this case, the configuration of the partial windings of each phase becomes Figure 16 and 17 Here, the case where the total phase difference is 40 degrees is described by taking the coil body Uc provided on the tooth T9 as an example.

[0271] like Figure 16 As shown, the coil body Uc provided on the tooth T9 is composed of the partial winding -W12 / +U22. The magnetomotive force Fw1b of the partial winding -W12 and the magnetomotive force Fu2a of the partial winding +U22 are shown in equations (10) and (3). When these are expressed in a vector diagram, they become Figure 18 Furthermore, when the magnetomotive force Fw1b of the partial winding -W12 and the magnetomotive force Fu2a of the partial winding +U22 are added together, the equation (35) is obtained.

[0272] [Number 15]

[0273] Fu3a=Fw1b+Fu2a

[0274] =N×I×sin(θ-60°)+N×I×sin(θ-20°)

[0275] =1.88×N×I×sin(θ-40°)···(35)

[0276] In formula (35), the number of turns of the partial winding -W12 and the number of turns of the partial winding +U22 are both N. As shown in formula (35), by winding the partial winding -W12 and the partial winding +U22 around the tooth T9, the magnetomotive force of the coil bodies Uc, Vc, and Wc can be realized, and the phase difference (total phase difference) between the magnetomotive force of the coil bodies Uc, Vc, and Wc and the magnetomotive force of the coil bodies Ua, Va, and Wa is 40 degrees.

[0277] Then, as shown in equation (35), the magnetomotive force is proportional to the number of turns of the partial winding. Therefore, if the number of turns of each partial winding is not set appropriately, the amplitude of the magnetomotive force will not be aligned between the coil bodies Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc.

[0278] Therefore, in the fourth embodiment, the number of turns of the coil bodies Ua, Va, Wa and the coil bodies Ub, Vb, and Wb are all the same number of turns "Na". When the number of turns of the first stator winding 32a and the number of turns of the second stator winding 32b wound around the third tooth are "Nb", the number of turns "Na" and "Nb" are set to satisfy the relationship 1.8 ≤ Na / Nb ≤ 2.0. Preferably, Na / Nb is close to 1.88. In this embodiment, the number of turns is set so that the ratio of Na:Nb is 19:10 (Na / Nb is 1.9).

[0279] Moreover, if Figure 12As shown, when the current phase difference "β" is "20°" and the magnetomotive force phase difference (total phase difference) is "40°", the voltage phase difference "δv" is "34°". Therefore, when implementing the motor control of the above embodiment, coordinate transformation is performed assuming that the current phase difference "β" is "20°" and the voltage phase difference "δv" is "34°".

[0280] As described above, the configuration of the fourth embodiment has the following effects.

[0281] The phase differences between the magnetomotive force of coil bodies Ub, Vb, and Wb relative to the magnetomotive force of coil bodies Ua, Va, and Wa, and the phase differences between the magnetomotive force of coil bodies Uc, Vc, and Wc relative to the magnetomotive force of coil bodies Ub, Vb, and Wb are set within a specified phase range including 20 degrees. Specifically, the phase difference between the magnetomotive force generated by the partial winding of the second stator winding 32b wound on the third tooth and the magnetomotive force generated by the partial winding of the first stator winding 32a wound on the third tooth is set to 40 degrees. In other words, the total phase difference is set to 40 degrees. As shown in formulas (15), (16), and (35), the 6th or 12th harmonic components of the torque can be eliminated, suppressing torque ripple.

[0282] Furthermore, the number of turns is set to satisfy the relationship 1.8 ≤ Na / Nb ≤ 2.0. In this embodiment, the number of turns is set to achieve a Na:Nb ratio of 19:10 (Na / Nb is 1.9). This ensures that the amplitudes of the magnetomotive forces of the coil bodies Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc are consistent, thus suppressing torque ripple.

[0283] The number of poles in the motor 10 is 14, and the number of slots 35 is 18. That is, the number of poles is (18±4)×m (m is an integer greater than or equal to 1), and the number of slots is 18×m. This allows for a balanced electromagnetic force around the axis, similar to the first embodiment.

[0284] (Fifth embodiment)

[0285] In the first to third embodiments, the current phase difference "β" between the first inverter circuit 51 and the second inverter circuit 52 is 20 electrical degrees, but in the fifth embodiment, it is 40 degrees. In other words, the phase difference between the magnetomotive force of the coil bodies Ub, Vb, and Wb and the magnetomotive force of the coil bodies Ua, Va, and Wa is 40 degrees.

[0286] To this end, in the fifth embodiment, in formulas (13) and (14), the first term corresponds to the component based on the coil bodies Ua, Va, and Wa, the second term corresponds to the component based on the coil bodies Uc, Vc, and Wc, and corresponds to the component based on the coil bodies Ub, Vb, and Wb.

[0287] Furthermore, in the third embodiment, "λ1" represents the phase difference between the magnetomotive force of the coil body Uc and the magnetomotive force of the coil body Ua in the U phase, represents the phase difference between the magnetomotive force of the coil body Vc and the magnetomotive force of the coil body Va in the V phase, and represents the phase difference between the magnetomotive force of the coil body Wc and the magnetomotive force of the coil body Wa in the W phase. Similarly, "λ2" represents the phase difference between the magnetomotive force of the coil body Ub and the magnetomotive force of the coil body Ua in the U phase, represents the phase difference between the magnetomotive force of the coil body Vb and the magnetomotive force of the coil body Va in the V phase, and represents the phase difference between the magnetomotive force of the coil body Wb and the magnetomotive force of the coil body Wa in the W phase. Furthermore, in equations (13) and (14), "Ta" is a constant proportional to the number of turns of the coil bodies Ua, Va, and Wa and the amplitude of the current. "Tb" is a constant proportional to the number of turns of the coil bodies Uc, Vc, and Wc and the amplitude of the current. “Tc” is a constant proportional to the number of turns of the coil bodies Ub, Vb, and Wb and the amplitude of the current.

[0288] Therefore, it can be said that as long as the phase difference between the magnetomotive force of the coil bodies Uc, Vc, and Wc relative to the magnetomotive force of the coil bodies Ua, Va, and Wa is 20 degrees, the torque ripple can be suppressed by using formulas (15) and (16).

[0289] In other words, the phase difference between the magnetomotive force of coil bodies Uc, Vc, and Wc relative to the magnetomotive force of coil bodies Ua, Va, and Wa, and the phase difference between the magnetomotive force of coil bodies Ub, Vb, and Wb relative to the magnetomotive force of coil bodies Uc, Vc, and Wc, are each 20 degrees. While the phase difference is preferably 20 degrees, it can also be within a specified phase range (e.g., a range of 15 to 25 degrees) that includes 20 degrees. In this case, the torque ripple suppression effect can also be achieved.

[0290] Therefore, in the fifth embodiment, the phase difference between the magnetomotive force generated by the partial windings of the first stator winding 32a wound around each third tooth and the magnetomotive force generated by the partial windings of the second stator winding 32b is set within a range of 72 to 88 electrical degrees. In other words, the total phase difference is set within a range of 72 to 88 electrical degrees. In the third embodiment, as in the first embodiment, the total phase difference is preferably 80 degrees.

[0291] Specifically, if Figure 19As shown, partial windings are arranged on each of teeth T1 to T18. This configuration enables the phase difference between the magnetomotive force of coils Uc, Vc, and Wc relative to that of coils Ua, Va, and Wa, and the phase difference between the magnetomotive force of coils Ub, Vb, and Wb relative to that of coils Uc, Vc, and Wc to be 20 degrees, respectively. Furthermore, as in the first embodiment, the number of turns is set so that the ratio Na:Nb is 3:2 (Na / Nb is 1.5) to align the magnetomotive force of coils Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc.

[0292] Moreover, if Figure 12 As shown, when the current phase difference "β" is "40°" and the magnetomotive force phase difference (total phase difference) is "80°", the voltage phase difference "δv" is "72°". Therefore, when implementing the motor control in the first to third embodiments, coordinate transformation is performed assuming that the current phase difference "β" is "40°" and the voltage phase difference "δv" is "72°".

[0293] With the above-described configuration, the fifth embodiment can achieve the same effects as those of the first to third embodiments.

[0294] (Sixth embodiment)

[0295] In the first through third embodiments, the current phase difference "β" between the first inverter circuit 51 and the second inverter circuit 52 is set to 20 electrical degrees. However, in the sixth embodiment, the current phase difference "β" between the inverter circuits 51 and 52 is set to 40 degrees, resulting in a total phase difference of 40 degrees. In other words, the phase difference between the magnetomotive force generated by the partial windings of the first stator winding 32a wound around each third tooth and the magnetomotive force generated by the partial windings of the second stator winding 32b is set to 40 degrees. While 40 degrees is preferred, it can be varied within a range of 32 to 48 degrees.

[0296] Specifically, if Figure 20 As shown, partial windings are arranged on each of teeth T1 to T18. This configuration enables the phase differences between the magnetomotive force of coils Uc, Vc, and Wc relative to the magnetomotive force of coils Ua, Va, and Wa, and the phase differences between the magnetomotive force of coils Ub, Vb, and Wb relative to the magnetomotive force of coils Uc, Vc, and Wc to be 20 degrees, respectively. Furthermore, for the same reasons as in the second embodiment, the number of turns is set so that the ratio Na:Nb is 19:10 (Na / Nb is 1.9) to align the magnetomotive force of coils Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc.

[0297] Moreover, if Figure 12As shown, when the current phase difference "β" is "40°" and the magnetomotive force phase difference (total phase difference) is "40°", the voltage phase difference "δv" is "26°". Therefore, when implementing the motor control in the first to third embodiments, coordinate transformation is performed assuming that the current phase difference "β" is "40°" and the voltage phase difference "δv" is "26°".

[0298] As described above, the sixth embodiment can achieve the same effects as those of the first to fourth embodiments.

[0299] (Other Embodiments)

[0300] In the above embodiment, the number of magnetic poles may be 22, the number of slots may be 18, the current phase difference β between the first inverter circuit 51 and the second inverter circuit 52 may be 20 degrees, and the total phase difference may be 80 degrees.

[0301] Moreover, if Figure 12 As shown, when the current phase difference "β" is "20°" and the magnetomotive force phase difference (total phase difference) is "80°", the voltage phase difference "δv" is "-12°". Therefore, when implementing the motor control in the first to third embodiments, coordinate transformation can be performed so that the current phase difference "β" is "20°" and the voltage phase difference "δv" is "-12°".

[0302] Figure 21 An example of the arrangement of the partial windings in this case is shown in FIG. Figure 21 As shown, the first stator winding 32a wound around the third tooth can be connected to the first stator winding 32a wound around one of the circumferentially adjacent teeth T1 to T18. For example, the partial winding -U12 of the first stator winding 32a wound around tooth T2, which is the third tooth in this example, can be connected to the partial winding +U11 of the first stator winding 32a wound around tooth T1, which is the first tooth in the circumferential direction.

[0303] Similarly, the second stator winding 32b wound around the third tooth can be connected to the second stator winding 32b wound around the other of the circumferentially adjacent teeth T1 to T18. For example, the partial winding +W21 of the second stator winding 32b wound around tooth T2, which serves as the third tooth in this example, can be connected to the partial winding -W22 of the second stator winding 32b wound around tooth T3, which serves as the second circumferentially adjacent tooth. This shortens the overlap wires connecting the slots 35 at the coil ends, facilitating connections and enabling a more compact design.

[0304] In the above embodiment, the number of magnetic poles may be 22, the number of slots may be 18, the current phase difference β between the first inverter circuit 51 and the second inverter circuit 52 may be 20 degrees, and the total phase difference may be 40 degrees. Figure 21 An example of the arrangement of the partial windings in this case is shown.

[0305] Moreover, if Figure 12 As shown, when the current phase difference "β" is "20°" and the magnetomotive force phase difference (total phase difference) is "40°", the voltage phase difference "δv" is "34°". Therefore, when implementing the motor control in the first to third embodiments, coordinate transformation can be performed so that the current phase difference "β" is "20°" and the voltage phase difference "δv" is "34°".

[0306] In the above embodiment, the number of magnetic poles may be 22, the number of slots may be 18, the current phase difference β between the first inverter circuit 51 and the second inverter circuit 52 may be 40 degrees, and the total phase difference may be 80 degrees. Figure 21 An example of the arrangement of the partial windings in this case is shown.

[0307] In this case, if Figure 21 As shown, the first stator winding 32a wound around the third tooth can be connected to the first stator winding 32a wound around one of the circumferentially adjacent teeth T1 to T18. For example, the partial winding +V11 of the first stator winding 32a wound around tooth T3, which is the third tooth in this example, can be connected to the partial winding -V12 of the first stator winding 32a wound around tooth T4, which is the first tooth in the circumferential direction.

[0308] Similarly, the second stator winding 32b wound around the third tooth can be connected to the second stator winding 32b wound around the other of the circumferentially adjacent teeth T1 to T18. For example, the partial winding +U22 of the second stator winding 32b wound around tooth T3, which is the third tooth in this example, can be connected to the partial winding -U21 of the second stator winding 32b wound around tooth T2, which is the second tooth in the circumferential direction. This shortens the overlap wires connecting the slots 35 at the coil ends, facilitating connections and enabling a more compact design.

[0309] Moreover, if Figure 12As shown, when the current phase difference "β" is "40°" and the magnetomotive force phase difference (total phase difference) is "80°", the voltage phase difference "δv" is "72°". Therefore, when implementing the motor control in the first to third embodiments, coordinate transformation can be performed so that the current phase difference "β" is "40°" and the voltage phase difference "δv" is "72°".

[0310] In the above embodiment, the number of magnetic poles may be 22, the number of slots may be 18, the current phase difference β between the first inverter circuit 51 and the second inverter circuit 52 may be 40 degrees, and the total phase difference may be 40 degrees. Figure 21 An example of the arrangement of the partial windings in this case is shown.

[0311] Moreover, if Figure 12 As shown, when the current phase difference "β" is "40°" and the magnetomotive force phase difference (total phase difference) is "40°", the voltage phase difference "δv" is "26°". Therefore, when implementing the motor control in the first to third embodiments, coordinate transformation can be performed so that the current phase difference "β" is "40°" and the voltage phase difference "δv" is "26°".

[0312] In the above embodiment, the number of magnetic poles may be 16, the number of slots may be 18, the current phase difference β between the first inverter circuit 51 and the second inverter circuit 52 may be 20 degrees, and the total phase difference may be 80 degrees. Figure 22 An example of the arrangement of the partial windings in this case is shown.

[0313] In this case, if Figure 22 As shown, the first stator winding 32a wound around the third tooth can be connected to the first stator winding 32a wound around teeth T1 to T18 that are adjacent to each other in the circumferential direction. For example, the partial winding +V11 of the first stator winding 32a wound around tooth T2, which is the third tooth in this example, can be connected to the partial winding +V12 of the first stator winding 32a wound around tooth T4, which is the first tooth that is adjacent to each other in the circumferential direction.

[0314] Similarly, the second stator winding 32b wound around the third tooth can be connected to the second stator winding 32b wound around teeth T1 to T18 that are adjacent to each other in the circumferential direction. For example, the partial winding -U21 of the second stator winding 32b wound around tooth T2, which is the third tooth in this example, can be connected to the partial winding -U24 of the second stator winding 32b wound around tooth T18, which is the second tooth that is adjacent to each other in the circumferential direction. This shortens the cross-links connecting the slots 35 at the coil ends, facilitating connections and enabling a more compact design.

[0315] Moreover, if Figure 12 As shown, when the current phase difference "β" is "20°" and the magnetomotive force phase difference (total phase difference) is "80°", the voltage phase difference "δv" is "-12°". Therefore, when implementing the motor control in the first to third embodiments, coordinate transformation can be performed so that the current phase difference "β" is "20°" and the voltage phase difference "δv" is "-12°".

[0316] In the above embodiment, the number of magnetic poles may be 16, the number of slots may be 18, the current phase difference β between the first inverter circuit 51 and the second inverter circuit 52 may be 20 degrees, and the total phase difference may be 40 degrees. Figure 22 An example of the arrangement of the partial windings in this case is shown.

[0317] In this case, if Figure 22 As shown, the first stator winding 32a wound around the third tooth can be connected to the first stator winding 32a wound around one of the circumferentially adjacent teeth T1 to T18. For example, the partial winding -U12 of the first stator winding 32a wound around tooth T2, which is the third tooth in this example, can be connected to the partial winding +U11 of the first stator winding 32a wound around tooth T1, which is the first tooth in the circumferential direction.

[0318] Similarly, the second stator winding 32b wound around the third tooth can be connected to the second stator winding 32b wound around the other of the circumferentially adjacent teeth T1 to T18. For example, the partial winding +V21 of the second stator winding 32b wound around tooth T2, which serves as the third tooth in this example, can be connected to the partial winding -V22 of the second stator winding 32b wound around tooth T3, which serves as the second circumferentially adjacent tooth. This shortens the overlap wires connecting the slots 35 at the coil ends, facilitating connections and enabling a more compact design.

[0319] Moreover, if Figure 12 As shown, when the current phase difference "β" is "20°" and the magnetomotive force phase difference (total phase difference) is "40°", the voltage phase difference "δv" is "34°". Therefore, when implementing the motor control in the first to third embodiments, coordinate transformation can be performed so that the current phase difference "β" is "20°" and the voltage phase difference "δv" is "34°".

[0320] In the above embodiment, the number of magnetic poles may be 16, the number of slots may be 18, the current phase difference β between the first inverter circuit 51 and the second inverter circuit 52 may be 40 degrees, and the total phase difference may be 80 degrees. Figure 22 An example of the arrangement of the partial windings in this case is shown.

[0321] In this case, if Figure 22 As shown, the first stator winding 32a wound around the third tooth can be connected to the first stator winding 32a wound around teeth T1 to T18 that are adjacent to each other in the circumferential direction. For example, the partial winding +U12 of the first stator winding 32a wound around tooth T3, which is the third tooth in this example, can be connected to the partial winding +U11 of the first stator winding 32a wound around tooth T1, which is the first tooth that is adjacent to each other in the circumferential direction.

[0322] Similarly, the second stator winding 32b wound around the third tooth can be connected to the second stator winding 32b wound around teeth T1 to T18 that are adjacent to each other in the circumferential direction. For example, the partial winding +W21 of the second stator winding 32b wound around tooth T3, which is the third tooth in this example, can be connected to the partial winding +W22 of the second stator winding 32b wound around tooth T5, which is the second tooth that is adjacent to each other in the circumferential direction. This shortens the overlap wires connecting the slots 35 at the coil ends, facilitating connections and enabling a more compact design.

[0323] Moreover, if Figure 12 As shown, when the current phase difference "β" is "40°" and the magnetomotive force phase difference (total phase difference) is "80°", the voltage phase difference "δv" is "72°". Therefore, when implementing the motor control in the first to third embodiments, coordinate transformation can be performed so that the current phase difference "β" is "20°" and the voltage phase difference "δv" is "72°".

[0324] In the above embodiment, the number of magnetic poles may be 16, the number of slots may be 18, the current phase difference β between the first inverter circuit 51 and the second inverter circuit 52 may be 40 degrees, and the total phase difference may be 40 degrees. Figure 22 An example of the arrangement of the partial windings in this case is shown.

[0325] In this case, if Figure 22 As shown, the first stator winding 32a wound around the third tooth can be connected to the first stator winding 32a wound around one of the circumferentially adjacent teeth T1 to T18. For example, the partial winding -V11 of the first stator winding 32a wound around tooth T3, which is the third tooth in this example, can be connected to the partial winding +V12 of the first stator winding 32a wound around tooth T4, which is the first tooth in the circumferential direction.

[0326] Similarly, the second stator winding 32b wound around the third tooth can be connected to the second stator winding 32b wound around the other of the circumferentially adjacent teeth T1 to T18. For example, the partial winding -V22 of the second stator winding 32b wound around tooth T3, which is the third tooth in this example, can be connected to the partial winding -V21 of the second stator winding 32b wound around tooth T2, which is the second tooth in the circumferential direction. This shortens the overlap wires connecting the slots 35 at the coil ends, facilitating connections and enabling a more compact design.

[0327] Moreover, if Figure 12 As shown, when the current phase difference "β" is "40°" and the magnetomotive force phase difference (total phase difference) is "40°", the voltage phase difference "δv" is "26°". Therefore, when implementing the motor control in the first to third embodiments, coordinate transformation can be performed so that the current phase difference "β" is "40°" and the voltage phase difference "δv" is "26°".

[0328] In the above embodiment, the number of magnetic poles may be 20, the number of slots may be 18, the current phase difference β between the first inverter circuit 51 and the second inverter circuit 52 may be 20 degrees, and the total phase difference may be 80 degrees. Figure 23 An example of the arrangement of the partial windings in this case is shown.

[0329] In this case, if Figure 23 As shown, the first stator winding 32a wound around the third tooth can be connected to the first stator winding 32a wound around teeth T1 to T18 that are adjacent to each other in the circumferential direction. For example, the partial winding +U12 of the first stator winding 32a wound around tooth T3, which is the third tooth in this example, can be connected to the partial winding +U11 of the first stator winding 32a wound around tooth T1, which is the first tooth that is adjacent to each other in the circumferential direction.

[0330] Similarly, the second stator winding 32b wound around the third tooth can be connected to the second stator winding 32b wound around teeth T1 to T18 that are adjacent to each other in the circumferential direction. For example, the partial winding -W21 of the second stator winding 32b wound around tooth T3, which is the third tooth in this example, can be connected to the partial winding -W22 of the second stator winding 32b wound around tooth T5, which is the second tooth that is adjacent to each other in the circumferential direction. This shortens the overlap wires connecting the slots 35 at the coil ends, facilitating connections and enabling a more compact design.

[0331] Moreover, if Figure 12As shown, when the current phase difference "β" is "20°" and the magnetomotive force phase difference (total phase difference) is "80°", the voltage phase difference "δv" is "-12°". Therefore, when implementing the motor control in the first to third embodiments, coordinate transformation can be performed so that the current phase difference "β" is "20°" and the voltage phase difference "δv" is "-12°".

[0332] In the above embodiment, the number of magnetic poles may be 20, the number of slots may be 18, the current phase difference β between the first inverter circuit 51 and the second inverter circuit 52 may be 20 degrees, and the total phase difference may be 40 degrees. Figure 23 An example of the arrangement of the partial windings in this case is shown.

[0333] In this case, if Figure 23 As shown, the first stator winding 32a wound around the third tooth can be connected to the first stator winding 32a wound around one of the circumferentially adjacent teeth T1 to T18. For example, the partial winding -W11 of the first stator winding 32a wound around tooth T3, which is the third tooth in this example, can be connected to the partial winding +W12 of the first stator winding 32a wound around tooth T4, which is the first tooth in the circumferential direction.

[0334] Similarly, the second stator winding 32b wound around the third tooth can be connected to the second stator winding 32b wound around the other of the circumferentially adjacent teeth T1 to T18. For example, the partial winding +U22 of the second stator winding 32b wound around tooth T3, which is the third tooth in this example, can be connected to the partial winding -U21 of the second stator winding 32b wound around tooth T2, which is the second tooth in the circumferential direction. This shortens the overlap wires connecting the slots 35 at the coil ends, facilitating connections and enabling a more compact design.

[0335] Moreover, if Figure 12 As shown, when the current phase difference "β" is "20°" and the magnetomotive force phase difference (total phase difference) is "40°", the voltage phase difference "δv" is "34°". Therefore, when implementing the motor control in the first to third embodiments, coordinate transformation can be performed so that the current phase difference "β" is "20°" and the voltage phase difference "δv" is "34°".

[0336] In the above embodiment, the number of magnetic poles may be 20, the number of slots may be 18, the current phase difference β between the first inverter circuit 51 and the second inverter circuit 52 may be 40 degrees, and the total phase difference may be 80 degrees. Figure 23 An example of the arrangement of the partial windings in this case is shown.

[0337] In this case, if Figure 23 As shown, the first stator winding 32a wound around the third tooth can be connected to the first stator winding 32a wound around teeth T1 to T18 that are adjacent to each other in the circumferential direction. For example, the partial winding +W11 of the first stator winding 32a wound around tooth T2, which is the third tooth in this example, can be connected to the partial winding +W12 of the first stator winding 32a wound around tooth T4, which is the first tooth that is adjacent to each other in the circumferential direction.

[0338] Similarly, the second stator winding 32b wound around the third tooth can be connected to the second stator winding 32b wound around teeth T1 to T18 that are adjacent to each other in the circumferential direction. For example, the partial winding +V21 of the second stator winding 32b wound around tooth T2, which is the third tooth in this example, can be connected to the partial winding +V24 of the second stator winding 32b wound around tooth T18, which is the second tooth that is adjacent to each other in the circumferential direction. This shortens the overlap wires connecting the slots 35 at the coil ends, facilitating connections and enabling a more compact design.

[0339] Moreover, if Figure 12 As shown, when the current phase difference "β" is "40°" and the magnetomotive force phase difference (total phase difference) is "80°", the voltage phase difference "δv" is "72°". Therefore, when implementing the motor control in the first to third embodiments, coordinate transformation can be performed so that the current phase difference "β" is "40°" and the voltage phase difference "δv" is "72°".

[0340] In the above embodiment, the number of magnetic poles may be 20, the number of slots may be 18, the current phase difference β between the first inverter circuit 51 and the second inverter circuit 52 may be 40 degrees, and the total phase difference may be 40 degrees. Figure 23 An example of the arrangement of the partial windings in this case is shown.

[0341] In this case, if Figure 23 As shown, the first stator winding 32a wound around the third tooth can be connected to the first stator winding 32a wound around one of the circumferentially adjacent teeth T1 to T18. For example, the partial winding -U12 of the first stator winding 32a wound around tooth T2, which is the third tooth in this example, can be connected to the partial winding +U11 of the first stator winding 32a wound around tooth T1, which is the first tooth in the circumferential direction.

[0342] Similarly, the second stator winding 32b wound around the third tooth can be connected to the second stator winding 32b wound around the other of the circumferentially adjacent teeth T1 to T18. For example, the partial winding -U21 of the second stator winding 32b wound around tooth T2, which is the third tooth in this example, can be connected to the partial winding -U22 of the second stator winding 32b wound around tooth T3, which is the second tooth in the circumferential direction. This shortens the cross-links connecting the slots 35 at the coil ends, facilitating connections and enabling a more compact design.

[0343] Moreover, if Figure 12 As shown, when the current phase difference "β" is "40°" and the magnetomotive force phase difference (total phase difference) is "40°", the voltage phase difference "δv" is "26°". Therefore, when implementing the motor control in the first to third embodiments, coordinate transformation can be performed so that the current phase difference "β" is "40°" and the voltage phase difference "δv" is "26°".

[0344] In the above embodiment, the number of poles may be (18±4)×m (m is an integer greater than or equal to 1), and the number of slots may be 18×m. Furthermore, the number of poles may be (18±2)×n (n is an integer greater than or equal to 1), and the number of slots may be 18×n. In addition, when the number of poles is (18±4)×m (m is an integer greater than or equal to 1), and the number of slots is 18×m, as in Figure 9 As described above, since the electromagnetic force increases at every 90-degree interval, a balance can be achieved, and noise and vibration can be suppressed.

[0345] In the above embodiment, the current phase difference "β" between the first inverter circuit 51 and the second inverter circuit 52 is preferably "20 degrees" or "40 degrees", but it may be changed to the range of 15 to 25 degrees and the range of 35 to 45 degrees, respectively.

[0346] In the above embodiment, the total phase difference between the first stator winding 32a and the second stator winding 32b wound on the third tooth is preferably "40 degrees" or "80 degrees", but it can also be changed within the range of 32 to 48 degrees and 72 to 88 degrees, respectively.

[0347] In the above embodiment, the electric motor 10 is not limited to a radial gap motor, and may be, for example, an axial gap motor. Furthermore, the electric motor 10 may be a reluctance motor or an induction motor.

[0348] In the above-described embodiment and modified examples, torque ripple is suppressed by setting the total phase difference (total magnetomotive force phase difference) between the magnetomotive force generated by the partial winding of the first stator winding 32a wound around the third tooth and the magnetomotive force generated by the partial winding of the second stator winding 32b wound around the third tooth within a predetermined range. Alternatively, instead of using this total magnetomotive force phase difference, the total phase difference (total current phase difference) between the current flowing through the partial winding of the first stator winding 32a wound around the third tooth and the current flowing through the partial winding of the second stator winding 32b wound around the third tooth may be used.

[0349] Furthermore, it is important to note that the phase of the current flowing through a partial winding may deviate from 180 degrees depending on the winding direction of the partial winding. In other words, even for partial windings with the same U phase, the phase difference between the current flowing through the "+" partial winding and the current flowing through the "-" partial winding, which are deviated by 180 degrees, must be considered.

[0350] For example, when the current phase difference "β" of the inverter is 20 degrees, the partial winding of the U phase, and the phase of the current flowing to the partial winding of the "﹢" is taken as the reference phase "θ", the phase of the current flowing to the partial winding of the V phase to the partial winding of the "﹣" is "θ-120 (phase deviation caused by the V phase)-20 (deviation based on the current phase difference β)-180 (phase deviation caused by the winding direction)" = "θ-320".

[0351] The control unit and its method described in the present disclosure may also be implemented by a dedicated computer provided by a processor and a memory programmed to execute one or more functions embodied by a computer program. Alternatively, the control unit and its method described in the present disclosure may also be implemented by a dedicated computer provided by a processor composed of one or more dedicated hardware logic circuits. Alternatively, the control unit and its method described in the present disclosure may also be implemented by one or more dedicated computers composed of a combination of a processor and a memory programmed to execute one or more functions and a processor composed of one or more hardware logic circuits. Furthermore, the computer program, as an instruction executed by a computer, may also be stored in a computer-readable non-transitory tangible recording medium.

[0352] Hereinafter, characteristic configurations extracted from the above-described embodiments will be described.

[0353] [Composition 1]

[0354] A rotating electric machine (10) comprises: a rotor (40) having a plurality of magnetic poles whose polarities alternate in a circumferential direction; and a stator (30) having a stator core and a multi-phase stator winding (32), wherein the stator core has a plurality of teeth (T1 to T18) arranged at predetermined intervals in a circumferential direction, and the stator winding is wound around the teeth, wherein:

[0355] The stator winding includes a first stator winding (32a) supplied with three-phase current from a first inverter (51) and a second stator winding (32b) supplied with three-phase current from a second inverter (52).

[0356] The three-phase currents supplied from the first inverter and the three-phase currents supplied from the second inverter have a predetermined current phase difference (β).

[0357] The rotating electrical machine comprises:

[0358] a U-phase coil body Ua formed by winding the first stator winding of the U-phase among the three phases around the first tooth;

[0359] a V-phase coil body Va, wherein the V-phase coil body Va is formed by winding the first stator winding of the V-phase among the three phases around the first tooth;

[0360] a W-phase coil body Wa, wherein the W-phase coil body Wa is formed by winding the first stator winding of the W-phase among the three phases around the first tooth;

[0361] a U-phase coil body Ub formed by winding the second stator winding of the U-phase around the second tooth;

[0362] a V-phase coil body Vb formed by winding the second stator winding of the V-phase around the second tooth;

[0363] a W-phase coil body Wb formed by winding the second W-phase stator winding around a second tooth;

[0364] a U-phase coil body Uc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth;

[0365] a V-phase coil body Vc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth; and

[0366] a W-phase coil body Wc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth;

[0367] The rotating electrical machine comprises:

[0368] a current command unit (101) that determines a current command value in a first dq coordinate system that corrects the current phase difference and performs coordinate conversion from a three-phase coordinate system; and

[0369] A flux weakening control unit (110) is configured to determine a field weakening current (ΔId) in flux weakening control based on a q-axis command voltage (Vq') in a second dq coordinate system obtained by performing coordinate conversion from a three-phase coordinate system by correcting a voltage phase difference (δv) between the voltages of each phase in the first stator winding and the voltages of each phase in the second stator winding.

[0370] The current command unit determines a d-axis current command value in consideration of the field weakening current input from the flux weakening control unit.

[0371] [Composition 2]

[0372] The rotating electrical machine according to Configuration 1, further comprising:

[0373] A current conversion unit (102) acquires each phase current, performs coordinate conversion on the acquired each phase current, and acquires a detection current in a first dq coordinate system;

[0374] a command voltage determination unit (103, 104) that performs current feedback control based on the current command value and the detected current in the first dq coordinate system to determine the command voltage of the d-axis and the command voltage of the q-axis in the first dq coordinate system; and

[0375] a voltage coordinate conversion unit (111) that converts the d-axis command voltage and the q-axis command voltage in the first dq coordinate system into the d-axis command voltage and the q-axis command voltage in the second dq coordinate system;

[0376] The flux weakening control unit acquires a command voltage of a q-axis in a second dq coordinate system from the voltage coordinate conversion unit.

[0377] [Composition 3]

[0378] The rotating electrical machine according to Configuration 1, wherein:

[0379] A current conversion unit (202) acquires each phase current, performs coordinate conversion on the acquired each phase current, and acquires a detection current in a second dq coordinate system;

[0380] a current coordinate conversion unit (211) that converts a current command value of a dq axis in a first dq coordinate system into a current command value of a dq axis in a second dq coordinate system; and

[0381] a command voltage determination unit (203, 204) that performs current feedback control based on the current command value and the detected current in the second dq coordinate system to determine the command voltage of the dq axis in the second dq coordinate system;

[0382] The flux-weakening control unit acquires a q-axis voltage in a second dq coordinate system from the command voltage determination unit.

[0383] [Composition 4]

[0384] A rotating electric machine (10) comprises: a rotor (40) having a plurality of magnetic poles whose polarities alternate in a circumferential direction; and a stator (30) having a stator core and a multi-phase stator winding (32), wherein the stator core has a plurality of teeth (T1 to T18) arranged at predetermined intervals in a circumferential direction, and the stator winding is wound around the teeth, wherein:

[0385] The stator winding includes a first stator winding (32a) supplied with three-phase current from a first inverter (51) and a second stator winding (32b) supplied with three-phase current from a second inverter (52).

[0386] The three-phase currents supplied from the first inverter and the three-phase currents supplied from the second inverter have a predetermined current phase difference (β).

[0387] The rotating electrical machine comprises:

[0388] a U-phase coil body Ua formed by winding the first stator winding of the U-phase among the three phases around the first tooth;

[0389] a V-phase coil body Va, wherein the V-phase coil body Va is formed by winding the first stator winding of the V-phase among the three phases around the first tooth;

[0390] a W-phase coil body Wa, wherein the W-phase coil body Wa is formed by winding the first stator winding of the W-phase among the three phases around the first tooth;

[0391] a U-phase coil body Ub formed by winding the second stator winding of the U-phase around the second tooth;

[0392] a V-phase coil body Vb formed by winding the second stator winding of the V-phase around the second tooth;

[0393] a W-phase coil body Wb formed by winding the second W-phase stator winding around a second tooth;

[0394] a U-phase coil body Uc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth;

[0395] a V-phase coil body Vc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth; and

[0396] a W-phase coil body Wc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth;

[0397] The rotating electrical machine comprises:

[0398] A current command unit (101) determines a current command value in a first dq coordinate system that corrects the current phase difference and performs coordinate conversion from a three-phase coordinate system;

[0399] an absolute value calculation unit (311) for calculating the absolute value of the induced voltage of the stator winding based on the square sum of the d-axis command voltage (Vd) and the q-axis command voltage (Vq) in the first dq coordinate system; and

[0400] a flux weakening control unit (310) for determining a field weakening current (ΔId) in flux weakening control based on the absolute value;

[0401] The current command unit determines a current command value of a d-axis current in consideration of the field weakening current input from the flux weakening control unit.

[0402] [Composition 5]

[0403] The rotating electrical machine according to any one of configurations 1 to 4, wherein the total phase difference between the magnetomotive force generated by the partial winding of the first stator winding wound around the third tooth and the magnetomotive force generated by the partial winding of the second stator winding wound around the third tooth, or the total phase difference between the current flowing through the partial winding of the first stator winding wound around the third tooth and the current flowing through the partial winding of the second stator winding wound around the third tooth, is set as follows:

[0404] The phase differences between the magnetomotive force of the coil bodies Uc, Vc, and Wc of each phase relative to the magnetomotive force of the coil bodies Ua, Va, and Wa of each phase, and the phase differences between the magnetomotive force of the coil bodies Ub, Vb, and Wb of each phase relative to the magnetomotive force of the coil bodies Uc, Vc, and Wc of each phase, are within a specified phase range including an electrical angle of 20 degrees.

[0405] Alternatively, the phase differences between the magnetomotive force of the coil bodies Ub, Vb, and Wb of each phase relative to the magnetomotive force of the coil bodies Ua, Va, and Wa of each phase, and the phase differences between the magnetomotive force of the coil bodies Uc, Vc, and Wc of each phase relative to the magnetomotive force of the coil bodies Ub, Vb, and Wb of each phase, are within a specified phase range including an electrical angle of 20 degrees.

[0406] [Composition 6]

[0407] A rotating electric machine as described in configuration 5, wherein the number of turns of the first stator winding wound on the third tooth and the number of turns of the second stator winding wound on the third tooth are different from the number of turns of the first stator winding wound on the first tooth or the number of turns of the second stator winding wound on the second tooth in such a manner that the magnetomotive force of the coil bodies Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, and Wc of each phase is within a prescribed amplitude range.

[0408] [Composition 7]

[0409] A control program is implemented by a control device (50) of a rotating electrical machine (10), the rotating electrical machine comprising: a rotor (40) having a plurality of magnetic poles whose polarities alternate in a circumferential direction; and a stator (30) having a stator core and a multi-phase stator winding (32), the stator core having a plurality of teeth (T1 to T18) arranged at predetermined intervals in a circumferential direction, the teeth being wound around the stator winding, wherein:

[0410] The stator winding includes a first stator winding (32a) supplied with three-phase current from a first inverter (51) and a second stator winding (32b) supplied with three-phase current from a second inverter (52).

[0411] The three-phase currents supplied from the first inverter and the three-phase currents supplied from the second inverter have a predetermined current phase difference (β).

[0412] The rotating electrical machine comprises:

[0413] a U-phase coil body Ua formed by winding the first stator winding of the U-phase among the three phases around the first tooth;

[0414] a V-phase coil body Va, wherein the V-phase coil body Va is formed by winding the first stator winding of the V-phase among the three phases around the first tooth;

[0415] a W-phase coil body Wa, wherein the W-phase coil body Wa is formed by winding the first stator winding of the W-phase among the three phases around the first tooth;

[0416] a U-phase coil body Ub formed by winding the second stator winding of the U-phase around the second tooth;

[0417] a V-phase coil body Vb formed by winding the second stator winding of the V-phase around the second tooth;

[0418] a W-phase coil body Wb formed by winding the second W-phase stator winding around a second tooth;

[0419] a U-phase coil body Uc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth;

[0420] a V-phase coil body Vc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth; and

[0421] a W-phase coil body Wc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth;

[0422] The control device is caused to implement:

[0423] Current command processing (101) that determines a current command value in a first dq coordinate system that corrects the current phase difference and performs coordinate conversion from a three-phase coordinate system; and

[0424] A flux weakening control process (110) is performed to correct a voltage phase difference (δv) between the voltage of each phase in the first stator winding and the voltage of each phase in the second stator winding, and to determine a field weakening current (ΔId) in the flux weakening control based on a q-axis command voltage (Vq') in a second dq coordinate system converted from a three-phase coordinate system.

[0425] The current command unit determines a d-axis current command value in consideration of the field weakening current input from the flux weakening control unit.

[0426] [Composition 8]

[0427] A control program is implemented by a control device (50) of a rotating electrical machine (10), the rotating electrical machine comprising: a rotor (40) having a plurality of magnetic poles whose polarities alternate in a circumferential direction; and a stator (30) having a stator core and a multi-phase stator winding (32), the stator core having a plurality of teeth (T1 to T18) arranged at predetermined intervals in a circumferential direction, the teeth being wound around the stator winding, wherein:

[0428] The stator winding includes a first stator winding (32a) supplied with three-phase current from a first inverter (51) and a second stator winding (32b) supplied with three-phase current from a second inverter (52).

[0429] The three-phase currents supplied from the first inverter and the three-phase currents supplied from the second inverter have a predetermined current phase difference (β).

[0430] The control device comprises:

[0431] a U-phase coil body Ua formed by winding the first stator winding of the U-phase among the three phases around the first tooth;

[0432] a V-phase coil body Va, wherein the V-phase coil body Va is formed by winding the first stator winding of the V-phase among the three phases around the first tooth;

[0433] a W-phase coil body Wa, wherein the W-phase coil body Wa is formed by winding the first stator winding of the W-phase among the three phases around the first tooth;

[0434] a U-phase coil body Ub formed by winding the second stator winding of the U-phase around the second tooth;

[0435] a V-phase coil body Vb formed by winding the second stator winding of the V-phase around the second tooth;

[0436] a W-phase coil body Wb formed by winding the second W-phase stator winding around a second tooth;

[0437] a U-phase coil body Uc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth;

[0438] a V-phase coil body Vc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth; and

[0439] a W-phase coil body Wc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth;

[0440] The control device is caused to implement:

[0441] Current command processing (101), which determines the current command value in the first dq coordinate system by correcting the current phase difference and performing coordinate conversion from the three-phase coordinate system;

[0442] an absolute value calculation process (311) for calculating the absolute value of the induced voltage based on the square sum of the d-axis voltage (Vd) and the q-axis voltage (Vq) in the first dq coordinate system; and

[0443] a flux weakening control process (310) for determining a field weakening current (ΔId) in the flux weakening control based on the absolute value;

[0444] In the current command process, a current command value of the d-axis current is determined in consideration of the field weakening current determined in the flux weakening control process.

[0445] [Composition 9]

[0446] The rotating electric machine according to any one of Configurations 1 to 5, wherein the total phase difference is set within a range of 72 to 88 electrical angle degrees.

[0447] [Composition 10]

[0448] According to the rotating electrical machine according to Configuration 9, the number of magnetic poles of the rotor is (18±4)×m (m is an integer greater than or equal to 1), and the number of slots between the teeth is 18×m.

[0449] [Composition 11]

[0450] According to the rotating electrical machine according to Configuration 9, the number of magnetic poles of the rotor is (18±2)×n (n is an integer greater than or equal to 1), and the number of slots between the teeth is 18×n.

[0451] [Composition 12]

[0452] The rotating electrical machine according to any one of configurations 1 to 5, wherein the number of magnetic poles of the rotor is 14 or 22, the number of slots between the teeth is 18, and the total phase difference is 80 electrical degrees.

[0453] [Composition 13]

[0454] The rotating electrical machine according to any one of configurations 1 to 5, wherein the number of magnetic poles of the rotor is 16 or 20, the number of slots between the teeth is 18, and the total phase difference is 80 electrical degrees.

[0455] [Composition 14]

[0456] A rotating electric machine according to any one of structures 9 to 13, wherein, when the number of turns of the first stator winding wound on the first tooth and the number of turns of the second stator winding wound on the second tooth are respectively "Na", and the number of turns of the first stator winding wound on the third tooth and the number of turns of the second stator winding wound on the third tooth are respectively "Nb", each number of turns is set in a manner that satisfies the relationship 1.4≦Na / Nb≦1.6.

[0457] [Composition 15]

[0458] The rotating electric machine according to any one of Configurations 1 to 5, wherein the total phase difference is set within a range of 32 to 48 electrical angle degrees.

[0459] [Composition 16]

[0460] According to the rotating electrical machine of Configuration 15, the number of magnetic poles of the rotor is (18±4)×m (m is an integer equal to or greater than 1), and the number of slots between the teeth is 18×m.

[0461] [Composition 17]

[0462] According to the rotating electrical machine of Configuration 15, the number of magnetic poles of the rotor is (18±2)×n (n is an integer greater than or equal to 1), and the number of slots between the teeth is 18×n.

[0463] [Composition 18]

[0464] The rotating electrical machine according to any one of configurations 1 to 5, wherein the number of magnetic poles of the rotor is 16 or 20, the number of slots between the teeth is 18, and the total phase difference is 40 electrical degrees.

[0465] [Composition 19]

[0466] A rotating electric machine according to any one of structures 15 to 18, wherein, when the number of turns of the first stator winding wound on the first tooth and the number of turns of the second stator winding wound on the second tooth are respectively "Na", and the number of turns of the first stator winding wound on the third tooth and the number of turns of the second stator winding wound on the third tooth are respectively "Nb", each number of turns is set in a manner that satisfies the relationship 1.8≦Na / Nb≦2.0.

[0467] [Composition 20]

[0468] According to any one of configurations 1 to 5 and 9 to 19, the current phase difference between the three-phase current supplied from the first inverter and the three-phase current supplied from the second inverter is set within a range of 15 to 25 degrees or a range of 35 to 45 degrees.

[0469] [Composition 21]

[0470] The rotating electrical machine according to any one of configurations 1 to 5 and 9 to 20, wherein an angle sensor (12) is provided on a rotating shaft (11) of the rotating electrical machine,

[0471] Lead wires (A1, B1, C1) of the first stator winding connected to the first inverter and lead wires (A2, B2, C2) of the second stator winding connected to the second inverter are arranged symmetrically around the rotation axis.

[0472] While the present disclosure is described with reference to exemplary embodiments, it should be understood that the present disclosure is not limited to such exemplary embodiments or configurations. Various modifications and variations within the scope of equivalents are encompassed by the present disclosure. Furthermore, various combinations and configurations, including combinations and configurations of only one element, or combinations and configurations of elements above or below such elements, are also encompassed within the scope and spirit of the present disclosure.

Claims

1. A rotating electric machine (10), comprising: a rotor (40) having a plurality of magnetic poles whose polarities alternate in a circumferential direction; and a stator (30) having a stator core and a multi-phase stator winding (32), wherein the stator core has a plurality of teeth (T1 to T18) arranged at predetermined intervals in a circumferential direction, the stator winding being wound around the teeth, characterized in that: The stator winding includes a first stator winding (32a) supplied with three-phase current from a first inverter (51) and a second stator winding (32b) supplied with three-phase current from a second inverter (52). The three-phase currents supplied from the first inverter and the three-phase currents supplied from the second inverter have a predetermined current phase difference (β). The rotating electrical machine comprises: a U-phase coil body Ua formed by winding the first stator winding of the U-phase among the three phases around the first tooth; a V-phase coil body Va, wherein the V-phase coil body Va is formed by winding the first stator winding of the V-phase among the three phases around the first tooth; a W-phase coil body Wa, wherein the W-phase coil body Wa is formed by winding the first stator winding of the W-phase among the three phases around the first tooth; a U-phase coil body Ub formed by winding the second stator winding of the U-phase around the second tooth; a V-phase coil body Vb formed by winding the second stator winding of the V-phase around the second tooth; a W-phase coil body Wb formed by winding the second W-phase stator winding around a second tooth; a U-phase coil body Uc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth; a V-phase coil body Vc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth; as well as a W-phase coil body Wc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth; The rotating electrical machine comprises: A current command unit (101) determines a current command value in a first dq coordinate system that corrects the current phase difference and performs coordinate conversion from a three-phase coordinate system; as well as A flux weakening control unit (110) determines a field weakening current (ΔId) in flux weakening control based on a q-axis command voltage (Vq') in a second dq coordinate system obtained by correcting a voltage phase difference (δv) between a voltage of each phase in the first stator winding and a voltage of each phase in the second stator winding and performing coordinate conversion from a three-phase coordinate system. The current command unit determines a d-axis current command value in consideration of the field weakening current input from the flux weakening control unit.

2. The rotating electrical machine according to claim 1, wherein have: A current conversion unit (102) acquires each phase current, performs coordinate conversion on the acquired each phase current, and acquires a detection current in a first dq coordinate system; a command voltage determination unit (103, 104) that performs current feedback control based on the current command value and the detected current in the first dq coordinate system to determine the command voltage of the d-axis and the command voltage of the q-axis in the first dq coordinate system; as well as a voltage coordinate conversion unit (111) that converts the d-axis command voltage and the q-axis command voltage in the first dq coordinate system into the d-axis command voltage and the q-axis command voltage in the second dq coordinate system; The flux weakening control unit acquires a command voltage of a q-axis in a second dq coordinate system from the voltage coordinate conversion unit.

3. The rotating electrical machine according to claim 1, wherein A current conversion unit (202) acquires each phase current, performs coordinate conversion on the acquired each phase current, and acquires a detection current in a second dq coordinate system; a current coordinate conversion unit (211) that converts a current command value of a dq axis in a first dq coordinate system into a current command value of a dq axis in a second dq coordinate system; as well as a command voltage determination unit (203, 204) that performs current feedback control based on the current command value and the detected current in the second dq coordinate system to determine the command voltage of the dq axis in the second dq coordinate system; The flux-weakening control unit acquires a q-axis voltage in a second dq coordinate system from the command voltage determination unit.

4. A rotating electric machine (10), comprising: a rotor (40) having a plurality of magnetic poles whose polarities alternate in a circumferential direction; and a stator (30) having a stator core and a multi-phase stator winding (32), wherein the stator core has a plurality of teeth (T1 to T18) arranged at predetermined intervals in a circumferential direction, the stator winding being wound around the teeth, characterized in that: The stator winding includes a first stator winding (32a) supplied with three-phase current from a first inverter (51) and a second stator winding (32b) supplied with three-phase current from a second inverter (52). The three-phase currents supplied from the first inverter and the three-phase currents supplied from the second inverter have a predetermined current phase difference (β). The rotating electrical machine comprises: a U-phase coil body Ua formed by winding the first stator winding of the U-phase among the three phases around the first tooth; a V-phase coil body Va, wherein the V-phase coil body Va is formed by winding the first stator winding of the V-phase among the three phases around the first tooth; a W-phase coil body Wa, wherein the W-phase coil body Wa is formed by winding the first stator winding of the W-phase among the three phases around the first tooth; a U-phase coil body Ub formed by winding the second stator winding of the U-phase around the second tooth; a V-phase coil body Vb formed by winding the second stator winding of the V-phase around the second tooth; a W-phase coil body Wb formed by winding the second W-phase stator winding around a second tooth; a U-phase coil body Uc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth; a V-phase coil body Vc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth; as well as a W-phase coil body Wc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth; The rotating electrical machine comprises: A current command unit (101) determines a current command value in a first dq coordinate system that corrects the current phase difference and performs coordinate conversion from a three-phase coordinate system; an absolute value calculation unit (311) for calculating the absolute value of the induced voltage of the stator winding based on the square sum of the d-axis command voltage (Vd) and the q-axis command voltage (Vq) in the first dq coordinate system; and a flux weakening control unit (310) for determining a field weakening current (ΔId) in flux weakening control based on the absolute value; The current command unit determines a current command value of a d-axis current in consideration of the field weakening current input from the flux weakening control unit.

5. The rotating electrical machine according to any one of claims 1 to 4, characterized in that: The total phase difference between the magnetomotive force generated by the partial winding of the first stator winding wound around the third tooth and the magnetomotive force generated by the partial winding of the second stator winding wound around the third tooth, or the total phase difference between the current flowing through the partial winding of the first stator winding wound around the third tooth and the current flowing through the partial winding of the second stator winding wound around the third tooth, is set as follows: The phase differences between the magnetomotive force of the coil bodies Uc, Vc, and Wc of each phase relative to the magnetomotive force of the coil bodies Ua, Va, and Wa of each phase, and the phase differences between the magnetomotive force of the coil bodies Ub, Vb, and Wb of each phase relative to the magnetomotive force of the coil bodies Uc, Vc, and Wc of each phase, are within a specified phase range including an electrical angle of 20 degrees. Alternatively, the phase differences between the magnetomotive force of the coil bodies Ub, Vb, and Wb of each phase relative to the magnetomotive force of the coil bodies Ua, Va, and Wa of each phase, and the phase differences between the magnetomotive force of the coil bodies Uc, Vc, and Wc of each phase relative to the magnetomotive force of the coil bodies Ub, Vb, and Wb of each phase, are within a specified phase range including an electrical angle of 20 degrees.

6. The rotating electrical machine according to claim 5, wherein: In such a way that the magnetomotive force of the coil bodies Ua, Va, Wa, Ub, Vb, Wb, Uc, Vc, Wc of each phase is within a specified amplitude range, the number of turns of the first stator winding wound on the third tooth and the number of turns of the second stator winding wound on the second tooth are different from the number of turns of the first stator winding wound on the first tooth or the number of turns of the second stator winding wound on the second tooth.

7. A control program for executing by a control device (50) of a rotating electrical machine (10), the rotating electrical machine comprising: a rotor (40) having a plurality of magnetic poles whose polarities alternate in a circumferential direction; and a stator (30) having a stator core and a multi-phase stator winding (32), the stator core having a plurality of teeth (T1 to T18) arranged at predetermined intervals in a circumferential direction, the teeth being wound around the stator winding, characterized in that: The stator winding includes a first stator winding (32a) supplied with three-phase current from a first inverter (51) and a second stator winding (32b) supplied with three-phase current from a second inverter (52). The three-phase currents supplied from the first inverter and the three-phase currents supplied from the second inverter have a predetermined current phase difference (β). The rotating electrical machine comprises: a U-phase coil body Ua formed by winding the first stator winding of the U-phase among the three phases around the first tooth; a V-phase coil body Va, wherein the V-phase coil body Va is formed by winding the first stator winding of the V-phase among the three phases around the first tooth; a W-phase coil body Wa, wherein the W-phase coil body Wa is formed by winding the first stator winding of the W-phase among the three phases around the first tooth; a U-phase coil body Ub formed by winding the second stator winding of the U-phase around the second tooth; a V-phase coil body Vb formed by winding the second stator winding of the V-phase around the second tooth; a W-phase coil body Wb formed by winding the second W-phase stator winding around a second tooth; a U-phase coil body Uc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth; a V-phase coil body Vc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth; as well as a W-phase coil body Wc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth; The control device is caused to implement: Current command processing (101), which determines the current command value in the first dq coordinate system by correcting the current phase difference and performing coordinate conversion from the three-phase coordinate system; as well as A flux weakening control process (110) is performed to determine a field weakening current (ΔId) in the flux weakening control based on a q-axis command voltage (Vq') in a second dq coordinate system obtained by correcting a voltage phase difference (δv) between the voltages of each phase in the first stator winding and the voltages of each phase in the second stator winding and performing coordinate conversion from a three-phase coordinate system. In the current command processing, a d-axis current command value is determined in consideration of the field weakening current input from the flux weakening control unit.

8. A control program for execution by a control device (50) of a rotating electrical machine (10), the rotating electrical machine comprising: a rotor (40) having a plurality of magnetic poles whose polarities alternate in a circumferential direction; and a stator (30) having a stator core and a multi-phase stator winding (32), the stator core having a plurality of teeth (T1 to T18) arranged at predetermined intervals in a circumferential direction, the teeth being wound around the stator winding, characterized in that: The stator winding includes a first stator winding (32a) supplied with three-phase current from a first inverter (51) and a second stator winding (32b) supplied with three-phase current from a second inverter (52). The three-phase currents supplied from the first inverter and the three-phase currents supplied from the second inverter have a predetermined current phase difference (β). The control device comprises: a U-phase coil body Ua formed by winding the first stator winding of the U-phase among the three phases around the first tooth; a V-phase coil body Va, wherein the V-phase coil body Va is formed by winding the first stator winding of the V-phase among the three phases around the first tooth; a W-phase coil body Wa, wherein the W-phase coil body Wa is formed by winding the first stator winding of the W-phase among the three phases around the first tooth; a U-phase coil body Ub formed by winding the second stator winding of the U-phase around the second tooth; a V-phase coil body Vb formed by winding the second stator winding of the V-phase around the second tooth; a W-phase coil body Wb formed by winding the second W-phase stator winding around a second tooth; a U-phase coil body Uc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth; a V-phase coil body Vc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth; as well as a W-phase coil body Wc formed by winding the first stator winding of any one of the three phases and the second stator winding of any one of the three phases around a third tooth; The control device is caused to implement: Current command processing (101), which determines the current command value in the first dq coordinate system by correcting the current phase difference and performing coordinate conversion from the three-phase coordinate system; an absolute value calculation process (311) for calculating the absolute value of the induced voltage based on the square sum of the d-axis voltage (Vd) and the q-axis voltage (Vq) in the first dq coordinate system; and a flux weakening control process (310) for determining a field weakening current (ΔId) in the flux weakening control based on the absolute value; In the current command process, a current command value of the d-axis current is determined in consideration of the field weakening current determined in the flux weakening control process.

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