Rotating electrical machine control device and program

Abstract

To provide a rotating electrical machine control device and a program with which it is possible to grasp a field current in a system not equipped with a brush.SOLUTION: A control device 30 is applied to a system equipped with a rotating electrical machine and an inverter electrically connected to a stator winding of the rotating electrical machine. The rotating electrical machine is configured such that a voltage is induced to the field winding of a rotor by a high frequency current flowing in the stator winding. The control device comprises: a switch control unit for exercising switching control of the inverter so that a composite current of the high frequency current and a fundamental wave current of a lower frequency than the high frequency current is flowed to the stator winding; an induced voltage calculation unit 113 for calculating an induced voltage EMF generated to the stator winding during rotation of the rotor while switching control by the switch control unit is underway; and a field current calculation unit 115 for calculating a field current on the basis of the calculated induced voltage EMF.SELECTED DRAWING: Figure 7

Description

[Technical field]

[0001] The present disclosure relates to a control device and a program for a rotating electric machine. [Background technology]

[0002] Conventionally, a system including a rotating electric machine having a stator including a stator winding and an inverter electrically connected to the stator winding is known. The rotating electric machine has a rotor including a field winding. In order to pass a field current through the field winding, the system includes a field current supply circuit electrically connected to the field winding. Such a system is described in, for example, Patent Document 1. [Prior art documents] [Patent documents]

[0003] [Patent Document 1] JP 2019-71733 A Summary of the Invention [Problem to be solved by the invention]

[0004] For example, to protect the rotor from overheating or to grasp the magnetic flux generated by the rotor, it is necessary to detect the field current. For this purpose, the system is provided with a field current sensor that detects the current flowing in the field current circuit. However, in such a configuration, brushes are required to electrically connect the field current circuit and the field winding. In order to simplify the system configuration, a system that does not include brushes is desirable. There is a demand for technology that can grasp the field current even in such a system.

[0005] A primary object of the present disclosure is to provide a control device and program for a rotating electric machine that is capable of grasping a field current in a system that is not equipped with brushes. [Means for solving the problem]

[0006] The present disclosure provides a rotating electric machine having a stator including a stator winding and a rotor including a field winding, an inverter electrically connected to the stator winding; A control device for a rotating electric machine applied to a system including: The rotating electric machine is configured such that a high-frequency current flows through the stator winding to induce a voltage in the field winding, thereby causing a field current to flow, a switch control unit that performs switching control of the inverter so that a composite current of the high-frequency current and a fundamental current having a frequency lower than that of the high-frequency current flows through the stator winding; an induced voltage calculation unit that calculates an induced voltage generated in the stator winding while the switching control unit performs switching control and the rotor is rotating; a field current calculation unit that calculates a field current flowing through the field winding based on the calculated induced voltage; Equipped with.

[0007] The rotating electric machine of the present disclosure is configured such that a high-frequency current flows through the stator winding, which induces a voltage in the field winding, causing a field current to flow. Also, a switch control unit controls switching of the inverter so that a high-frequency current having a higher frequency than the fundamental current flows through the stator winding, in addition to a fundamental current intended to generate torque in the rotating electric machine. This makes it possible to pass a field current through the field winding without providing a field current circuit and brushes that electrically connect the field current circuit and the field winding.

[0008] When the switch control unit performs switching control, the rotor rotates and an induced voltage is generated in the stator winding. The induced voltage is correlated with the flux linkage of the field winding, and the flux linkage of the field winding is correlated with the field current.

[0009] In view of this, the present disclosure includes an induced voltage calculation unit that calculates an induced voltage generated in a stator winding while a rotor is rotating, in which switching control is performed by a switch control unit, and a field current calculation unit that calculates a field current based on the calculated induced voltage, thereby making it possible to grasp the field current without providing a field current sensor that detects the field current. [Brief description of the drawings]

[0010] [Figure 1] 1 is an overall configuration diagram of a control system for a rotating electric machine according to a first embodiment; [Diagram 2] FIG. 2 is a diagram showing an inverter and its peripheral configuration. [Diagram 3] FIG. [Figure 4] FIG. 4 is a diagram showing an electric circuit provided in the rotor. [Diagram 5] FIG. 4 is a block diagram of a torque control process of the control device. [Figure 6] 1 is a diagram showing a fundamental wave current and a high frequency current (harmonic current). [Figure 7] FIG. 4 is a block diagram of a field current calculation process and a fail-safe process of the control device. [Figure 8] 5 is a flowchart showing a procedure for a field current calculation process. [Figure 9] 10 is a flowchart showing a procedure of a field current calculation process according to a second embodiment. [Figure 10] FIG. 13 is a block diagram of a field current calculation process and a fail-safe process according to a third embodiment. [Figure 11] 5 is a flowchart showing a procedure for a field current calculation process. [Figure 12] FIG. 13 is a block diagram of a field current calculation process and a fail-safe process according to a fourth embodiment. [Figure 13] FIG. 13 is a block diagram of a field current calculation process and a fail-safe process according to a fifth embodiment. [Figure 14] FIG. 13 is a block diagram of a gain adjustment process according to the sixth embodiment. [Figure 15] FIG. 4 is a graph showing the relationship between the amplitude and gain of a d-axis high-frequency current. [Figure 16] FIG. 23 is a block diagram of a gain adjustment process according to the seventh embodiment. [Figure 17] FIG. 4 is a diagram showing the relationship between the amplitude and gain of a fundamental wave current. [Figure 18] FIG. 23 is a diagram showing a modification of the amplitude of the d-axis high-frequency current according to the eighth embodiment. [Figure 19] FIG. 23 is a diagram showing a modification of the amplitude of the d-axis high-frequency current according to the ninth embodiment. DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

[0011] Several embodiments will be described with reference to the drawings. In several embodiments, functionally and / or structurally corresponding and / or associated parts may be given the same reference numerals or reference numerals with different digits of 100 or more. For corresponding and / or associated parts, the description of other embodiments may be referred to.

[0012] First Embodiment A first embodiment of a rotating electric machine and a control device for the rotating electric machine according to the present disclosure will be described below with reference to the drawings. The rotating electric machine and the control device constitute a control system for the rotating electric machine, and the control system is mounted on a vehicle. The rotating electric machine is a power source for driving the vehicle.

[0013] 1, the control system includes a DC power supply 10, an inverter 20, a control device 30, and a rotating electric machine 40. The rotating electric machine 40 is a self-excited field winding type synchronous machine. For example, a mechanically and electrically integrated drive device may be configured by including the rotating electric machine 40, the inverter 20, and the control device 30, or the rotating electric machine 40, the inverter 20, and the control device 30 may each be configured by a respective component.

[0014] The rotating electric machine 40 includes a housing 41, and a stator 50 and a rotor 60 housed in the housing 41. The rotating electric machine 40 of this embodiment is an inner rotor type rotating electric machine in which the rotor 60 is disposed radially inside the stator 50.

[0015] The stator 50 includes a stator core 51 and a stator winding 52. The stator winding 52 is made of, for example, a copper wire, and includes U-, V-, and W-phase windings 52U, 52V, and 52W that are arranged offset from each other by 120° in electrical angle.

[0016] The rotor 60 includes a rotor core 61 and a field winding 70. The field winding 70 is made of, for example, aluminum wire, copper wire, or CNT (carbon nanotube). A rotating shaft 32 is inserted through a central hole of the rotor core 61. The rotating shaft 32 is rotatably supported by the housing 41 via a bearing 42.

[0017] As shown in FIG. 2, the inverter 20 includes a series connection of U-, V-, and W-phase upper-arm switches SUp, SVp, and SWp and U-, V-, and W-phase lower-arm switches SUn, SVn, and SWn. First ends of the U-, V-, and W-phase windings 52U, 52V, and 52W are connected to the connection points of the U-, V-, and W-phase upper-arm switches SUp, SVp, and SWp and the U-, V-, and W-phase lower-arm switches SUn, SVn, and SWn. Second ends of the U-, V-, and W-phase windings 52U, 52V, and 52W are connected at the neutral point. That is, in this embodiment, the U-, V-, and W-phase windings 52U, 52V, and 52W are star-connected. In this embodiment, each of the switches SUp to SWn is an IGBT. A freewheel diode is connected in inverse parallel to each of the switches SUp to SWn.

[0018] The collectors of the U-, V-, and W-phase upper-arm switches SUp, SVp, and SWp are connected to a positive terminal of a DC power supply 10. The emitters of the U-, V-, and W-phase lower-arm switches SUn, SVn, and SWn are connected to a negative terminal of the DC power supply 10. A smoothing capacitor 11 is connected in parallel to the DC power supply 10.

[0019] Next, the stator 50 and the rotor 60 will be described with reference to FIG.

[0020] The stator 50 and the rotor 60 are both arranged coaxially (specifically, on the central axis O of rotation) with the rotating shaft 32. In the following description, the direction in which the rotating shaft 32 extends is referred to as the axial direction, the direction extending radially from the center of the rotating shaft 32 is referred to as the radial direction, and the direction extending circumferentially around the rotating shaft 32 is referred to as the circumferential direction.

[0021] The stator 50 is made of laminated steel plates made of soft magnetic material, and has an annular back yoke 51a and a plurality of teeth 51b protruding radially inward from the back yoke 51a. A plurality of slots 54 are formed between adjacent teeth 51b and aligned in the circumferential direction. The stator winding 52 is formed by accommodating the phase windings of each phase in each slot 54 in a predetermined order.

[0022] The rotor 60 is made of a soft magnetic material, for example, laminated steel plates. The rotor 60 has a cylindrical rotor core 61 and a plurality of main poles 62 protruding radially outward from the rotor core 61. In this embodiment, eight main poles 62 are provided at equal intervals in the circumferential direction.

[0023] The field winding 70 includes a first winding portion 71a and a second winding portion 71b. In each main pole portion 62, the first winding portion 71a is wound radially outward, and the second winding portion 71b is wound radially inward from the first winding portion 71a. In each main pole portion 62, the winding directions of the first winding portion 71a and the second winding portion 71b are the same. In addition, among the main pole portions 62 adjacent in the circumferential direction, the winding directions of the winding portions 71a and 71b wound around one of the main pole portions 62 are opposite to the winding directions of the winding portions 71a and 71b wound around the other of the main pole portions 62 adjacent in the circumferential direction. Therefore, the magnetization directions of the main pole portions 62 adjacent in the circumferential direction are opposite to each other.

[0024] Fig. 4 shows an electric circuit on the rotor 60 side including the winding portions 71a, 71b wound around a common main pole portion 62. The first winding portion 71a shown in Fig. 4 is a series connection of the first winding portions 71a wound around each main pole portion 62, and the second winding portion 71b shown in Fig. 4 is a series connection of the second winding portions 71b wound around each main pole portion 62.

[0025] The rotor 60 is provided with a diode 80 as a rectifying element and a capacitor 81. The diode 80 is electrically connected in parallel to the series connection of the first winding portion 71a and the second winding portion 71b. In detail, the cathode of the diode 80 is connected to a first end of the first winding portion 71a, and the second end of the first winding portion 71a is connected to a first end of the second winding portion 71b. The anode of the diode 80 is connected to a second end of the second winding portion 71b. The capacitor 81 is electrically connected in parallel to the second winding portion 71b. In FIG. 4, L1 indicates the inductance of the first winding portion 71a, L2 indicates the inductance of the second winding portion 71b, and C indicates the capacitance of the capacitor 81.

[0026] In this embodiment, a series resonant circuit is configured including the first winding portion 71a and the capacitor 81, and a parallel resonant circuit is configured including the second winding portion 71b and the capacitor 81. In Fig. 4, f1 indicates a first resonant frequency which is the resonant frequency of the series resonant circuit, and f2 indicates a second resonant frequency which is the resonant frequency of the parallel resonant circuit.

[0027] Alternatively, the anode of the diode 80 may be connected to the first end of the first winding portion 71a, and the cathode of the diode 80 may be connected to the second end of the second winding portion 71b.

[0028] Returning to the explanation of Fig. 2, the control system includes a current sensor 21, an angle sensor 22, and a voltage sensor 23. The current sensor 21 detects at least two phases of currents flowing through the rotating electric machine 40. The angle sensor 22 detects the rotation angle (electrical angle) of the rotor 60. In this embodiment, the voltage sensor 23 includes a sensor that detects the voltage of the DC power supply 10, and a sensor that detects the output voltage (phase voltage) of each phase of the inverter 20. The detection values ​​of the sensors 21 to 23 are input to the control device 30.

[0029] The control device 30 is an electronic control unit mainly composed of a microcomputer 31. The microcomputer 31 includes a CPU (Central Processing Unit). The functions provided by the microcomputer 31 can be provided by software recorded in a substantial memory device and a computer that executes the software, by software alone, by hardware alone, or by a combination of these. For example, when the microcomputer 31 is provided by an electronic circuit that is hardware, it can be provided by a digital circuit including a large number of logic circuits, or by an analog circuit. For example, the microcomputer 31 executes a program stored in a non-transitory tangible storage medium as a storage unit provided in the microcomputer 31. The program includes, for example, programs for processing shown in Figs. 5, 7, 8, etc., which will be described later. A method corresponding to the program is executed by executing a set of instructions that constitute the program. The storage unit is, for example, a non-volatile memory. The program stored in the storage unit can be updated via a communication network such as the Internet, for example, OTA (Over The Air), etc.

[0030] The control device 30 generates drive signals to turn on and off each of the switches SUp to SWn that constitute the inverter 20. In particular, the control device 30 generates drive signals to turn on and off each of the arm switches SUp to SWn and supplies the generated drive signals to the gates of each of the arm switches SUp to SWn in order to convert the DC power output from the DC power source 10 into AC power and supply it to the U-, V-, and W-phase windings 52U, 52V, and 52W. As a result, in each phase, the upper arm switches and the lower arm switches are alternately turned on with dead times therebetween.

[0031] The control device 30 turns on and off the switches SUp to SWn so as to pass a composite current of a fundamental current and a harmonic current (specifically, a harmonic excitation current) having a higher frequency than the fundamental current through each of the phase windings 52U, 52V, 52W. The fundamental current is a current that mainly serves to generate torque in the rotating electric machine 40. The harmonic current is a current that mainly serves to excite the field winding 70 and induce a field current in the field winding 70. The phase currents flowing through the phase windings 52U, 52V, 52W are shifted by 120° in electrical angle.

[0032] The torque control of the rotating electrical machine 40 executed by the control device 30 will be described with reference to FIG.

[0033] The two-phase conversion unit 100 converts the U-, V-, and W-phase currents in a three-phase fixed coordinate system into a d-axis current Idr and a q-axis current Iqr in a two-phase rotating coordinate system (dq coordinate system) based on the detection value of the current sensor 21 and the electrical angle θe detected by the angle sensor 22.

[0034] The command current calculation unit 101 calculates a d-axis base command current Idbref and a q-axis command current Iqref based on the command torque Tref. The d-axis base command current Idbref and the q-axis command current Iqref are command values ​​of DC components corresponding to a fundamental wave current. The command current calculation unit 101 may calculate the d-axis base command current Idbref and the q-axis command current Iqref based on, for example, map information in which the command torque Tref, the d-axis base command current Idbref, and the q-axis command current Iqref are associated with each other, and the input command torque Tref.

[0035] The excitation current calculation unit 102 calculates the d-axis high frequency command current Idhref. The d-axis high frequency command current Idhref is a command value of an AC component corresponding to a harmonic current that excites the field winding 70, and is expressed by the following equation (eq1) in this embodiment. In the following equation (eq1), Idamp is the amplitude of the d-axis high frequency command current Idhref, and fh is the fluctuation frequency of the d-axis high frequency command current Idhref.

[0036]

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[0037] The superimposing unit 103 calculates the d-axis command current Idref by adding the d-axis high-frequency command current Idhref to the d-axis basic command current Idbref.

[0038] The d-axis deviation calculation unit 104 calculates the d-axis current deviation ΔId by subtracting the d-axis current Idr from the d-axis command current Idref. The q-axis deviation calculation unit 105 calculates the q-axis current deviation ΔIq by subtracting the q-axis current Iqr from the q-axis command current Iqref.

[0039] The d-axis current control unit 106 calculates a d-axis voltage command value Vdref based on the d-axis current deviation ΔId as a manipulated variable for feedback-controlling the d-axis current Idr to the d-axis command current Idref. The q-axis current control unit 107 calculates a q-axis voltage command value Vqref based on the q-axis current deviation ΔIq as a manipulated variable for feedback-controlling the q-axis current Iqr to the q-axis command current Iqref. In this embodiment, the feedback control of each of the current control units 106 and 107 is proportional-integral control.

[0040] A three-phase conversion unit 108 converts the d- and q-axis voltage command values ​​Vdref, Vqref in the two-phase rotating coordinate system into U-, V- and W-phase voltage command values ​​VUref, VVref, and VWref in the three-phase fixed coordinate system based on the d- and q-axis voltage command values ​​Vdref, Vqref and the electrical angle θe. The U-, V- and W-phase voltage command values ​​VUref, VVref, and VWref have waveforms with phases shifted by 120 degrees in electrical angle. The frequencies of harmonic components included in the U-, V- and W-phase voltage command values ​​VUref, VVref, and VWref are set to frequencies near the first resonance frequency f1.

[0041] The signal generating unit 109 generates drive signals for the upper and lower arm switches SUp to SWn of the U, V and W phases by PWM modulation based on the U, V and W phase voltage command values ​​VUref, VVref and VWref, the power supply voltage Vdc and a carrier signal (e.g. a triangular wave signal). The generated drive signals are input to the gates of the respective switches. This executes switching control of the inverter 20. In this embodiment, the signal generating unit 109 corresponds to a "switch control unit."

[0042] As a result of switching control of inverter 20, a composite current in which harmonic currents (see solid lines in FIG. 6(b)) are superimposed on a fundamental current (see FIG. 6(a)) flows through each phase winding 52U, 52V, 52W. FIG. 6(a) shows the progression of the fundamental current over one electrical angle period. The dashed dotted line in FIG. 6(b) shows the envelope of the harmonic current. The envelope of the harmonic current has the same period as the fundamental current. The values ​​on the vertical axis in FIG. 6 indicate the relative relationship between the magnitudes of the waveforms shown in FIGS. 6(a) and (b).

[0043] A harmonic current flowing through the stator winding 52 causes a field current to flow through the field winding 70. In this embodiment, the control device 30 calculates the field current If flowing through the field winding. Hereinafter, the calculation method will be described with reference to FIG.

[0044] In the control device 30, a speed calculation unit 110 calculates an electrical angular speed ωe based on the detected electrical angle θe.

[0045] The first low-pass filter 111 calculates a filtered q-axis voltage Vqf by performing low-pass filtering on the q-axis voltage command value Vqref calculated by the q-axis current control unit 107. The second low-pass filter 112 calculates a filtered q-axis current Iqf by performing low-pass filtering on the q-axis current Iqr calculated by the two-phase conversion unit 100.

[0046] In this embodiment, the field current If is calculated based on the voltage equation of the motor in a two-phase rotating coordinate system. The voltage equations are shown in the following equations (eq2) and (eq3). In the following equations (eq2) and (eq3), R is the resistance value of the stator winding 52, Ld and Lq are d-axis and q-axis inductances, and φ is the effective value of the flux linkage of the stator winding 52. The reason for applying the low-pass filter process is to eliminate the influence of the time differential value of the q-axis current Iq in the second term on the right side of the following equation (eq3).

[0047]

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[0048]

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[0049]

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[0050] By using the q-axis voltage command value Vqref, which is a command value rather than a detected value, to calculate the induced voltage EMF, it is possible to calculate the induced voltage EMF while suppressing the effects of voltage fluctuations accompanying PWM modulation.

[0051] The flux linkage calculation unit 114 calculates the flux linkage of the field winding 70 (hereinafter, field flux linkage φf) based on the calculated induced voltage EMF and the electrical angular velocity ωe. In detail, the flux linkage calculation unit 114 calculates the field flux linkage φf based on the following equation (eq5).

[0052]

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[0053]

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[0054] The calculated field current If is input to the excitation current calculation unit 102. The excitation current calculation unit 102 adjusts the amplitude Idamp so that the excess or deficiency of the acquired field current If with respect to the field current command value corresponding to the amplitude Idamp of the d-axis high frequency command current Idhref approaches zero.

[0055] The fail-safe unit 116 performs a temperature estimation process to calculate the temperature of the rotor 60 based on the calculated field current If and the resistance value of the field winding 70. The fail-safe unit 116 performs an output suppression process. The output suppression process includes a process of outputting a command to the excitation current calculation unit 102 to reduce the amplitude Idamp when it is determined that the calculated temperature of the rotor 60 exceeds the temperature threshold value. This reduces the field current If, and suppresses heat generation in the rotor 60. The fail-safe unit 116 performs a fail-safe process. The fail-safe process includes a process of outputting a command to reduce the amplitude Idamp when it is determined that the calculated field current If exceeds the current threshold value. This allows the rotor 60 to be evacuated to a safe state when an abnormality occurs.

[0056] 8 shows a flowchart of a field current calculation process executed by the control device 30. This process is repeatedly executed at a predetermined control period, for example.

[0057] In step S10, the first low-pass filter 111 calculates the filtered q-axis voltage Vqf, the second low-pass filter 112 calculates the filtered q-axis current Iqf, the speed calculation unit 110 calculates the electrical angular velocity ωe, and the two-phase conversion unit 100 calculates the d-axis current Idr.

[0058] In step S11, the induced voltage calculation unit 113 calculates an induced voltage EMF based on the calculated filtered q-axis voltage Vqf, filtered q-axis current Iqf, electrical angular velocity ωe, and d-axis current Idr.

[0059] In step S12, the field flux linkage calculation unit 114 calculates the field flux linkage φf based on the calculated induced voltage EMF.

[0060] In step S13, the field current calculation unit 115 calculates the field current If based on the calculated field flux linkage φf.

[0061] In step S14, a process based on the calculated field current If is performed. Specifically, for example, the above-mentioned temperature estimation process is performed, and if necessary, the above-mentioned output suppression process and fail-safe process are performed.

[0062] According to the present embodiment described above in detail, in a system that does not include a field current circuit and brushes, the field current can be detected without including a field current sensor that detects the field current. This allows the number of components of the system to be reduced, and the system to be simplified.

[0063] <Modification of the first embodiment> The parameters input to the induced voltage calculation unit 113 may be the q-axis command current Iqref and the d-axis command current Idref instead of the filtered q-axis current Iqf and the d-axis current Idr. The d-axis current Idr input to the induced voltage calculation unit 113 may be the d-axis current Idr from which high-frequency components have been removed by a low-pass filter.

[0064] The induced voltage calculation unit 113 may calculate the induced voltage EMF based on the q-axis voltage command value Vqref and the q-axis current Iqr that have not been subjected to low-pass filtering, instead of the filtered q-axis voltage Vqf and the filtered q-axis current Iqf. In this case, the induced voltage calculation unit 113 may calculate the induced voltage EMF based on "EMF=Vqref-R×Iqr-Lq×d / dt(Iq)-ωe×Ld×Idr".

[0065] <Second embodiment> Hereinafter, the second embodiment will be described with reference to the drawings, focusing on the differences from the first embodiment. In this embodiment, the control device 30 performs a calculation process of the field current If on the condition that it is determined that a specific condition is satisfied.

[0066] 9 shows a flowchart of a field current calculation process executed by the control device 30. This process is repeatedly executed at a predetermined control period, for example.

[0067] After the process of step S10 is completed, in step S15, it is determined whether or not the first condition, the second condition, and the third condition are satisfied. Each condition is set to improve the calculation accuracy of the field current If.

[0068] The first condition is a condition that the calculated electrical angular velocity ωe is equal to or greater than a speed threshold ωth, and the amplitude Idamp of the d-axis high-frequency command current Idhref is equal to or greater than an amplitude threshold Ia. The first condition is a condition for calculating the field current when the generated induced voltage is large.

[0069] The second condition is a condition that (A) the magnitude of the d-axis current Idr is equal to or less than the d-axis current threshold Idth, (B) the magnitude of the q-axis current Iqr is equal to or less than the q-axis current threshold Iqth, (C) the magnitude of the d-axis basic command current Idbref is equal to or less than the d-axis command threshold Idrfth, and (D) the magnitude of the q-axis command current Iqref is equal to or less than the q-axis command threshold Iqrfth, and the magnitude of the command torque Tref is equal to or less than the torque threshold Tth. The second condition is a condition for calculating the field current when the rotating electric machine 40 operates in a region where the voltage components other than the induced voltage are small. The d-axis current Idr used in the second condition (A) may be, for example, the d-axis current Idr from which high-frequency components have been removed by a low-pass filter.

[0070] The third condition is that the fluctuation amount Δω of the electrical angular velocity ωe is equal to or smaller than a predetermined value dωth. The third condition is a condition for calculating the field current when the operation of the rotating electric machine 40 is stable. The fluctuation amount Δω is, for example, the difference between the maximum value and the minimum value of the electrical angular velocity ωe in one electrical angle period.

[0071] If it is determined in step S15 that all of the first to third conditions are met, the process proceeds to step S11.

[0072] According to the present embodiment described above, it is possible to improve the calculation accuracy of the field current If.

[0073] <Modification of the second embodiment> The specific conditions used in step S15 are not limited to all of the first to third conditions, but may be any one of the first to third conditions, or any two of the first to third conditions.

[0074] In step S15, among the second conditions, for example, conditions (C) to (E) do not have to be used.

[0075] <Third embodiment> Hereinafter, the third embodiment will be described with reference to the drawings, focusing on the differences from the first embodiment. In this embodiment, the method of calculating the field current If is changed.

[0076] FIG. 10 is a block diagram of the field current calculation process and the fail-safe process executed by the control device 30. As shown in FIG.

[0077] The primary component extraction unit 117 extracts a primary component EMF1 contained in the induced voltage EMF based on the induced voltage EMF calculated by the induced voltage calculation unit 113. The primary component EMF1 is a component of the d-axis high frequency command current Idhref at a frequency fh contained in the induced voltage EMF. The primary component extraction unit 117 may extract the primary component EMF1 by using, for example, a digital Fourier transform.

[0078] The flux linkage calculation unit 118 calculates the flux primary component φ1, which is the primary component of the flux linkage of the field winding 70, based on the extracted primary component EMF1 and the electrical angular velocity ωe. The flux primary component φ1 is a component of the frequency fh of the d-axis high frequency command current Idhref, which is included in the field flux linkage φf. The flux linkage calculation unit 118 calculates the flux primary component φ1 based on the following equation (eq7).

[0079]

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[0080]

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[0081] The field current calculation unit 119 may calculate the field current If based on map information of the field current If associated with the magnetic flux primary component φ1.

[0082] According to the method of calculating the field current If based on the primary magnetic flux component φ1, the influences of R, Ld, and Lq in the above equation (eq3) and the influences of the sixth harmonic generated due to the dead time of the inverter 20 and the magnetic circuit of the rotating motor 40 can be suppressed to calculate the field current If.

[0083] 11 shows a flowchart of a field current calculation process executed by the control device 30. This process is repeatedly executed at a predetermined control period, for example.

[0084] In step S20, the first low-pass filter 111 calculates the filtered q-axis voltage Vqf, the second low-pass filter 112 calculates the filtered q-axis current Iqf, the speed calculation unit 110 calculates the electrical angular velocity ωe, and the two-phase conversion unit 100 calculates the d-axis current Idr.

[0085] In step S21, the induced voltage calculation unit 113 calculates an induced voltage EMF based on the calculated filtered q-axis voltage Vqf, filtered q-axis current Iqf, electrical angular velocity ωe, and d-axis current Idr.

[0086] In step S22, the primary component extractor 117 extracts the primary component EMF1 based on the calculated induced voltage EMF.

[0087] In step S23, the flux linkage calculation unit 118 calculates the magnetic flux primary component φ1 based on the extracted primary component EMF1.

[0088] In step S24, the field current calculation unit 119 calculates the field current If based on the calculated magnetic flux primary component φ1.

[0089] In step S25, similar to step S14, processing based on the calculated field current If is performed.

[0090] <Modification of the third embodiment> The extraction unit 117 may extract a secondary component EMF2 included in the induced voltage EMF based on the induced voltage EMF calculated by the induced voltage calculation unit 113. The secondary component EMF2 is a component of "2×fh" of the d-axis high frequency command current Idhref included in the induced voltage EMF. The flux linkage calculation unit 118 calculates a flux secondary component φ2 based on the extracted secondary component EMF2, and the field current calculation unit 119 calculates the field current If based on the calculated flux secondary component φ2. The flux secondary component φ2 is a component of "2×fh" of the d-axis high frequency command current Idhref included in the field flux linkage φf.

[0091] <Fourth embodiment> Hereinafter, the fourth embodiment will be described with reference to the drawings, focusing on the differences from the first embodiment. In this embodiment, the method of calculating the field current If is changed.

[0092] 12 is a block diagram of the field current calculation process and the fail-safe process executed by the control device 30. In the following, an example will be described in which the parameters of the U phase are used to calculate the field current If.

[0093] The first low-pass filter 120 calculates a filtered U-phase voltage VUf by performing low-pass filtering on the U-phase voltage command value VUref calculated by the three-phase conversion unit 108. The second low-pass filter 121 calculates a filtered U-phase current IUr detected by the current sensor 21 by performing low-pass filtering.

[0094] In this embodiment, the field current If is calculated based on the following equation (eq9), which is a voltage equation in a three-phase fixed coordinate system. In the following equation (eq9), L is the self-inductance of each phase. The reason for applying the low-pass filter process is to eliminate the influence of the time differential value of the phase current in the second term on the right side of the following equation (eq9).

[0095]

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[0096]

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[0097]

number

[0098]

number

[0099] <Modification of the Fourth Embodiment> The parameter input to the first low-pass filter 120 may be the U-phase voltage VUr detected by the voltage sensor 23, instead of the U-phase voltage command value VUref.

[0100] The parameter input to the induced voltage calculation unit 122 may be a U-phase current command value calculated based on the d- and q-axis command currents Idref, Iqref and the electrical angle θe, instead of the filtered U-phase current IUf.

[0101] The control device 30 may calculate the induced voltage based on the V-phase parameters (V-phase voltage command value VVref, V-phase current IVr) or the W-phase parameters (W-phase voltage command value VWref, W-phase current IWr) instead of the U-phase parameters (U-phase voltage command value VUref, U-phase current IUr).

[0102] Considering that there is a correlation between the phase voltage and the line voltage, the control device 30 may calculate the induced voltage based on the line voltage instead of the phase voltage.

[0103] <Fifth embodiment> Hereinafter, the fifth embodiment will be described with reference to the drawings, focusing on the differences from the first embodiment. In this embodiment, the method of calculating the field current If is changed.

[0104] FIG. 13 is a block diagram of the field current calculation process and the fail-safe process executed by the control device 30. As shown in FIG.

[0105] The q-axis voltage calculation unit 130 calculates the q-axis voltage Vqr based on the U-, V-, and W-phase voltages VUr, VVr, and VWr detected by the voltage sensor 23 and the electrical angle θe. In detail, the q-axis voltage calculation unit 130 calculates the q-axis voltage Vqr based on the following equation (eq13).

[0106]

number

[0107] According to the present embodiment described above, the field current If can also be calculated.

[0108] Sixth Embodiment The sixth embodiment will be described below with reference to the drawings, focusing on the differences from the first embodiment. In this embodiment, the d, q-axis current control units 106, 107 change the feedback gain of the feedback control when the amplitude Idamp of the d-axis high-frequency command current Idhref is large, more than when the amplitude Idamp is small. This change process is performed in consideration of the fact that the inductance of the rotating electric machine 40 decreases when the amplitude Idamp is large.

[0109] 14 and 15, the d-axis current control unit 106 increases the proportional gain Kpd and the integral gain Kid in the proportional-integral control as the amplitude Idamp increases. For example, the d-axis current control unit 106 may increase the proportional gain Kpd and the integral gain Kid stepwise or continuously as the amplitude Idamp increases.

[0110] The q-axis current control unit 107 increases the proportional gain Kpq and the integral gain Kiq in the proportional-integral control as the amplitude Idamp increases. For example, the q-axis current control unit 107 may increase the proportional gain Kpq and the integral gain Kiq stepwise or continuously as the amplitude Idamp increases.

[0111] According to the present embodiment described above, even if the inductance of the rotary electric machine 40 changes due to a change in the magnitude of the current, the responsiveness of the current control can be maintained at a high level.

[0112] Seventh embodiment The seventh embodiment will be described below with reference to the drawings, focusing on the differences from the sixth embodiment. In this embodiment, the d-axis and q-axis current control units 106 and 107 use the magnitude of the d-axis basic command current Idbref and the magnitude of the q-axis command current Iqref instead of the magnitude of the amplitude Idamp of the d-axis high-frequency command current Idhref.

[0113] 16 and 17, the d-axis current control unit 106 increases the proportional gain Kpd and the integral gain Kid in the proportional-integral control as the d-axis base command current Idbref and the q-axis command current Iqref increase. The q-axis current control unit 107 increases the proportional gain Kpq and the integral gain Kiq in the proportional-integral control as the d-axis base command current Idbref and the q-axis command current Iqref increase.

[0114] According to the present embodiment described above, even if the inductance of the rotary electric machine 40 changes due to a change in the magnitude of the current, the responsiveness of the current control can be maintained at a high level.

[0115] Eighth embodiment The eighth embodiment will be described below with reference to the drawings, focusing on the differences from the first embodiment. In this embodiment, as shown in Fig. 18, when the calculated electrical angular velocity ωe is lower than the sixth-order electrical angular velocity ω6th of the rotor 60, the control device 30 (corresponding to the "change unit") sets the frequency fh of the d-axis high-frequency command current Idhref to a first specified frequency "ωa / (2π)" (e.g., 2.4 kHz) higher than the frequency "ω6th / (2π)" (e.g., 2.2 kHz) corresponding to the sixth-order electrical angular velocity ω6th. Note that "ω6th=ωe×6".

[0116] On the other hand, when the electrical angular velocity ωe is equal to or greater than the sixth electrical angular velocity ω6th, the control device 30 sets the frequency fh of the d-axis high-frequency command current Idhref to a second specified frequency "ωb / (2π)" (e.g., 2.0 kHz) that is lower than the frequency corresponding to the sixth electrical angular velocity. The frequency range from the first specified frequency to the second specified frequency is the frequency range that the frequency fh of the d-axis high-frequency command current Idhref can take.

[0117] According to the present embodiment described above, it is possible to prevent the electrical angular velocity corresponding to the frequency fh of the d-axis high-frequency command current Idhref from coinciding with the sixth-order electrical angular velocity ω6th, thereby improving the NV characteristics of the rotating electrical machine 40.

[0118] <Ninth embodiment> Hereinafter, the ninth embodiment will be described with reference to the drawings, focusing on the differences from the eighth embodiment. In this embodiment, as shown in Fig. 19, the control device 30 sets the frequency fh of the d-axis high-frequency command current Idhref to be lower as the electrical angular velocity ωe is higher.

[0119] When the electrical angular velocity ωe is 0, the control device 30 sets the frequency fh of the d-axis high-frequency command current Idhref to the above-mentioned first specified frequency "ωa / (2π)", and when the electrical angular velocity ωe is a sixth-order electrical angular velocity ω6th, the control device 30 sets the frequency fh of the d-axis high-frequency command current Idhref to a frequency corresponding to the sixth-order electrical angular velocity ω6th.

[0120] According to the present embodiment described above, it is also possible to prevent the electrical angular velocity corresponding to the frequency fh of the d-axis high-frequency command current Idhref from coinciding with the sixth-order electrical angular velocity ω6th.

[0121] <Other embodiments> Each of the above embodiments may be modified as follows.

[0122] In the eighth and ninth embodiments, for example, a second-, third-, twelfth- or eighteenth-order electrical angular velocity may be used in the processing of the control device 30 instead of the sixth-order electrical angular velocity ω6th.

[0123] The high-frequency current (specifically, high-frequency excitation current) passed through the stator winding 52 is not limited to a harmonic current whose fluctuating frequency is N times (N is an integer equal to or greater than 2) the frequency of the fundamental current, but may be a current whose fluctuating frequency is other than N times the frequency of the fundamental current as long as the fluctuating frequency is higher than the frequency of the fundamental current.

[0124] The second winding portion 71b may be disposed closer to the stator 50 in the radial direction than the first winding portion 71a.

[0125] The capacitor 81 that constitutes the resonant circuit may be electrically connected in parallel to the first winding portion 71a instead of the second winding portion 71b.

[0126] The rotating electric machine is not limited to an inner rotor type rotating electric machine, but may be an outer rotor type rotating electric machine. In this case, the main pole portion protrudes radially inward from the rotor core.

[0127] The rotating electric machine is not limited to a star-connected rotating electric machine, but may be a delta-connected rotating electric machine.

[0128] In the first embodiment, the stator core may not be provided with teeth.

[0129] The capacitor 81 does not have to be provided in the resonant circuit of the rotor 60.

[0130] The rotating electric machine is not limited to a rotating electric machine used as an in-vehicle main engine, but may be, for example, a rotating electric machine used as an ISG (Integrated Starter Generator) that serves as both a motor and a generator.

[0131] The moving body on which the control system is mounted is not limited to a vehicle, but may be, for example, an aircraft or a ship. Furthermore, the control system is not limited to a system mounted on a moving body, but may be a stationary system.

[0132] The control device and the method described in the present disclosure may be realized by a special-purpose computer provided by configuring a processor and a memory programmed to execute one or more functions embodied in a computer program. Alternatively, the control device and the method described in the present disclosure may be realized by a special-purpose computer provided by configuring a processor with one or more dedicated hardware logic circuits. Alternatively, the control device and the method described in the present disclosure may be realized by one or more special-purpose computers configured by a combination of a processor and a memory programmed to execute one or more functions and a processor configured with one or more hardware logic circuits. In addition, the computer program may be stored in a computer-readable non-transitory tangible recording medium as instructions executed by the computer.

[0133] Characteristic configurations extracted from each of the above-described embodiments will be described below. [Configuration 1] a rotating electric machine (40) having a stator (50) including a stator winding (52) and a rotor (60) including a field winding (70); an inverter (20) electrically connected to the stator winding; A control device (30) for a rotating electric machine applied to a system including: The rotating electric machine is configured such that a high-frequency current flows through the stator winding to induce a voltage in the field winding, thereby causing a field current to flow, a switch control unit (109) that performs switching control of the inverter so that a composite current of the high-frequency current and a fundamental current having a frequency lower than that of the high-frequency current flows through the stator winding; an induced voltage calculation unit (113, 122) configured to calculate an induced voltage generated in the stator winding while the rotor is rotating and switching control is performed by the switch control unit; a field current calculation unit (115, 119, 124) that calculates a field current flowing through the field winding based on the calculated induced voltage; A control device for a rotating electric machine comprising: [Configuration 2] The induced voltage calculation unit 2. The control device for a rotating electric machine according to configuration 1, wherein the induced voltage is calculated based on a current flowing through the stator winding and a voltage applied from the inverter to the stator winding. [Configuration 3] a current control unit (107) that calculates voltage command values ​​(Vqref, VUref) to be applied to the stator windings in order to control the currents flowing through the stator windings to command currents (Idref, Iqref), 3. The control device for a rotating electric machine according to configuration 2, wherein the induced voltage calculation unit uses the calculated voltage command value as a voltage to be applied to the stator winding. [Configuration 4] The system includes a current sensor (21) that detects a current flowing through the stator winding, a two-phase conversion unit (100) that converts a current of the stator winding in a three-phase fixed coordinate system of the rotating electric machine into d-axis and q-axis currents (Idr, Iqr) in a two-phase rotating coordinate system of the rotating electric machine based on a detection value of the current sensor, the current control unit is a q-axis current control unit (107) that calculates a q-axis voltage command value (Vqref) to be applied to the stator winding in order to control the converted q-axis current to a q-axis command current (Iqref); The switch control unit performs the switching control based on the calculated q-axis voltage command value, 4. The control device for a rotating electric machine according to configuration 3, wherein the induced voltage calculation unit (113) calculates the induced voltage (EMF) based on the converted d, q axes currents and the calculated q axis voltage command value. [Configuration 5] An extraction unit (117) that extracts an AC component of the calculated induced voltage, 5. The control device for a rotating electric machine according to configuration 4, wherein the field current calculation unit calculates the field current based on the extracted AC component. [Configuration 6] a superposition unit (103) that calculates a d-axis command current (Idref) by superimposing a d-axis high-frequency command current (Idhref), which is an AC component, on a d-axis basic command current (Idbref), which is a DC component; a d-axis current control unit (106) that calculates a d-axis voltage command value (Vdref) to be applied to the stator winding in order to control the converted d-axis current to the d-axis command current; Equipped with The switch control unit performs the switching control based on the calculated d, q-axis voltage command values. 6. The control device for a rotating electric machine according to configuration 5, wherein the extraction unit extracts, as the AC component of the induced voltage, an AC component of the induced voltage at a frequency of a first component of the d-axis high frequency command current. [Configuration 7] the d-axis current control unit calculates the d-axis voltage command value to be applied to the stator winding in order to feedback control the converted d-axis current to the d-axis command current; the q-axis current control unit calculates the q-axis voltage command value to be applied to the stator winding in order to feedback control the converted q-axis current to the q-axis command current; 7. The control device for a rotating electric machine according to configuration 6, wherein the d, q axes current control unit changes a feedback gain of the feedback control based on the magnitude of the amplitude of the d axis high frequency command current. [Configuration 8] the d-axis current control unit calculates the d-axis voltage command value to be applied to the stator winding in order to feedback control the converted d-axis current to the d-axis command current; the q-axis current control unit calculates the q-axis voltage command value to be applied to the stator winding in order to feedback control the converted q-axis current to the q-axis command current; 7. The control device for a rotating electric machine according to configuration 6, wherein the d, q axes current control unit changes a feedback gain of the feedback control based on a magnitude of an amplitude of the fundamental wave current. [Configuration 9] The control device for a rotating electric machine according to any one of configurations 6 to 8, wherein the induced voltage calculation unit calculates the induced voltage under the condition that the electrical angular velocity of the rotor is equal to or greater than a speed threshold (ωth) and the amplitude of the d-axis high frequency command current is equal to or greater than an amplitude threshold (Ia). [Configuration 10] The control device for a rotating electric machine according to any one of configurations 1 to 9, wherein the induced voltage calculation unit calculates the induced voltage under the condition that a d-axis current flowing through the stator winding is equal to or less than a d-axis current threshold (Idth) and a q-axis current flowing through the stator winding is equal to or less than a q-axis current threshold (Iqth). [Configuration 11] 11. The control device for a rotating electric machine according to any one of configurations 1 to 10, wherein the induced voltage calculation unit calculates the induced voltage under the condition that an amount of fluctuation in an electrical angular velocity of the rotor is equal to or less than a predetermined value. [Configuration 12] 7. The control device for a rotating electric machine according to configuration 6, further comprising a change unit that changes a frequency of the d-axis high frequency command current based on an electrical angular frequency of the rotor. [Configuration 13] The change unit is When the electrical angular speed of the rotor is lower than a sixth-order electrical angular speed (ω6th) of the rotor, the frequency (fh) of the d-axis high-frequency command current is set to a frequency (ωa / (2π)) higher than a frequency corresponding to the sixth-order electrical angular speed, 13. The control device for a rotating electric machine according to claim 12, wherein, when the electrical angular speed of the rotor is equal to or greater than the sixth electrical angular speed, the frequency of the d-axis high frequency command current is set to a frequency (ωb / (2π)) lower than a frequency corresponding to the sixth electrical angular speed. [Configuration 14] The rotor has a rotor core (61) and main pole portions (62) that are provided at predetermined intervals in the circumferential direction and protrude radially from the rotor core, the field winding has a first winding portion (71a) and a second winding portion (71b) electrically connected in series, The first winding portion and the second winding portion are wound around the respective main pole portions, The rotor is a diode (80) electrically connected in parallel to the series connection of the first winding portion and the second winding portion; a capacitor (81) electrically connected in parallel to either the first winding portion or the second winding portion; 14. The control device for a rotating electric machine according to any one of configurations 1 to 13, comprising: [Explanation of symbols]

[0134] 20... inverter, 30... control device, 40... rotating electric machine, 50... stator, 52... stator winding, 60... rotor, 70... field winding.

Claims

1. A rotating electric machine (40) having a stator (50) including a stator winding (52) and a rotor (60) including a field winding (70); an inverter (20) electrically connected to the stator winding; A control device (30) for a rotating electric machine applied to a system including: The rotating electric machine is configured such that a high-frequency current flows through the stator winding to induce a voltage in the field winding, thereby causing a field current to flow, a switch control unit (109) that performs switching control of the inverter so that a composite current of the high-frequency current and a fundamental current having a frequency lower than that of the high-frequency current flows through the stator winding; an induced voltage calculation unit (113, 122) configured to calculate an induced voltage generated in the stator winding while the rotor is rotating and switching control is performed by the switch control unit; a field current calculation unit (115, 119, 124) that calculates a field current flowing through the field winding based on the calculated induced voltage; A control device for a rotating electric machine comprising:

2. The induced voltage calculation unit 2. The control device for a rotating electric machine according to claim 1, wherein the induced voltage is calculated based on a current flowing through the stator winding and a voltage applied from the inverter to the stator winding.

3. a current control unit (107) that calculates voltage command values ​​(Vqref, VUref) to be applied to the stator windings in order to control the currents flowing through the stator windings to command currents (Idref, Iqref), The control device for a rotating electric machine according to claim 2 , wherein the induced voltage calculation unit uses the calculated voltage command value as a voltage to be applied to the stator winding.

4. The system includes a current sensor (21) that detects a current flowing through the stator winding; a two-phase conversion unit (100) that converts a current of the stator winding in a three-phase fixed coordinate system of the rotating electric machine into d-axis and q-axis currents (Idr, Iqr) in a two-phase rotating coordinate system of the rotating electric machine based on a detection value of the current sensor, the current control unit is a q-axis current control unit (107) that calculates a q-axis voltage command value (Vqref) to be applied to the stator winding in order to control the converted q-axis current to a q-axis command current (Iqref); The switch control unit performs the switching control based on the calculated q-axis voltage command value, 4. The control device for a rotating electric machine according to claim 3, wherein the induced voltage calculation unit (113) calculates the induced voltage (EMF) based on the converted d-axis, q-axis currents and the calculated q-axis voltage command value.

5. An extraction unit (117) that extracts an AC component of the calculated induced voltage, The control device for a rotating electric machine according to claim 4 , wherein the field current calculation unit calculates the field current based on the extracted AC component.

6. a superposition unit (103) for calculating a d-axis command current (Idref) by superposing a d-axis high-frequency command current (Idhref), which is an AC component, on a d-axis basic command current (Idbref), which is a DC component; a d-axis current control unit (106) that calculates a d-axis voltage command value (Vdref) to be applied to the stator winding in order to control the converted d-axis current to the d-axis command current; Equipped with The switch control unit performs the switching control based on the calculated d-axis and q-axis voltage command values. The control device for a rotating electric machine according to claim 5 , wherein the extractor extracts, as the AC component of the induced voltage, an AC component of the induced voltage at a frequency of a first-order component of the d-axis high-frequency command current.

7. the d-axis current control unit calculates the d-axis voltage command value to be applied to the stator winding in order to feedback control the converted d-axis current to the d-axis command current; the q-axis current control unit calculates the q-axis voltage command value to be applied to the stator winding in order to feedback control the converted q-axis current to the q-axis command current; 7. The control device for a rotating electric machine according to claim 6, wherein the d, q axes current control unit changes a feedback gain of the feedback control based on the magnitude of the amplitude of the d axis high frequency command current.

8. the d-axis current control unit calculates the d-axis voltage command value to be applied to the stator winding in order to feedback control the converted d-axis current to the d-axis command current; the q-axis current control unit calculates the q-axis voltage command value to be applied to the stator winding in order to feedback control the converted q-axis current to the q-axis command current; 7. The control device for a rotating electric machine according to claim 6, wherein the d, q axes current control unit changes a feedback gain of the feedback control based on the magnitude of the amplitude of the fundamental wave current.

9. The control device for a rotating electric machine according to any one of claims 6 to 8, wherein the induced voltage calculation unit calculates the induced voltage under the condition that the electrical angular velocity of the rotor is equal to or greater than a speed threshold (ωth) and the amplitude of the d-axis high frequency command current is equal to or greater than an amplitude threshold (Ia).

10. The control device for a rotating electric machine according to any one of claims 1 to 5, wherein the induced voltage calculation unit calculates the induced voltage under the condition that a d-axis current flowing through the stator winding is equal to or less than a d-axis current threshold (Idth) and a q-axis current flowing through the stator winding is equal to or less than a q-axis current threshold (Iqth).

11. 6. The control device for a rotating electric machine according to claim 1, wherein the induced voltage calculation unit calculates the induced voltage under the condition that an amount of fluctuation in the electrical angular velocity of the rotor is equal to or less than a predetermined value.

12. The control device for a rotating electric machine according to claim 6 , further comprising a change unit that changes a frequency of the d-axis high frequency command current based on an electrical angular frequency of the rotor.

13. The change unit is when the electrical angular velocity of the rotor is lower than a sixth electrical angular velocity (ω6th) of the rotor, the frequency (fh) of the d-axis high frequency command current is set to a frequency (ωa / (2π)) higher than a frequency corresponding to the sixth electrical angular velocity, 13. The control device for a rotating electric machine according to claim 12, wherein, when the electrical angular velocity of the rotor is equal to or greater than the sixth electrical angular velocity, the frequency of the d-axis high frequency command current is set to a frequency (ωb / (2π)) lower than a frequency corresponding to the sixth electrical angular velocity.

14. The rotor has a rotor core (61) and main pole portions (62) provided at predetermined intervals in the circumferential direction and protruding in the radial direction from the rotor core, The field winding has a first winding portion (71a) and a second winding portion (71b) electrically connected in series, The first winding portion and the second winding portion are wound around the respective main pole portions, The rotor is a diode (80) electrically connected in parallel to the series connection of the first winding portion and the second winding portion; a capacitor (81) electrically connected in parallel to either the first winding portion or the second winding portion; The control device for a rotating electric machine according to any one of claims 1 to 8, 12 and 13, further comprising:

15. A rotating electric machine (40) having a stator (50) including a stator winding (52) and a rotor (60) including a field winding (70); an inverter (20) electrically connected to the stator winding; A computer (31); In a program applied to a system comprising: The rotating electric machine is configured such that a high-frequency current flows through the stator winding to induce a voltage in the field winding, thereby causing a field current to flow, The computer includes: a process of performing switching control of the inverter so that a composite current of the high-frequency current and a fundamental current having a frequency lower than that of the high-frequency current flows through the stator winding; a process of calculating an induced voltage generated in the stator winding while the switching control is being performed and the rotor is rotating; A process of calculating a field current flowing through the field winding based on the calculated induced voltage; A program to execute.

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