Highly efficient hybrid regulator

Abstract

According to an embodiment of the present invention, there is provided a switch network including a first switch block, a second switch block, a third switch block, and a fourth switch block connected in series to each other, a flying capacitor is connected to a first node to which the first switch block and the second switch block are connected, a second node to which the third switch block and the fourth switch block are connected, and an inductor is connected to a third node to which the second switch block and the third switch block are connected; a control circuit for controlling the switch network in a second state in which an inductor current forms a resonant waveform and a fourth state in which an inductor current is turned on, the control circuit controlling the switch network in such a way that the third state and the fourth state alternate, in which an inductor current forms a resonant waveform, and when a magnitude of the inductor current deviates from a required range, the control circuit controlling the switch network in such a way that the first state or the second state is formed between the third state and the fourth state.

Description

[Technical field]

[0001] The present embodiment relates to a power conversion device. [Background technology]

[0002] A typical buck or boost converter transfers energy through an inductor.

[0003] If the current flowing from such a buck converter or boost converter to the inductor can be appropriately controlled, it has the advantage of being able to stably control the output power, but it can have the disadvantage of power loss due to the relatively high DC resistance of the inductor. Since the power loss in the DC resistance increases in proportion to the square of the output current, there is a problem in that the efficiency of power transmission via an inductor decreases as the amount of power to be transmitted increases.

[0004] To improve this, switched capacitor converters, which transfer energy via capacitors having low DC resistance, have attracted attention.

[0005] The switched capacitor converter has the advantage of being highly efficient, but has the disadvantage that in order to stably control the output power, a separate low-efficiency linear regulator must be added or the input power must be controlled through a separate global loop like a PPS (Programmable Power Supply) adapter. Summary of the Invention [Problem to be solved by the invention]

[0006] In this context, an object of the present embodiment is, in one aspect, to provide a highly efficient power conversion device. In another aspect, an object of the present embodiment is to provide a technique for stably controlling a power conversion device without adding a complicated configuration. In yet another aspect, an object of the present embodiment is to provide a power conversion device that is relatively small in size. [Means for solving the problem]

[0007] In order to achieve the above object, one embodiment of the present invention provides a switch network including a first switch block, a second switch block, a third switch block, and a fourth switch block that are connected in series to each other, a flying capacitor is connected to a first node to which the first switch block and the second switch block are connected, a second node to which the third switch block and the fourth switch block are connected, and an inductor is connected to a third node to which the second switch block and the third switch block are connected; a control circuit for controlling the switch network in a second state in which an inductor current forms a resonant waveform and in the fourth state in which an inductor current is outside a required range, the control circuit controlling the switch network so that the third state and the fourth state alternate, in which an inductor current forms a resonant waveform, and the first state or the second state is formed between the third state and the fourth state when a magnitude of the inductor current deviates from a required range.

[0008] The control circuit may exit the third state or the fourth state when the inductor current reaches a zero level.

[0009] A high voltage is supplied to one side of the first switch block, and the control circuit can control the switch network such that the first state is formed between the third state and the fourth state when the magnitude of the inductor current is smaller than the required range.

[0010] The control circuit can control the switch network so that the first state is formed between the third state and the fourth state when the input voltage is less than a voltage obtained by multiplying the output voltage by R (R is a positive number greater than or equal to 2) minus a delta voltage.

[0011] A low voltage is supplied to one side of the fourth switch block, and the control circuit can control the switch network such that the second state is formed between the third state and the fourth state when the magnitude of the inductor current is greater than the required range.

[0012] The control circuit can control the switch network so that the second state is formed between the third state and the fourth state when the voltage of the third node is lower than a first lower limit, or can control the switch network so that the second state is formed between the third state and the fourth state when the voltage of the flying capacitor is lower than an upper limit and higher than a second lower limit.

[0013] The control circuit can terminate the third state or the fourth state before the inductor current reaches a zero level, and can terminate the second state when the inductor current reaches a zero level in the second state.

[0014] The control circuit can control the switch network in a fifth state in which the first switch block and the fourth switch block are turned on, and can control the switch network in the fifth state when the voltage of the flying capacitor is lower than a preset voltage range.

[0015] The control circuit can operate the power semiconductors included in the first switch block or the fourth switch block in a linear mode in the fifth state to limit the magnitude of the current supplied to the flying capacitor.

[0016] The control circuit can control the switch network in a sixth state in which the second switch block and the third switch block are turned on, and can control the switch network in the sixth state when a voltage state of the flying capacitor is higher than a preset voltage range.

[0017] The control circuit can control the switch network in the third state or the fourth state when a difference between a control value and a reference value is equal to or greater than a reference value, and can control the switch network in a state in which the first switch block through the fourth switch block are turned off when a difference between the control value and the reference value is smaller than the reference value.

[0018] The control circuit basically controls the switch network in the third state or the fourth state, and can control the switch network in the first state when sufficient power cannot be transferred in the third state and the fourth state alone, and can control the switch network in the second state when the magnitude of the inductor current is greater than the required range.

[0019] A high voltage may be supplied to one side of the first switch block, and a power semiconductor included in the first switch block may be an active element having a bi-directional body diode characteristic.

[0020] Another embodiment provides a regulator including a switch network including a plurality of switch elements, at least two of which are connected to connection nodes of the switch elements, and at least one of which is connected to an inductor, the switch network having one side supplied with a high voltage and the other side supplied with a low voltage; and a control circuit configured to control the switch network in a first state in which the high voltage is connected to one side of the inductor, a second state in which the low voltage is connected to one side of the inductor, a third state in which the high voltage, the flying capacitor, and the inductor are connected in series and an inductor current forms a resonant waveform, and a fourth state in which the low voltage, the flying capacitor, and the inductor are connected in series and the inductor current forms a resonant waveform, the control circuit controlling the switch network to alternate between the third state and the fourth state, and when a magnitude of the inductor current deviates from a required range, controlling the switch network so that the first state or the second state is formed between the third state and the fourth state.

[0021] The control circuit may exit the third state or the fourth state when the inductor current reaches a zero level.

[0022] The control circuit can output a pulse enable signal at a high level when a difference between a control value and a reference value is equal to or greater than a reference value, and control the switch network so that the first state is formed between the third state and the fourth state when the inductor current reaches the zero level N or more times (N is a natural number equal to or greater than 2) while the pulse enable signal is maintained at a high level.

[0023] When the first state operates, the control circuit can generate a power-up flag to cause a power supplier that supplies the high voltage to increase output power, and can send the power flag to a device that controls the power supplier.

[0024] The control circuit may, when the first state is not operating, not generate the power-up flag, calculate an efficiency value, and, when the efficiency value is less than a target value, generate a power-down flag and cause the power supplier to reduce output power.

[0025] The control circuit can control the switch network such that the first state is formed between the third state and the fourth state when the magnitude of the inductor current is less than the required range.

[0026] The control circuit can control the switch network such that the second state is formed between the third state and the fourth state when the magnitude of the inductor current is greater than the required range.

[0027] The control circuit may control the switch network in a fifth state in which one side of the inductor is floating and the high voltage, the flying capacitor and the low voltage are connected in series, and may control the switch network in the fifth state when the voltage of the flying capacitor is lower than a preset voltage range.

[0028] The control circuit can control the switch network in the fifth state at initial power-up, operate power semiconductors turned on in the fifth state in a linear mode, and limit the magnitude of current supplied to the flying capacitor.

[0029] Yet another embodiment provides a regulator including a switch network including a plurality of switch elements, at least two of which are connected to connection nodes of the switch elements, and at least one of which is connected to an inductor, the switch network having one side supplied with a high voltage and the other side supplied with a low voltage, and a control circuit configured to control the switch network in a first state in which the high voltage is connected to one side of the inductor, a second state in which the low voltage is connected to one side of the inductor, a third state in which the high voltage, the flying capacitor, and the inductor are connected in series and an inductor current forms a resonant waveform, and a fourth state in which the low voltage, the flying capacitor, and the inductor are connected in series and the inductor current forms a resonant waveform, the control circuit controlling the switch network to alternate between the third state and the fourth state, and controlling the switch network so that the first state or the second state is formed between the third state and the fourth state when the magnitude of the inductor current deviates from a required range. The regulator is arranged in parallel with each other while sharing an output.

[0030] The regulator may further include a MUX circuit that may share an input of the regulator block.

[0031] The regulator may further include a switched capacitor converter at the input of the regulator block.

[0032] The regulator can control at least two of the regulator blocks in different states for the third state and the fourth state. Effect of the Invention

[0033] As described above, according to this embodiment, the efficiency of the power conversion device can be increased, the power conversion device can be stably controlled without adding a complex configuration to the power conversion device, and the size of the power conversion device can be reduced. [Brief description of the drawings]

[0034] [Figure 1] FIG. 1 is a diagram illustrating an example of a configuration of a power conversion device. [Diagram 2] FIG. 11 is a diagram illustrating another exemplary configuration of a power conversion device. [Diagram 3] FIG. 2 is a block diagram of a regulator according to one embodiment. [Figure 4] FIG. 2 illustrates a 0th state of a switch network according to one embodiment. [Diagram 5] FIG. 2 illustrates a first state of a switch network according to one embodiment. [Figure 6] FIG. 2 illustrates a second state of the switch network according to one embodiment. [Figure 7] FIG. 2 illustrates a third state of the switch network according to one embodiment. [Figure 8] FIG. 13 illustrates a fourth state of the switch network according to one embodiment. [Figure 9] FIG. 13 illustrates pulse shaping of an inductor current using a third state and a fourth state in one embodiment. [Figure 10] FIG. 13 illustrates that in one embodiment, a first state and a second state are further formed between the third state and the fourth state. [Figure 11] FIG. 2 shows an overshaped pulse and an undershaped pulse. [Figure 12a] FIG. 11 is a first illustrative diagram showing the regulator adding a first state between the third state and the fourth state. [Figure 12b] FIG. 11 is a second illustrative diagram showing the regulator adding a first state between the third state and the fourth state. [Figure 13a] FIG. 11 is a first illustrative diagram showing the regulator adding a second state between the third state and the fourth state. [Figure 13b] FIG. 11 is a second example diagram showing the regulator adding a second state between the third state and the fourth state. [Figure 14] FIG. 13 illustrates a fifth state of the switch network according to one embodiment. [Figure 15] FIG. 13 illustrates a sixth state of the switch network according to one embodiment. [Figure 16] FIG. 13 is a diagram illustrating an exemplary configuration for performing pulse skip control in a control circuit according to an embodiment. [Figure 17a] FIG. 13 is a diagram showing main waveforms in a first example of pulse skip control. [Figure 17b] FIG. 13 is a diagram showing main waveforms in a second example of pulse skip control. [Figure 18] FIG. 11 is a third illustrative diagram showing the regulator adding a first state between the third state and the fourth state. [Figure 19] FIG. 2 illustrates an example input and output of a regulator according to one embodiment. [Figure 20] 1A and 1B are diagrams for explaining element characteristics of a first switch in a switch network of an embodiment. [Figure 21] FIG. 1 is a diagram illustrating a first exemplary configuration of an extended regulator. [Figure 22] FIG. 13 is a diagram showing a second exemplary configuration of an extended regulator. [Figure 23] FIG. 13 is a third exemplary configuration diagram of an extended regulator. [Figure 24] FIG. 11 illustrates a first control state of a regulator according to a third example. [Diagram 25] FIG. 11 illustrates a second control state of the regulator according to the third example. [Figure 26] FIG. 11 illustrates a third control state of the regulator according to the third example. [Figure 27] FIG. 13 illustrates a fourth control state of the regulator according to the third example. [Figure 28] FIG. 13 is a diagram showing main waveforms of a regulator according to a third example. [Figure 29] FIG. 2 illustrates cooperative control between a regulator and a host according to one embodiment. [Diagram 30] 4 is a flowchart of a method for cooperative control between a regulator and a host according to an embodiment. DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

[0035] Hereinafter, some embodiments of the present invention will be described in detail with reference to the drawings. Please note that when adding reference numerals to components in each drawing, the same numerals are used to refer to the same components even if they are shown in different drawings. In addition, when describing the present invention, if a detailed description of related known configurations or functions is determined to make the gist of the present invention unclear, the detailed description will be omitted.

[0036] In addition, in describing components of the present invention, terms such as first, second, A, B, (a), (b), etc. can be used. Such terms are used to distinguish the components from other components, and do not limit the nature, order, sequence, etc. of the components. When a component is described as being "coupled," "coupled," or "connected" to another component, it should be understood that the component may be directly coupled or connected to the other component, but that there may also be another component "coupled," "coupled," or "connected" between each component.

[0037] FIG. 1 is a diagram showing an example of the configuration of a power conversion device.

[0038] Referring to FIG. 1, a power conversion device 10 may include an inductor converter 11, a switched capacitor converter 12, an input stage 13, an overvoltage protection IC (IC: integrated circuit) 14, and the like.

[0039] The inductor converter 11 may include an upper switch QE, a lower switch QF, and an inductor L.

[0040] The switched capacitor converter 120 includes a first switch QA, a second switch QB, a third switch QC, and a fourth switch QD, and a flying capacitor C FLY may include.

[0041] In some cases, the power conversion device 10 can convert power input having a first voltage V1 to output power having a second voltage V2, and can convert power input having the second voltage V2 to output power having the first voltage V1.

[0042] The power conversion device 10 may convert power using an inductor converter 11 when not functioning as a PPS adapter, and may convert power using a switched capacitor converter 12 when functioning as a PPS adapter.

[0043] Here, the switched capacitor converter 12 is a hard switched capacitor converter in which the switches are turned on and off while current flows.

[0044] The power conversion device 10 shown in FIG. 1 has the disadvantages of a large solution size and high cost because two different ICs must be used together. Furthermore, when using the switched capacitor converter 12, the power conversion device 10 must use a separate input stage 13 and an overvoltage protection IC 14 for power regulation in an abnormal situation (e.g., a power control malfunction or slow operation of a PPS adapter), which may result in low efficiency and large size. In addition, the power conversion device 10 uses a flying capacitor C with a large capacitance to increase the efficiency of the switched capacitor converter 12. FLY However, such a large flying capacitor C FLY This can increase the overall size.

[0045] FIG. 2 is a diagram showing another exemplary configuration of the power conversion device.

[0046] Referring to FIG. 2, the power conversion device 20 may include a 3-level buck / boost converter 22, an input stage 23, and an overvoltage protection IC 24, among others.

[0047] The 3-level buck / boost converter 22 includes a first switch QA, a second switch QB, a third switch QC, and a fourth switch QD, and includes an inductor L and a flying capacitor C FLY may include.

[0048] The power conversion device 20 can convert input power having a first voltage V1 and output power having a second voltage V2.

[0049] When the power conversion device 20 is not functioning as a PPS adapter, it can convert power using the 3-level buck / boost converter 22, and when it is functioning as a PPS adapter, the components included in the 3-level buck / boost converter 22 can operate as a hard-switched capacitor converter.

[0050] The power converter 20 shown in Figure 2 may have a smaller solution size than the power converter (see 10 in Figure 1) shown in Figure 1. However, when the power converter 20 shown in Figure 2 operates as a hard switched capacitor converter, the power loss is large due to the high DC resistance of the inductor L, so that the power conversion efficiency may be lower than that of a typical switched capacitor converter.

[0051] In addition, the power converter 20 shown in FIG. 2 must use the input stage 23 and the overvoltage protection IC 24, similar to the power converter shown in FIG. 1 (see 10 in FIG. 1), so the efficiency may be low and the size may be large. Also, the flying capacitor C FLY This can increase the overall size.

[0052] FIG. 3 is a block diagram of a regulator according to one embodiment.

[0053] Referring to FIG. 3, regulator 300 may include a switch network 310, a control circuit 320, and current sensors 331-334.

[0054] The regulator 300 can convert power having a first voltage V1 and input to the first node N1 to generate power having a second voltage V2 and output it to the sixth node N6. Alternatively, the regulator 300 can convert power having the second voltage V2 and input to the sixth node N6 to generate power having the first voltage V1 and output it to the first node N1.

[0055] The switch network 310 may include a first switch block, a second switch block, a third switch block, and a fourth switch block that are serially connected to each other.

[0056] Each switch block may include at least one switch. For example, the first switch block may include a first switch Q1, the second switch block may include a second switch Q2, the third switch block may include a third switch Q3, and the fourth switch block may include a fourth switch Q4. In the following, for convenience of explanation, an example in which each switch block includes one switch will be mainly described, but the present embodiment is not limited to such an example.

[0057] In the following, the control of the first switch Q1 may be understood as the control of the first switch block, the control of the second switch Q2 may be understood as the control of the second switch block, the control of the third switch Q3 may be understood as the control of the third switch block, and the control of the fourth switch Q4 may be understood as the control of the fourth switch block. For example, turning off the first switch Q1 may be understood as turning off the first switch block, and turning on the second switch Q2 may be understood as turning on the second switch block.

[0058] The first switch Q1, the second switch Q2, the third switch Q3, and the fourth switch Q4 may be power semiconductors. For example, the first switch Q1, the second switch Q2, the third switch Q3, and the fourth switch Q4 may be MOSFETs (Metal Oxide Semiconductor Field Effect Transistors), IGBTs (Insulated Gate Bipolar Transistors), or other forms of power semiconductors.

[0059] The first switch Q1, the second switch Q2, the third switch Q3, and the fourth switch Q4 may be connected to each other in series. For example, the first switch Q1 and the second switch Q2 may be connected to each other via a second node N2, the second switch Q2 and the third switch Q3 may be connected to each other via a third node N3, and the third switch Q3 and the fourth switch Q4 may be connected to each other via a fourth node N4.

[0060] A first node N1 may be formed on one side of the first switch Q1, and a second node N2 may be formed on the other side, and a first voltage V1 may be supplied or output to the first node N1. A fifth node N5 may be formed on one side of the fourth switch Q4, and a fourth node N4 may be formed on the other side, and a low voltage (e.g., ground voltage) may be supplied to the fifth node N5. The first voltage V1 supplied to the first node N1 may be a voltage relatively higher than the low voltage supplied to the fifth node N5. Thus, the voltage supplied to the first node N1 may be referred to as a high voltage, and the voltage supplied to the fifth node N5 may be referred to as a low voltage.

[0061] The switch network 310 includes an inductor L and a flying capacitor C FLY and can be linked together.

[0062] Flying Capacitor C FLY One side of the first switch Q1 and the second switch Q2 may be connected to a second node N2, and the other side of the second switch Q1 and the second switch Q2 may be connected to a fourth node N4, to which a third switch Q3 and a fourth switch Q4 are connected.

[0063] The inductor L may have one side connected to a third node N3 to which the second switch Q2 and the third switch Q3 are connected, and the other side connected to a sixth node N6 from which the second voltage V2 is output.

[0064] Furthermore, an output capacitor C may further be disposed between the sixth node N6 and the low voltage.

[0065] The control circuit 320 can control the switches Q1 to Q4 included in the switch network 310. The control circuit 320 can put the switch network 310 into a plurality of states while turning on or off the switches Q1 to Q4.

[0066] The control circuit 320 can send gate signals to the gates of the switches Q1 to Q4 to turn on or off the switches Q1 to Q4.

[0067] The control circuit 320 can operate at least one of the switches Q1 to Q4 in a linear mode. When operating in the linear mode, the amount of current flowing through at least one switch can be limited to a certain level in response to a gate signal.

[0068] The control circuit 320 senses the current, voltage, etc. of the switch network 310 or each of the nodes N1 to N6, and can change the state of the switch network 310 using the sensed values.

[0069] For example, the control circuit 320 controls the first voltage V1, the second voltage V2, the flying capacitor voltage V CFLY , the third node voltage V SW The control circuit 320 can sense the first switch current I Q1 , the second switch current I Q2 , the third switch current I Q3 , the fourth switch current I Q4 etc. can be sensed.

[0070] The control circuit 320 then controls the first voltage V1, the second voltage V2, and the flying capacitor voltage V CFLY , the third node voltage V SW , the first switch current I Q1 , the second switch current I Q2 , the third switch current I Q3 , and the fourth switch current I Q4At least one of the sensed values ​​may be used to determine or change the state of the switch network 310.

[0071] All of the above values ​​can be sensed, or only some of the values ​​can be sensed. For example, the control circuit 320 can sense the first switch current I Q1 and the third switch current I Q3 Only one of the two switches can be sensed, and the second switch current I Q2 and the fourth switch current I Q4 Only one of these can be sensed.

[0072] The control circuit 320 can control the switch network 310 in seven states, which will be described later.

[0073] FIG. 4 is a diagram illustrating a zeroth state of a switch network according to one embodiment.

[0074] Referring to FIG. 4, the control circuit can turn off all the switches Q1 to Q4 of the switch network 310 to put the switch network 310 into the 0th state.

[0075] FIG. 5 illustrates a first state of a switch network according to one embodiment.

[0076] Referring to FIG. 5, the control circuit can turn on the first switch Q1 and the second switch Q2 and turn off the third switch Q3 and the fourth switch Q4 to put the switch network 310 in a first state.

[0077] In the first state, the flying capacitor C FLY is floated and the flying capacitor voltage V CFLY can be maintained at a certain level.

[0078] A first voltage V1 (high voltage) can be supplied to one side of the first switch Q1, and in the first state, the first switch Q1 and the second switch Q2 are turned on, and the third switch Q3 and the fourth switch Q4 are turned off, so that the first voltage V1 can be supplied to one side of the inductor L.

[0079] A second voltage V2 can be applied to the other side of the inductor L, so that in the first state, the first voltage V1 can be applied to one side of the inductor L and the second voltage V2 can be applied to the other side. In addition, such voltages V1 and V2 can cause the inductor current i L can be built up.

[0080] The first state may be identical to operation in a buck converter or a boost converter.

[0081] FIG. 6 illustrates a second state of the switch network according to one embodiment.

[0082] Referring to FIG. 6, the control circuit can turn off the first switch Q1 and the second switch Q2 and turn on the third switch Q3 and the fourth switch Q4 to put the switch network 310 into a second state.

[0083] In the second state, the flying capacitor C FLY is floated and the flying capacitor voltage V CFLY can be maintained at a certain level.

[0084] A ground voltage (low voltage) can be supplied to one side of the fourth switch Q4, but in the second state, the first switch Q1 and the second switch Q2 are turned off and the third switch Q3 and the fourth switch Q4 are turned on, so that the ground voltage (low voltage) can be supplied to one side of the inductor L.

[0085] A second voltage V2 may be applied to the other side of the inductor L, so that in the second state, one side of the inductor L is supplied with a ground voltage (low voltage) and the other side is supplied with the second voltage V2. Such a voltage causes the inductor current i L can be built up.

[0086] Inductor current i L can be built up in opposite directions in the first and second states. For example, if the direction of current flowing from one side of the inductor L to the other side is defined as the positive direction, then in the first state, the inductor current i L can be built up in an increasing direction, and in the second state, the inductor current i L can be built up in a decreasing direction.

[0087] The second state may be identical to the operation in a buck converter or a boost converter.

[0088] FIG. 7 illustrates a third state of the switch network according to one embodiment.

[0089] Referring to FIG. 7, the control circuit can turn on the first switch Q1 and the third switch Q3 and turn off the second switch Q2 and the fourth switch Q4 to put the switch network 310 in a third state.

[0090] In the third state, the flying capacitor C FLY and inductor L are connected in series, and the inductor current i L and the flying capacitor voltage V CFLY and can form a resonant waveform.

[0091] In the third state, the inductor current i L can form a resonant waveform that increases and then decreases. Such an inductor current i LDue to this resonant waveform, the control circuit can turn each of the switches Q1 to Q4 off at zero current or on at zero current.

[0092] The third state may be identical to the operation in a resonant converter.

[0093] FIG. 8 illustrates a fourth state of the switch network according to one embodiment.

[0094] Referring to FIG. 8, the control circuit can turn off the first switch Q1 and the third switch Q3 and turn on the second switch Q2 and the fourth switch Q4 to put the switch network 310 into a fourth state.

[0095] In the fourth state, the flying capacitor C FLY and inductor L are connected in series, and the inductor current i L and the flying capacitor voltage V CFLY and can form a resonant waveform.

[0096] In the fourth state, the inductor current i L can form a resonant waveform that increases and then decreases. Such an inductor current i L Due to this resonant waveform, the control circuit can turn each of the switches Q1 to Q4 off at zero current or on at zero current.

[0097] The fourth state may be identical to the operation in a resonant converter.

[0098] The control circuitry can control the switch network to alternate between the third state and the fourth state.

[0099] A regulator according to one embodiment can transfer power via resonance between a flying capacitor and an inductor.

[0100] The control circuit can drive the third and fourth states at or near the resonant frequency of the flying capacitor and inductor, allowing power to be transferred via the resonance of the flying capacitor and inductor like a resonant converter.

[0101] The third and fourth states can be controlled to alternate, for example the switch network can operate in the third state followed by the fourth state and vice versa.

[0102] When forming an increasing / decreasing waveform as the inductor current increases and then decreases is defined as pulse shaping, one pulse shaping may be performed in each of the third state and the fourth state.

[0103] FIG. 9 illustrates pulse shaping of the inductor current using a third state and a fourth state in one embodiment.

[0104] Referring to FIG. 9, the control circuitry can control the switch network to alternate between the third and fourth states.

[0105] The control circuit then regulates the inductor current i L When reaches the zero level, the third state or the fourth state can be terminated.

[0106] In the third state, the flying capacitor is charged and the flying capacitor voltage V CFLY can increase. And the inductor current i L In the third state, the control circuit controls the inductor current i L When reaches the zero level (within a preset error band of zero), the third state can be ended and pulse shaping can be ended.

[0107] In the fourth state, the flying capacitor is discharged, and the flying capacitor voltage V CFLY can decrease. And the inductor current i L In the fourth state, the control circuit controls the inductor current i L When reaches the zero level (within a preset error band at zero), the fourth state can be ended and pulse shaping can be ended.

[0108] The regulator may be adapted to alternate between such third and fourth states.

[0109] However, the regulator according to one embodiment can form other states between the third state and the fourth state.

[0110] FIG. 10 illustrates that in one embodiment, a first state and a second state are further formed between the third state and the fourth state.

[0111] Referring to FIG. 10 , the control circuit can control the switch network to alternate between the third state and the fourth state, and further form a first state and a second state between the third state and the fourth state.

[0112] The control circuit can control the switch network in a first state before controlling the switch network in a third state, and can provide a first voltage to one side of the inductor in the first state, thereby allowing the inductor current to increase linearly.

[0113] The control circuit can then control the switch network in a third state to transfer the resonant energy of the flying capacitor and the inductor to the output, and at this time, the inductor current can form a resonant waveform.

[0114] Because the first state caused the inductor current to increase by a certain amount, the third state may be exited with the inductor current at a level above zero.

[0115] The control circuit can control the switch network in a second state after the third state has been completed, where a low voltage is provided to one side of the inductor, allowing the inductor current to ramp down linearly.

[0116] The control circuitry can then control the switch network in a first state, in a fourth state after the first state, and in the second state after the fourth state.

[0117] On the other hand, there are cases where the pulse shaping of the inductor current is not as desired. The peak of the inductor current may be formed higher than the desired level, or the peak of the inductor current may be formed lower than the desired level. When the peak of the inductor current is formed higher than the desired level, the waveform can be called an over-shaped pulse, and when it is formed lower than the desired level, the waveform can be called an under-shaped pulse.

[0118] FIG. 11 is a diagram showing an overshaped pulse and an undershaped pulse.

[0119] Referring to FIG. 11, in some cases, the inductor current i L In this case, the output current iout can be formed to be higher than the desired level.

[0120] And, in some cases, the inductor current i L In this case, an undersink pulse may be formed in which the level of iout is lower than the desired level. In this case, the output current iout may be lower than the desired level.

[0121] In order to adjust the output current iout to a desired level, the regulator can be placed in other states between the third and fourth states.

[0122] FIG. 12a illustrates the regulator adding a first state between the third and fourth states.

[0123] Referring to FIG. 12a, the regulator control circuit regulates the inductor current i L When the magnitude of is less than the desired range or level, the first state can be formed between the third state and the fourth state.

[0124] The control circuit regulates the inductor current i L The peak of the inductor current i L If the peak of is lower than the required level, a first state can be added between the third and fourth states, or between the fourth and third states.

[0125] Inductor current i L The magnitude of the inductor current i can be determined as a function of the flying capacitor voltage at resonance. However, if the energy charged in the flying capacitor at resonance is insufficient, the desired magnitude of the inductor current i L may not be generated.

[0126] To improve this, the control circuit builds up the inductor current through the first state, and then resonates (alternating between the third and fourth states) to produce the desired inductor current i L , through which a desired output current magnitude can be generated.

[0127] The control circuit can determine the time to add and end the first state based on a combination of input sensing values ​​(e.g., the first voltage, the second voltage, the flying capacitor voltage, the third node voltage, etc.) Alternatively, the control circuit can determine the switching time points among the first state, the third state, and the fourth state based on a combination of input sensing values.

[0128] FIG. 12b is a second example diagram showing the regulator adding a first state between the third and fourth states.

[0129] Referring to FIG. 12b, the control circuit can decide whether to add a first state depending on the relationship between the regulator's input voltage and output voltage.

[0130] The control circuit can add a first state between the third state and the fourth state, or between the fourth state and the third state (S1220) when the regulator's input voltage is less than twice the output voltage minus the delta voltage (YES in S1210).

[0131] When the first voltage V1 is an input voltage and the second voltage V2 is an output voltage, the control circuit can add a first state when the first voltage V1 is less than twice the second voltage V2 plus a delta voltage. When the second voltage V2 is an input voltage and the first voltage V1 is an output voltage, the control circuit can add a first state when the second voltage V2 is less than twice the first voltage V1 plus a delta voltage. Here, the delta voltage is a voltage corresponding to a margin and can have different magnitudes depending on the embodiment.

[0132] The control circuit can then stop the operation of the first state according to the relationship between the input voltage and the output voltage of the regulator.

[0133] When the input voltage of the regulator is greater than twice the output voltage plus the delta voltage (YES in S1230), the control circuit does not need to operate the first state (S1240).

[0134] When the first voltage V1 is an input voltage and the second voltage V2 is an output voltage, the control circuit may not activate the first state when the first voltage V1 is greater than twice the second voltage V2 plus a delta voltage. And when the second voltage V2 is an input voltage and the first voltage V1 is an output voltage, the control circuit may not activate the first state when the second voltage V2 is greater than twice the first voltage V1 plus a delta voltage.

[0135] FIG. 13a is a first exemplary diagram showing the regulator adding a second state between the third and fourth states.

[0136] Referring to FIG. 13a, the regulator control circuit regulates the inductor current i L A second state can be formed between the third state and the fourth state when the magnitude of is greater than the desired range or level.

[0137] The control circuit regulates the inductor current i L The peak of the inductor current i L When the peak of is higher than the desired level, a second state can be added between the third and fourth states, or between the fourth and third states.

[0138] Inductor current i L The magnitude of can be determined as a function of the flying capacitor voltage at resonance. However, if the energy charged in the flying capacitor at resonance is greater than necessary, the desired magnitude of inductor current i L No inductor current is generated, and the inductor current i LIf this occurs, not only will the output current not be as large as desired, but the excessive current may also damage internal or external elements.

[0139] To improve this, the control circuit reduces the inductor current through the second state, and then resonates (alternating between the third and fourth states) to generate the desired inductor current i L , through which a desired output current magnitude can be generated.

[0140] The control circuit can determine the time to add and end the second state based on a combination of input sensing values ​​(e.g., the first voltage, the second voltage, the flying capacitor voltage, the third node voltage, etc.) Alternatively, the control circuit can determine the switching times of the second state, the third state, and the fourth state based on a combination of input sensing values.

[0141] The control circuit regulates the inductor current i L The second state can be terminated when reaches the zero level.

[0142] FIG. 13b is a second example diagram showing the regulator adding a second state between the third and fourth states.

[0143] Referring to FIG. 13b, the regulator control circuitry, for example, controls the third node voltage V SW and the first lower limit limit Lower 1, the third node voltage V SW is the first lower limit limit Lower When the first lower limit comparator 1312 is set to a positive input stage, the first lower limit value limit is input to the positive input stage of the first lower limit comparator 1312. When the first lower limit value limit is set to a positive input stage of the first lower limit comparator 1312, the first lower limit value limit is generated.Lower A signal corresponding to 1 is input, and the negative input stage is connected to the third node voltage V SW The first lower limit comparator 1312 receives a signal corresponding to the third node voltage V SW and the first lower limit limit Lower 1, and the third node voltage V SW is the first lower limit limit Lower When it goes below 1, a second state enable signal Enable_State2 can be generated.

[0144] As another example, the regulator’s control circuitry may regulate the flying capacitor voltage V CFLY and the upper limit Upper , and the second lower limit Lower 2, the flying capacitor voltage V CFLY is the upper limit Upper The second lower limit, limit Lower When the upper limit comparator 1322 is greater than 2, a second state enable signal Enable_State2 can be generated (the second state enable signal Enable_State2 can be changed from low to high). The control circuit can include an upper limit comparator 1322, a second lower limit comparator 1324, and an AND logic circuit 1326. The upper limit comparator 1322 receives an upper limit value limit Upper A signal corresponding to the flying capacitor voltage V is input to the negative input stage. CFLY A signal corresponding to the flying capacitor voltage V CFLY A signal corresponding to the second lower limit limit is input to the negative input stage. Lower The output of the upper limit comparator 1322 and the output of the second lower limit comparator 1324 are input to an AND logic circuit 1326, and when both outputs are high, the AND logic circuit 1326 can output a second state enable signal Enable_State2.

[0145] FIG. 14 illustrates a fifth state of the switch network in accordance with one embodiment.

[0146] Referring to FIG. 14, the control circuit can turn on the first switch Q1 and the fourth switch Q4 and turn off the second switch Q2 and the third switch Q3 to put the switch network 310 into a fifth state.

[0147] During initial start-up or in abnormal conditions, the flying capacitor voltage V CFLY is below a preset voltage range or voltage level, the control circuit may control the switch network 310 in a fifth state.

[0148] In the fifth state, the first voltage V1, the first switch Q1, and the flying capacitor C FLY A current path is formed in series between the fourth switch Q4 and the ground voltage, and the current in this current path causes the flying capacitor C FLY can be charged.

[0149] In the fifth state, in order to prevent an excessive current (e.g., an in-rush current) from flowing through the first switch Q1 and / or the fourth switch Q4, the control circuit can operate the first switch Q1 and the fourth switch Q4 in a linear mode. At this time, the control circuit can sense the current flowing through the first switch Q1 and the fourth switch Q4 and control the first switch Q1 and the fourth switch Q4 according to the sensed value.

[0150] FIG. 15 illustrates a sixth state of the switch network in accordance with one embodiment.

[0151] Referring to FIG. 15, the control circuit can turn off the first switch Q1 and the fourth switch Q4 and turn on the second switch Q2 and the third switch Q3 to put the switch network 310 into a sixth state.

[0152] In abnormal situations, the flying capacitor voltage V CFLY is greater than a preset voltage range or voltage level, the control circuit may control the switch network 310 in a sixth state.

[0153] In the sixth state, the second switch Q2 and the third switch Q3 are connected to the flying capacitor C FLY The flying capacitor C can be arranged in parallel with the second switch Q2 and the third switch Q3. FLY can be discharged.

[0154] In the sixth state, in order to prevent an excessive current from flowing through the second switch Q2 and / or the third switch Q3, the control circuit can operate the second switch Q2 and the third switch Q3 in a linear mode. At this time, the control circuit can sense the current flowing through the second switch Q2 and the third switch Q3 and control the second switch Q2 and the third switch Q3 according to the sensed value.

[0155] The regulator can provide pulse skip control as well as pulse shaping control to shape the resonant waveform of the inductor current.

[0156] The regulator can make the inductor current have a resonant waveform through the third state or the fourth state. Forming the inductor current into a resonant waveform in this way is called pulsing, and maintaining the inductor current at a zero level or a very low level can be called pulse skipping.

[0157] The regulator, via control, can either output a pulse or skip a pulse.

[0158] FIG. 16 is a diagram illustrating an exemplary configuration for performing pulse skip control in a control circuit according to an embodiment.

[0159] Referring to FIG. 16, a pulse skip controller 1600 of the control circuit may include a sensing value combination unit 1610, a first comparison unit 1620, and a second comparison unit 1630, etc.

[0160] The sensing value combination unit 1610 may select one sensing value from among the sensing values ​​using a multiplexer, or may combine two or more sensing values ​​to generate one value.

[0161] When the output of the sensing value combination unit 1610 is used as a control value, the first comparison unit 1620 compares the control value with a reference value V REF_S The first comparator 1620 can compare the control value with the reference value V REF_S can be subtracted to generate an error value Vc.

[0162] The second comparator 1630 compares the error value Vc with the reference value V REF_C The error value Vc is compared with the reference value V REF_C When the error value Vc is equal to or greater than the reference value V REF_C When it is less than this, the output of the pulse enable signal can be stopped.

[0163] The control circuit can control the switch network to a third state or a fourth state to output a pulse when the pulse enable signal is output, and can perform pulse skip control so that a pulse is not output when the pulse enable signal is not output.

[0164] FIG. 17a is a diagram showing main waveforms in a first example of pulse skip control.

[0165] Referring to FIG. 17a, the control circuit determines whether the error value Vc is equal to or smaller than the reference value V REF_C When the inductor current i L The control circuit then determines whether the error value Vc is greater than the reference value V REF_Cor more, the inductor current i is regulated through a pulse shaping control that controls the switch network in the third state or the fourth state. L The waveform can be made to be a resonant waveform.

[0166] The control circuit then detects whether the error value Vc is equal to the reference value V REF_C When the inductor current i L can be made to maintain the zero level. At this time, the first switch or the fourth switch can be turned off.

[0167] The control circuit can determine whether to perform pulse shaping control or pulse skip control at a certain period or each time when the pulse shaping control ends.

[0168] FIG. 17b shows main waveforms in a second example of pulse skip control.

[0169] Referring to FIG. 17b, the control circuitry determines whether the error value Vc is greater than the reference value V REF_C When the inductor current i L The control circuit then determines whether the error value Vc is greater than the reference value V REF_C or more, the inductor current i is regulated through a pulse shaping control that controls the switch network in the third state or the fourth state. L The waveform can be made to be a resonant waveform.

[0170] The control circuit then detects whether the error value Vc is equal to the reference value V REF_C When the inductor current i L can maintain the zero level. At this time, the first switch or the fourth switch can be turned off.

[0171] On the other hand, the reference value V REF_C may be a variable value. For example, the reference value V REF_C is the inductor current iL It may be a value that is a certain multiple of .

[0172] The input of the regulator may be a first voltage and the output may be a second voltage, or the input of the regulator may be a second voltage and the output may be the first voltage.

[0173] Meanwhile, apart from what has been described with reference to FIG. 12, the control circuit can determine whether the first state is operated or not according to a pulse enable signal.

[0174] FIG. 18 is a third example diagram showing the regulator adding a first state between the third state and the fourth state.

[0175] Referring to FIG. 18, the control circuit controls the pulse enable signal and the inductor current I L The magnitude of can be used to determine whether to add a first state.

[0176] The control circuit controls the inductor current I L When ZCD (Zero Current Detection) occurs N times consecutively (N is a natural number equal to or greater than 2) (YES in S1810), the first state can be added between the third state and the fourth state, or between the fourth state and the third state (S1820).

[0177] The control circuit then regulates the inductor current I L When a state in which a pulse enable signal is generated (a state in which a rising edge occurs in the pulse enable signal) occurs M (M is a natural number greater than or equal to 2) times consecutively while maintaining a zero level (YES in S1830), the first state does not need to be operated (S1840).

[0178] FIG. 19 is a diagram illustrating an example of the input and output of a regulator according to one embodiment.

[0179] As shown on the left side of FIG. 19, the regulator may have a first voltage V1 as an input and a second voltage V2 as an output. In such an example, a load may be coupled to the node where the second voltage V2 is formed. Then, the input current i IN is supplied through the first switch Q1, and the output current i OUT is the inductor current i L It can have a waveform very similar to that of

[0180] As shown on the right side of FIG. 19, the regulator can have a second voltage V2 as an input and a first voltage V1 as an output. In such an example, a load can be coupled to the node where the first voltage V1 is formed. Then, the input current i IN is the inductor current i L and the output current i OUT can be supplied to the load via the first switch Q1.

[0181] FIG. 20 is a diagram for explaining element characteristics of a first switch in the switch network of an embodiment.

[0182] On the left in FIG. 20 is the power converter 20 described with reference to FIG. 2, and on the right in FIG. 20 is a regulator according to one embodiment.

[0183] In the power conversion device 20 described with reference to FIG. 2, an overvoltage protection IC 24 and an input stage 23 were required, but in one embodiment of the switch network 310, the first switch Q1 can perform the functions of both the overvoltage protection IC 24 and the input stage 23.

[0184] In the switch network 310 of one embodiment, the first switch Q1 may be an active element having a bi-directional body diode characteristic. For example, the first switch Q1 may be a bi-directional GaN FET or a Si-FET back to back element.

[0185] When such an active element is used in the first switch Q1, the first switch Q1 can not only function as a switching element, but also switch the switch network to state 0 when the first voltage V1 becomes higher than a certain voltage level, and function as a reverse block in the input stage.

[0186] On the other hand, a regulator according to an embodiment can be highly scalable.

[0187] When the structure in which the above-mentioned control circuit, switch network, flying capacitor, and inductor are combined is referred to as a regulator block, a single expanded regulator can be configured with a plurality of regulator blocks sharing an output.

[0188] FIG. 21 is a first exemplary block diagram of an extended regulator.

[0189] Referring to FIG. 21, a regulator 2100 can include a first regulator block 2110 and a second regulator block 2120.

[0190] The first regulator block 2110 and the second regulator block 2120 may each include a switch network according to the above-described embodiment, and the first regulator block 2110 and the second regulator block 2120 may each control the switch network in seven states from the 0th state to the 6th state described above.

[0191] The first regulator block 2110 and the second regulator block 2120 can output a second voltage V2. And, the first regulator block 2110 and the second regulator block 2120 can be arranged in parallel and share the output.

[0192] The first regulator block 2110 may include a first switch network 2111 including a 1-1 switch Q1A, a 2-1 switch Q2A, a 3-1 switch Q3A, and a 4-1 switch Q4A. The first regulator block 2110 may receive the 1-1 voltage V1A as an input and output a second voltage V2.

[0193] The second regulator block 2120 may include a second switch network 2121 including a first-2 switch Q1B, a second-2 switch Q2B, a third-2 switch Q3B, and a fourth-2 switch Q4B. The second regulator block 2120 may receive the first-2 voltage V1B as an input and output a second voltage V2.

[0194] The 1-1 voltage V1A and the 1-2 voltage V1B may be voltages having different voltage levels from each other, or may be voltages having the same voltage level from each other.

[0195] The regulator 2100 according to the first example may have a first power path through which power flows from a node to which the 1-1 voltage V1A is supplied to a node to which the second voltage V2 is output, and a second power path through which power flows from a node to which the 1-2 voltage V1B is supplied to a node to which the second voltage V2 is output.

[0196] FIG. 22 is a second exemplary schematic diagram of an extended regulator.

[0197] Referring to FIG. 22, a regulator 2200 may include a first regulator block 2210, a second regulator block 2220, a MUX circuit 2230, and the like.

[0198] The first regulator block 2210 and the second regulator block 2220 may each include a switch network according to the above-described embodiment, and the first regulator block 2210 and the second regulator block 2220 may each control the switch network in seven states, from the 0th state to the 6th state, described above.

[0199] The first regulator block 2210 and the second regulator block 2220 can output a second voltage V2. And, the first regulator block 2210 and the second regulator block 2220 can be arranged in parallel with each other and share the output.

[0200] The first regulator block 2210 may include a first switch network 2211 including a 1-1 switch Q1A, a 2-1 switch Q2A, a 3-1 switch Q3A, and a 4-1 switch Q4A, and the first regulator block 2210 may output a second voltage V2.

[0201] The second regulator block 2220 may include a second switch network 2221 including a first-second switch Q1B, a second-second switch Q2B, a third-second switch Q3B, and a fourth-second switch Q4B, and may output a second voltage V2.

[0202] The MUX circuit 2230 can selectively transmit the first-1 voltage V1A and the first-2 voltage V1B to the first regulator block 2210 and / or the second regulator block 2220.

[0203] As an example, the MUX circuit 2230 can transmit the 1-1 voltage V1A to the first regulator block 2210 and transmit the 1-2 voltage V1B to the second regulator block 2220. In this case, the regulator 2200 according to the second example can operate similarly to the regulator according to the first example (see 2100 in FIG. 21).

[0204] As another example, the MUX circuit 2230 can transmit the 1-1 voltage V1A to the first regulator block 2210 and the second regulator block 2220 simultaneously, and the MUX circuit 2230 can transmit the 1-2 voltage V1B to the first regulator block 2210 and the second regulator block 2220 simultaneously.

[0205] The MUX circuit 2230 may include an upper switch QHA, a lower switch QHB, a coupling switch QI, and the like.

[0206] The upper switch QHA can control the connection between the first input node NI1 and the first output node NO1, the lower switch QHB can control the connection between the second input node NI2 and the second output node NO2, and the connection switch QI can control the connection between the first output node NO1 and the second output node NO2.

[0207] The first input node NI1 may be supplied with a 1-1 voltage VIA, and the second input node NI2 may be supplied with a 1-2 voltage NI2. The first output node NO1 may be coupled to an input of a first regulator block 2210, and the second output node NO2 may be coupled to an input of a second regulator block 2220.

[0208] The MUX circuit 2230 can turn on the upper switch QHA and the lower switch QHB and turn off the connecting switch QI to transmit the 1-1 voltage V1A to the first regulator block 2210 and transmit the 1-2 voltage V1B to the second regulator block 2220.

[0209] Then, the MUX circuit 2230 can turn on the upper switch QHA, turn off the lower switch QHB, and turn on the connecting switch QI to transmit the 1-1st voltage V1A to the first regulator block 2210 and the second regulator block 2220 simultaneously.

[0210] And, the MUX circuit 2230 can transmit the first-second voltage V1B to the first regulator block 2210 and the second regulator block 2220 simultaneously by turning off the upper switch QHA, turning on the lower switch QHB, and turning off the connecting switch QI.

[0211] Such a parallel configuration may increase efficiency because the node at which the second voltage V2 is output sees a lower impedance.

[0212] Furthermore, since the upper switch QHA and the lower switch QHB can be used for overvoltage protection, the first-1 switch Q1A and the first-2 switch Q1B do not need to support bidirectional body diode operation.

[0213] The 1-1 voltage V1A and the 1-2 voltage V1B may be voltages having different voltage levels from each other, or may be voltages having the same voltage level from each other.

[0214] FIG. 23 is a third exemplary schematic diagram of an extended regulator.

[0215] Referring to FIG. 23, a regulator 2300 may include a first regulator block 2310, a second regulator block 2320, a switched capacitor converter 2330, and so on.

[0216] The first regulator block 2310 and the second regulator block 2320 may each include a switch network according to the above-described embodiment, and the first regulator block 2310 and the second regulator block 2320 may each control the switch network in seven states, from the 0th state to the 6th state, described above.

[0217] The first regulator block 2310 and the second regulator block 2320 can output a second voltage V2. The first regulator block 2310 and the second regulator block 2320 are arranged in parallel and can share the output.

[0218] The first regulator block 2310 may include a first switch network 2311 including a 1-1 switch Q1A, a 2-1 switch Q2A, a 3-1 switch Q3A, and a 4-1 switch Q4A, and the first regulator block 2310 may output a second voltage V2.

[0219] The second regulator block 2320 may include a second switch network 2321 including a first-2 switch Q1B, a second-2 switch Q2B, a third-2 switch Q3B, and a fourth-2 switch Q4B, and may output a second voltage V2.

[0220] The switched capacitor converter 2330 can perform both the functions of a MUX and a converter.

[0221] The MUX function of the switched capacitor converter 2330 can form a power path that transfers power from the 1-1 voltage V1A to the second voltage V2, and a power path that transfers power from the 1-2 voltage V1B to the second voltage V2, and conversely, a power path that transfers power from the second voltage V2 to the 1-1 voltage V1A, and a power path that transfers power from the second voltage V2 to the 1-2 voltage V1B can be formed.

[0222] The converter function of the switched capacitor converter 2330 allows the conversion ratio from the first-1 voltage V1A to the second voltage V2 or the conversion ratio from the first-2 voltage V1B to the second voltage V2 to be expanded to 4to1 or 3to1.

[0223] The switched capacitor converter 2330 includes a first control switch QU, a second control switch QW, a third control switch QS, a fourth control switch QL, and a flying capacitor C FLY_H may include.

[0224] The flying capacitors C included in each of the regulator blocks 2310 and 2320 FLY_L and the flying capacitor C included in the switched capacitor converter 2330. FLY_H In order to distinguish between the regulator blocks 2310 and 2320, a flying capacitor C FLY_L The first flying capacitor C FLY_L The flying capacitor C included in the switched capacitor converter 2330 is called FLY_H The second flying capacitor C FLY_H It is called.

[0225] The first control switch QU can control a connection between the first converter node NC1 and the third converter node NC3. The second control switch QW can control a connection between the third converter node NC3 and the second converter node NC2. The third control switch QS can control a connection between the intermediate node NM and the 4th converter node NO4. And, the fourth control switch QL can control a connection between the intermediate node NM and a low voltage stage (e.g., a portion to which a ground voltage is connected).

[0226] A 1-1 voltage V1A may be formed at the first converter node NC1, and a 1-2 voltage V1B may be formed at the second converter node NC2.

[0227] The third converter node NC3 may be connected to the outside of the 1-1 switch Q1A of the first regulator block 2310, and the fourth converter node NC4 may be connected to the inside of the 1-2 switch Q1B of the second regulator block 2320. Here, the outside may refer to the external side of the switch network, and the inside may refer to the internal side of the switch network.

[0228] When the fourth converter node NC4 is coupled to the inside of the first-second switch Q1B of the second regulator block 2320, the fifth converter node NC5 may be coupled to the outside of the first-second switch Q1b of the second regulator block 2320.

[0229] The second converter node NC2 may be electrically the same node as the fifth converter node NC5.

[0230] Second flying capacitor C FLY_H One side of the third converter node NC3 may be coupled to the third converter node NC3, and the other side may be coupled to the intermediate node NM.

[0231] During normal operation, a voltage that is approximately half the 1-1 voltage V1A or half the 1-2 voltage V1B may be formed at the intermediate node NM.

[0232] FIG. 24 is a diagram showing a first control state of the regulator according to the third example, FIG. 25 is a diagram showing a second control state of the regulator according to the third example, FIG. 26 is a diagram showing a third control state of the regulator according to the third example, FIG. 27 is a diagram showing a fourth control state of the regulator according to the third example, and FIG. 28 is a diagram showing main waveforms of the regulator according to the third example.

[0233] In the regulator 2300, the first regulator block 2310 and the second regulator block 2320 can be controlled in different states.

[0234] 24-28, in a first control state, regulator 2300 can control a first regulator block 2310 in a fourth state and a second regulator block 2320 in a third state.

[0235] At this time, the second flying capacitor C FLY_H can be charged.

[0236] In the first control state, the second regulator block 2320 can turn off the first-2 switch Q1B. At this time, the third control switch QS of the switched capacitor converter 2330 is turned on instead of the first-2 switch Q1B, so that the second regulator block 2320 can have the same configuration as in the third state.

[0237] In the first control state, the first control switch QU may be turned on, the second control switch QW may be turned off, the third control switch QS may be turned on, and the fourth control switch QL may be turned off.

[0238] In a second control state, the regulator 2300 can control the first regulator block 2310 in a third state and the second regulator block 2320 in a fourth state.

[0239] At this time, the second flying capacitor C FLY_H can be discharged.

[0240] In the second control state, the first control switch QU may be turned off, the second control switch QW may be turned off, the third control switch QS may be turned off, and the fourth control switch QL may be turned on.

[0241] In a third control state, the regulator 2300 can control the first regulator block 2310 in a fourth state and the second regulator block 2320 in the third state.

[0242] At this time, the second flying capacitor C FLY_H can be charged.

[0243] In the third control state, the second regulator block 2320 can turn off the first-second switch Q1B. At this time, the third control switch QS of the switched capacitor converter 2330 is turned on instead of the first-second switch Q1B, so that the second regulator block 2320 can have the same configuration as in the third state.

[0244] In the third control state, the first control switch QU may be turned off, the second control switch QW may be turned on, the third control switch QS may be turned on, and the fourth control switch QL may be turned off.

[0245] In a fourth control state, the regulator 2300 can control the first regulator block 2310 in a third state and the second regulator block 2320 in a fourth state.

[0246] At this time, the second flying capacitor C FLY_H can be discharged.

[0247] In the fourth control state, the first control switch QU may be turned off, the second control switch QW may be turned on, the third control switch QS may be turned on, and the fourth control switch QL may be turned off.

[0248] During normal operation, the second flying capacitor C FLY_H If the voltage V1b is higher than this, regulator 2300 can perform the second control state or the fourth control state two or more times in succession, and if the voltage V1b is lower than this, regulator 2300 can perform the first control state or the third control state two or more times in succession. Otherwise, regulator 2300 can perform the first control state through the fourth control state sequentially.

[0249] On the other hand, the regulator can further improve efficiency through cooperative control with the host.

[0250] FIG. 29 is a diagram illustrating cooperative control between a regulator and a host according to one embodiment.

[0251] Referring to FIG. 29, regulator 2910 can generate a power up flag PWU in host 2920, causing power supplier 2930 to provide a higher output to regulator 2910.

[0252] For example, when regulator 2910 generates and transmits a power-up flag PWU to host 2920, host 2920 can control power supplier 2930 to increase the level of first voltage V1 supplied to regulator 2910.

[0253] Higher efficiency can be achieved by continuously alternating between the third and fourth states without pulse skipping in the heavy rod. The regulator 2910 can further operate the first state when there is insufficient power from the power supplier 2930, and in the case of a power supplier whose output power is regulated, such as a PPS adapter, increase the output of the power supplier 2930 via the host 2920 to prevent the first state from operating.

[0254] On the other hand, when the output of the power supplier is higher than necessary, a pulse skip may occur, and such control can increase efficiency in a light load, but in a heavy load, the third state and the fourth state can be operated continuously and alternately without pulse skipping to achieve higher efficiency. In this way, the regulator 2910 can check whether the efficiency is sufficient in a heavy load when the first state does not operate, and if the efficiency is not sufficient, the power supplier 2930 can lower the output and generate a power down flag PWD to have optimal efficiency.

[0255] FIG. 30 is a flow chart of a method for cooperative control between a regulator and a host according to one embodiment.

[0256] Referring to FIG. 30, the control circuit of the regulator can check whether the first state operates (S3010).

[0257] Then, when it is determined that the first state is operating (YES in S3010), the control circuit can generate a power-up flag PWU to a device (eg, a host) that controls the power supplier (S3012).

[0258] Then, the power supplier can increase the output in response to this power-up flag PWU (S3014).

[0259] Then, when it is determined that the first state is a state in which the operation is not performed (NO in S3010), the control circuit does not need to generate the power-up flag PWU (S3016).

[0260] Then, the control circuit can calculate the efficiency (S3018). The efficiency can be calculated, for example, by dividing the product of the output voltage and the output current by the product of the input voltage and the current flowing through the first switch.

[0261] The control circuit compares the calculated efficiency value with the target value, and when the efficiency value is equal to or greater than the target value (YES in S3020), can return to S3010 for determining whether or not the first state operates.

[0262] Then, when the calculated efficiency value is smaller than the target value (NO in S3020), the control circuit can generate a power-down flag PWD (S3022).

[0263] Then, the power supplier can reduce the output in response to the power down flag PWD (S3024).

[0264] Then, the control circuit can return to S3010 where it determines again whether the first state is active.

[0265] As described above, the regulator according to one embodiment is capable of high-efficiency regulation in a small size.

[0266] Furthermore, since the regulator according to an embodiment can regulate regardless of the type (power control level) of the input power (first voltage or second voltage), there is no need to add a separate buck converter or boost converter, thereby reducing the size of the solution.

[0267] Furthermore, the regulator according to the embodiment is capable of switching at the LC resonant frequency, thereby minimizing power loss and increasing efficiency.

[0268] And because the regulator according to one embodiment can operate as a resonant switched capacitor converter, a small size flying capacitor is sufficient, thereby allowing the size of passive components to be reduced.

[0269] Additionally, a regulator according to one embodiment may eliminate the need for an overvoltage protection IC or input stage, reducing solution size.

[0270] Furthermore, the regulator according to the embodiment has scalability to support increased output power and multiple input sources.

[0271] As described above, according to this embodiment, the efficiency of the power conversion device can be increased, the power conversion device can be stably controlled without adding a complex configuration to the power conversion device, and the size of the power conversion device can be reduced.

[0272] The terms "comprise", "constitute" or "have" described above mean that the relevant element can be contained therein, unless otherwise specified to the contrary, and should be interpreted as including other elements without excluding other elements. All terms, including technical or scientific terms, have the same meaning as commonly understood by a person of ordinary skill in the art to which the present invention belongs, unless otherwise defined. Terms commonly used, such as predefined terms, should be interpreted as being consistent with the contextual meaning of the relevant art, and should not be interpreted in an ideal or overly formal sense unless clearly defined in the present invention.

[0273] The above description is merely an illustrative example of the technical concept of the present invention, and a person having ordinary knowledge in the technical field to which the present invention belongs may make various modifications and variations without departing from the essential characteristics of the present invention. Therefore, the embodiments disclosed in the present invention are for the purpose of illustrating, rather than limiting, the technical concept of the present invention, and the scope of the technical concept of the present invention is not limited by such embodiments. The scope of protection of the present invention should be interpreted according to the following claims, and all technical concepts within the scope equivalent thereto should be interpreted as being included in the scope of the present invention.

Claims

1. A switch network including a first switch block, a second switch block, a third switch block, and a fourth switch block connected in series to each other, a flying capacitor connected to a first node to which the first switch block and the second switch block are connected, a second node to which the third switch block and the fourth switch block are connected, and an inductor connected to a third node to which the second switch block and the third switch block are connected; a control circuit for controlling the switch network in a second state in which an inductor current forms a resonant waveform and a fourth state in which an inductor current is turned on, the control circuit controlling the switch network so that the third state and the fourth state alternate, and when a magnitude of the inductor current deviates from a required range, the control circuit controlling the switch network so that the first state or the second state is formed between the third state and the fourth state.

2. The regulator of claim 1 , wherein the control circuitry causes the third state or the fourth state to exit when the inductor current reaches a zero level.

3. 2. The regulator of claim 1, wherein the control circuit controls the switch network such that the first state is formed between the third state and the fourth state when an input voltage is less than an output voltage multiplied by R (R is a positive number equal to or greater than 2) plus a delta voltage.

4. 2. The regulator of claim 1, wherein the control circuit controls the switch network so that the second state is formed between the third state and the fourth state when a voltage of the third node is lower than a first lower limit, or controls the switch network so that the second state is formed between the third state and the fourth state when a voltage of the flying capacitor is lower than an upper limit and higher than a second lower limit.

5. 5. The regulator of claim 4, wherein the control circuit exits the third state or the fourth state before the inductor current reaches a zero level, and thereafter exits the second state when the inductor current reaches a zero level in the second state.

6. 2. The regulator of claim 1, wherein the control circuit is capable of controlling the switch network in a fifth state in which the first switch block and the fourth switch block are turned on, and controls the switch network in the fifth state when a voltage of the flying capacitor is lower than a preset voltage range.

7. 7. The regulator according to claim 6, wherein the control circuit operates a power semiconductor included in the first switch block or the fourth switch block in a linear mode in the fifth state to limit a magnitude of a current supplied to the flying capacitor.

8. 2. The regulator of claim 1, wherein the control circuit is capable of controlling the switch network in a sixth state in which the second switch block and the third switch block are turned on, and controls the switch network in the sixth state when a voltage state of the flying capacitor is higher than a preset voltage range.

9. 2. The regulator of claim 1, wherein the control circuit controls the switch network in the third state or the fourth state when a difference between a control value and a reference value is equal to or greater than a reference value, and controls the switch network in a state in which the first switch block through the fourth switch block are turned off when a difference between the control value and the reference value is smaller than the reference value.

10. 2. The regulator of claim 1, wherein a high voltage is supplied to one side of the first switch block, and a power semiconductor included in the first switch block is an active element having a bidirectional body diode characteristic.

11. a switch network including a plurality of switch elements, a flying capacitor connected to at least two connection nodes of the switch elements, an inductor connected to at least one connection node of the connection nodes, one side of the switch network being supplied with a high voltage and the other side being supplied with a low voltage; and a control circuit configured to control the switch network in a first state in which the high voltage is connected to one side of the inductor, a second state in which the low voltage is connected to one side of the inductor, a third state in which the high voltage, the flying capacitor, and the inductor are connected in series and an inductor current forms a resonant waveform, and a fourth state in which the low voltage, the flying capacitor, and the inductor are connected in series and the inductor current forms a resonant waveform, the control circuit controlling the switch network to alternate between the third state and the fourth state, and controlling the switch network so that the first state or the second state is formed between the third state and the fourth state when a magnitude of the inductor current deviates from a required range.

12. The regulator of claim 11 , wherein the control circuitry causes the third state or the fourth state to exit when the inductor current reaches a zero level.

13. 12. The regulator of claim 11, wherein the control circuit outputs a pulse enable signal at a high level when a difference between a control value and a reference value is equal to or greater than a reference value, and controls the switch network such that the first state is formed between the third state and the fourth state when the inductor current reaches the zero level N or more times (N is a natural number equal to or greater than 2) while the pulse enable signal is maintained at a high level.

14. 12. The regulator of claim 11, wherein the control circuit generates a power-up flag when the first state operates, and transmits the power flag to a device that controls the power supplier, so that a power supplier that supplies the high voltage increases output power.

15. 15. The regulator of claim 14, wherein the control circuit does not assert the power-up flag when the first state is not operational, calculates an efficiency value, and asserts a power-down flag when the efficiency value is less than a target value, causing the power supplier to reduce output power.

16. 12. The regulator of claim 11, wherein the control circuit controls the switch network in a fifth state in which one side of the inductor is floating and the high voltage, the flying capacitor and the low voltage are connected in series, and controls the switch network in the fifth state when the voltage of the flying capacitor is lower than a preset voltage range.

17. 17. The regulator of claim 16, wherein the control circuit controls the switch network in the fifth state upon initial power-up to operate power semiconductors turned on in the fifth state in a linear mode to limit the magnitude of current provided to the flying capacitor.

18. a first state in which a high voltage is connected to one side of the inductor; a second state in which the low voltage is connected to one side of the inductor; a third state in which the high voltage, the flying capacitor, and the inductor are connected in series and an inductor current forms a resonant waveform; and a fourth state in which the low voltage, the flying capacitor, and the inductor are connected in series and an inductor current forms a resonant waveform.

19. The regulator of claim 18 , further comprising a switched capacitor converter disposed at an input of the regulator block.

20. 20. The regulator according to claim 18, wherein at least two of said regulator blocks are controlled in states different from each other for said third state and said fourth state.

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