Systems and methods for a World Wide Energy Matrix (WEM)

Abstract

The present invention discloses a repeater for a wireless power beam and a satellite equipped with the repeater. The repeater is an array of coaxial waveguide elements, each element including an input polarization section, an output polarization section, and a phase shift section located between the input polarization section and the output polarization section, and the input polarization section, the output polarization section, and the phase shift section are rotatable controllably around the longitudinal axis of the coaxial waveguide, an array of coaxial waveguide elements, and a processor that controls rotation of the input polarization section, the output polarization section, and the phase shift section.

Description

Technical Field

[0001] The present application belongs to the field of wireless power transmission, particularly to the field of coaxial waveguide phase shifter arrays for wireless power transmission.

Background Art

[0002] Wireless power transmission from space-based microwave antennas and solar arrays to Earth dates back to the 1970s and is currently commonly referred to as Space Solar Power (SBSP) by modern space agencies (such as ESA, NASA, JAXA, etc.). However, it has not yet been practically implemented due to severe engineering challenges associated with kilometer-scale structures required both in orbit and on Earth.

Summary of the Invention

[0003] Generally, the present invention can mitigate some of the engineering challenges associated with SBSP and / or introduce a World Wide Energy Matrix (WEM) that is a more flexible concept, for example, using renewable or other Earth-based extensive energy sources to significantly improve the connectivity of energy supply worldwide.

[0004] According to some embodiments of the present invention, there is provided a repeater for a wireless power beam, including an array of coaxial waveguide elements, each element including an input polarization section, an output polarization section, and a phase shift section located between the input polarization section and the output polarization section, wherein the input polarization section, the output polarization section, and the phase shift section are rotatable controllably around the longitudinal axis of the coaxial waveguide, and a processor for controlling the rotation of the input polarization section, the output polarization section, and the phase shift section.

[0005] In some embodiments, the input polarization section and the output polarization section each include two pairs of diametrically opposed polarization irises protruding into the waveguide.

[0006] In some embodiments, the repeater is configured to relay a wireless power beam having a free-space wavelength λ, the wireless power beam in the waveguide has a wavelength λg, and each pair of polarization irises in the input polarization section and the output polarization section are located at a longitudinal distance of λg / 8 from the other pair of polarization irises in their respective polarization sections.

[0007] In some embodiments, the phase shift section includes three pairs of diametrically opposed phase shift irises protruding into the waveguide.

[0008] In some embodiments, the repeater is configured to relay a wireless power beam having a free-space wavelength λ, the wireless power beam in the waveguide has a wavelength λg, and the central pair of phase shift irises in the phase shift section are located at a longitudinal distance of λg / 6 from each of the other pairs of phase shift irises in the phase shift section.

[0009] In some embodiments, the coaxial waveguide element includes an inner portion defined by an inner diameter and an outer portion defined by a portion between the inner diameter and an outer diameter, and the inner portion does not permit propagation of an incident wireless power beam having a free-space wavelength λ.

[0010] In some embodiments, the inner portion is substantially hollow.

[0011] In some embodiments, the processor is located within the inner portion of the coaxial waveguide element.

[0012] In some embodiments, the repeater further includes an input pilot beam analyzer adjacent to the input polarization unit and an output pilot beam analyzer adjacent to the output polarization unit. The input pilot beam analyzer and the output pilot beam analyzer can each measure the characteristics of the incident pilot beam and transmit the measured characteristics to the processor. The processor can control the rotation of the input polarization unit, the output polarization unit, and the phase shift unit based on the measured characteristics.

[0013] In some embodiments, the array of coaxial waveguide elements is a hexagonal array.

[0014] In some embodiments, the array of coaxial waveguide elements is a linear array.

[0015] In some embodiments, the distance between two adjacent coaxial waveguide elements is between 5.0 mm and 10.0 mm.

[0016] In some embodiments, the distance between two adjacent coaxial waveguide elements is between 6.0 mm and 7.0 mm.

[0017] In some embodiments, the repeater is configured to relay a radio power beam having a free space wavelength λ, and the ratio of d / λ is less than 0.7, where d represents the distance between two adjacent coaxial waveguide elements.

[0018] In some embodiments, the repeater is configured to relay a radio power beam having a free space wavelength λ, and the ratio of d / λ is less than 0.6, where d represents the distance between two adjacent coaxial waveguide elements.

[0019] In some embodiments, the repeater further includes a reflecting surface at one end of each coaxial waveguide element.

[0020] According to some embodiments of the present invention, there is also provided a low Earth orbit satellite including a repeater described in one embodiment of the present invention.

[0021] According to some embodiments of the present invention, there is also provided a group of satellites including a plurality of low Earth orbit satellites each including a repeater described in one embodiment of the present invention.

[0022] According to some embodiments of the present invention, there is also provided a satellite including a repeater described in one embodiment of the present invention, wherein the satellite is one of a geostationary orbit (GEO) satellite, a medium Earth orbit (MEO) satellite, a polar orbit satellite, or a sun-synchronous orbit (SSO) satellite.

Brief Description of the Drawings

[0023] The subject matter of the present invention is particularly pointed out in the concluding part of the specification and is clearly claimed. However, the configuration and operation method of the present invention, as well as its objectives, features, and advantages, can be best understood by reading the following detailed description with reference to the accompanying drawings.

[0024]

Figure 1

Figure 2

Figure 3

Figure 4A

Figure 4B

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Figure 6A

Figure 6B

Figure 7

Figure 8

DETAILED DESCRIPTION OF THE INVENTION

[0025] In the following description, various aspects of the present invention will be described. For the purpose of explanation, specific configurations and details are set forth to provide a thorough understanding of the present invention. However, it will be apparent to those skilled in the art that the present invention may be practiced without the specific details presented herein. Further, well - known features may be omitted or simplified so as not to obscure the present invention.

[0026] The Worldwide Energy Matrix (WEM) system may include one or a network of ground - based RF phased - array antennas, and each antenna is operated by electricity generated from one or more sources including solar, wind, wave, hydro - power generation, and / or geothermal (e.g., renewable energy sources). This electrical energy is converted, for example, usually using solid - state or vacuum - tube power amplifier technology operating at microwave frequencies, into electromagnetic waves that are transmitted into space as a parallel beam through the amplitude and phase distributions at the phased - array aperture. These ground - based transmitter units may be the transmitter units described in PCT International Application No. PCT / IB2020 / 060595 (International filing date November 11, 2020), which claims the benefit of U.S. Provisional Patent Application No. 62 / 934,511, filed November 12, 2019, and Australian Patent Application No. 2019904254, filed November 12, 2019, all of which are incorporated herein by reference.

[0027] The WEM system may further include one or more satellites (e.g., a satellite constellation or satellite formation) that operate with a ground transmitter. The transmission beam may be electronically steered by the transmitter towards such orbiting satellites. For example, the satellite may transmit a radio frequency homing signal that provides information regarding the satellite's position to the ground transmitter. The homing signal may be generated, for example, by a dedicated antenna system mounted on the orbiting satellite that operates at a different frequency compared to the power beam and has a significantly reduced power level. Also, to guide the power beam radiated from the satellite, the power may be transmitted in the direction opposite to the direction from the satellite to the Earth using the homing signal generated by the ground transmitter. In some embodiments, the homing signal is incorporated into the electromagnetic beam as a data stream, enabling simultaneous transfer of power and data.

[0028] It should be understood that the dimensions of the transmitter antenna can be derived based on the wavelength of the power beam and / or the distance required for transmission as a parallel beam to the satellite. Examples of the dimensions of the ground and satellite-based antenna arrays are shown herein.

[0029] The satellite may receive the incident parallel power beam from the transmitter array using a receiving antenna. Upon receiving the power beam, the satellite can transfer the power beam (or substantially all of the power beam) to one or more locations such as one or more satellites within the satellite constellation, or one or more locations on Earth, or a combination thereof (e.g., power beam splitting).

[0030] Figure 1 shows a schematic diagram of a World Wide Energy Matrix (WEM) configuration 100 according to some embodiments of the present invention, provides an example of the basic concept, and illustrates (by way of example) two ground transmitters and nine satellites. The orbiting satellites 110 form a matrix of relay nodes for power beams from the Earth to the satellites, from the satellites to the Earth, and / or from satellite to satellite. The dual-purpose (e.g., transmitter and receiver: transceiver) Earth-based microwave phased array antenna 120 converts terrestrial electricity into an electromagnetic beam transmitted to an orbiting node (e.g., a satellite). The same ground antenna can also receive an electromagnetic beam from an orbiting node and convert it into electricity by rectification.

[0031] The WEM according to embodiments of the present invention may be provided as a group of orbiting satellites of one or more different types. For example, the group of satellites may include low Earth orbit (LEO) satellites, geostationary orbit (GEO) satellites, or a combination of LEO satellites and GEO satellites. The group of satellites may also include one or more satellites having other satellite orbit types such as medium Earth orbit (MEO) satellites, polar orbit satellites, or sun-synchronous orbit (SSO) satellites. The WEM may include a sufficient number of satellites to supply beam energy to a wide area of the world, such as a continent or ocean, and / or locations around the world.

[0032] Alternatively, the WEM (or a part thereof) according to some embodiments of the present invention may include a plurality of ground transmitters and one satellite, and the satellite functions to receive power beamed from a transmitter antenna at a first ground location and, without transferring it to a second satellite, functions as a transmitter to transfer a power beam to a receiving antenna (rectenna) at a second ground location. The satellite may be, for example, a LEO satellite such as a polar orbit satellite. For example, a single LEO satellite can traverse the circumferential surface area of the Earth, receive power from a ground transmitter at a first location (e.g., the North Pole), transmit it to a second location (e.g., the South Pole), and retransmit the power to a ground receiver at the second location.

[0033] On Earth, substantially the same phased array antenna technology used in the transmitter may be used to receive an incident parallel power beam from any space-based satellite platform. To guide the beam to the intended destination on Earth, a homing signal may be transmitted from a ground receiving antenna to an orbiting satellite.

[0034] The incident electromagnetic beam may be converted into an electrical signal and transferred to a rectifier circuit to supply the attached load or to convert it to DC electricity, such as for connection to an existing power grid after conversion to AC.

[0035] The ground antenna that can be used in embodiments of the present invention may be a dedicated transmitter (e.g., disposed close to a power source) and another dedicated receiver (e.g., close to a load). According to some embodiments of the present invention, the same ground antenna uses a waveguide-based coupler / splitter network between the antenna radiating element and its source (for transmission) or rectifier circuit (for reception), and uses microwave engineering components such as circulators, isolators, quadrature mode transducers, and / or waveguide switches to separate and isolate the contributions of the incident and outgoing waves, and thus can be used for both the transmission and reception functions.

[0036] In some embodiments, one or more orbiting satellites may include a receiving surface incorporating an array of phase correction elements that transfer and / or refocus (e.g., re-collimate) the incident beam to the intended target or the next station (e.g., ground- or space-based). As further described herein, the satellite may be equipped with a reflective surface or a transmissive phase correction surface, or a combination of both.

[0037] Figure 2 shows a schematic diagram of a satellite including a combination of a reflective phase compensator front face and a transmissive phase compensator front face according to some embodiments of the present invention. Satellite 200 may include a reflective phase corrector 210 for a power beam from the satellite to the Earth or from the Earth to the satellite. The satellite may also include a bidirectional transmissive phase corrector 220 for a power beam from satellite to satellite. The three phase correctors may share a common axis of rotation 230.

[0038] In some embodiments, one or more reflective phase correctors 210 are used for power beam propagation from space to Earth and from Earth to space. The reflective phase corrector may include, for example, an array of open waveguide structures (e.g., coaxial waveguide element 500 further described in FIG. 5) terminated by a mechanically adjustable short-circuit end plate or solid-state electronic device to achieve a phase shift. The phase of the reflected waves from each array element can cause a phase distribution at the exit aperture, resulting in radiation in a desired beam direction with desired focusing characteristics. The position of the intended target may be provided by a homing signal transmitted from the position of the target on Earth. A processor onboard the satellite can calculate the reflection angle for directing the received energy towards the target and control the parameters of the phased array to do so.

[0039] In some embodiments, the transmissive phase corrector 220 is used to refocus a power beam from one satellite to an adjacent satellite within the same satellite constellation, i.e., for space-to-space propagation of the power beam. In some embodiments, the transmissive phase corrector can provide a phase distribution at the exit aperture while passing through the incident wavefront to focus and steer the outgoing beam. This may be implemented, for example, as a microwave lens with fixed or configurable phase correction elements at the aperture. The configurable device is realized by mechanical control, electrical control, or a combination of electrical and mechanical control.

[0040] According to some embodiments, a satellite may be provided that includes a combination of a reflective phase - compensating front and a transmissive phase - compensating front. For example, as shown in FIG. 2, the satellite enables two - way beam propagation between satellites, from the satellite to the Earth, and from the Earth to the satellite. The three phase correctors may share a common axis of rotation 230.

[0041] The configuration of FIG. 2 enables the transfer of a power beam from space, which propagates through the orbital ring of the transmissive phase corrector (shown in the satellite cluster in FIG. 1), to a terrestrial - based target by steering it to hit one of the reflective phase correctors. The pair of reflective phase correctors enables the transfer of the power beam from space to the Earth in either direction, i.e., clockwise or counter - clockwise around the satellite's orbital link.

[0042] It should be noted that only a small angular deviation of the power beam is required between satellites or between the Earth and the satellite. As a result, usually, it is not necessary to use many densely packed phase - shift elements on the surface of either the transmissive phase corrector or the reflective phase corrector, as would typically be implemented with electronically steered phased - array antennas. The small angular deviation of the power beam can be achieved, for example, by using a simpler phase - shift configuration that requires only four phase shifters, with each phase shifter applied to one quadrant of the aperture of the phase corrector. This can significantly reduce the complexity and cost of the phase - shift mechanism of the beam from space required for small - angle steering of the satellite phase corrector.

[0043] It should be understood that the antenna shape shown in FIG. 2 is an example, and depending on the implementation, other antenna array shapes are possible. This configuration may be extended to include lateral propagation by adding an arrangement similar to the reflective and transmissive phase correctors mounted at 90 degrees above or below that shown in FIG. 2.

[0044] In the case of satellites in LEO, each member of the satellite constellation may have a significant relative velocity with respect to an observer on Earth. As an example, at an altitude of 400 km, a satellite typically moves at a speed of about 7300 m / s (about Mach 23) relative to the Earth. Therefore, real-time tracking by the ground transmit / receive antennas of the WEM system may be required. This can be achieved, for example, by the homing signals described above in conjunction with electronic beam steering of the antenna array.

[0045] In the case of satellites in GEO, the distance to the Earth is 36000 km, the orbit is synchronized with the Earth's rotation, and the satellite appears to be stationary to an observer on Earth. In a GEO configuration, typically only small Earth-based beam steering corrections are anticipated.

[0046] (Beamforming in the near field) The satellite or repeater of the WEM according to some embodiments of the present invention may use a radiating near-field beam propagation system. Despite the fact that a clearly long distance is involved in beam propagation from space to Earth, by appropriately selecting the antenna dimensions for a given wavelength and antenna separation distance using embodiments of the present invention, it is possible to create a radiating near-field scenario (Fresnel region) that optimizes the beam collection efficiency. Equation 1 can provide the relationship between antenna dimensions, wavelength, and range in the form of a dimensionless parameter c called the Fresnel number. This parameter c can be defined by an appropriate amplitude distribution at the antenna aperture, such as the antenna aperture that maximizes the value of the beam collection efficiency. The amplitude distribution can take the form of an angularly oblate spheroidal wave function with the parameter c as the independent variable. The phase distribution of the electric field at the antenna aperture can be determined by the focusing electric field condition that equalizes the path lengths from the transmitting antenna element to the center of the receiving aperture. Using the present invention, for example, by setting a given Fresnel number to a value exceeding 4, a beam collection efficiency exceeding 99% can be achieved, whereby the present invention can substantially eliminate energy leakage at the receiving aperture. This can improve the efficiency of the system and / or limit the beam to an area smaller than the antenna size, thereby improving the safety of the system in a manner not normally achievable with far-field systems.

[0047] The beam collection efficiency may be characterized by a dimensionless parameter c, as defined by Equation 1 below. The beam collection efficiency is typically for a square transmitting antenna of dimension D r focused on a receiving aperture of range R and wavelength λ, and is an important parameter in the oblate spheroidal wave theory for specifying the optimal amplitude taper. t

Equation

[0048] The spheroidal wave function is an eigenfunction of the Fourier integral and can be converted into the same function form, so it can have very advantageous characteristics for wireless power transmission.

[0049] FIG. 3 is a diagram of the optimal beam collection efficiency for parameter c according to some embodiments of the present invention. As described above, the beam collection efficiency can be increased by increasing the value of c. For a value of c≧4, the beam collection efficiency exceeds 99%.

[0050] Examples of the dimensions of the antenna and the orbital phase corrector are shown below.

[0051] Assuming an example frequency of 5.8 GHz (wavelength of about 52 mm), a ground antenna with a size of 1000 m square can generate a focused beam spot with a diameter of about 100 m at a distance of 400 km (e.g., LEO altitude) with a beam collection efficiency of about 99.9%. A size of 100 m is approximately equivalent to the size of an existing International Space Station (ISS).

[0052] In this example, a satellite aperture with a diameter of 100 m may be used to refocus the beam to an adjacent satellite with the same receiving aperture size using the same optimized amplitude taper and phase taper as used in the uplink from the Earth to space. At this satellite aperture size (100 m), power can be beamed to an adjacent satellite approximately 50 km away with a beam collection efficiency of about 99.9%.

[0053] In the case of a GEO-based configuration, with optimal beamforming over a range of approximately 36000 km and the same size square transmitting and receiving apertures, the antenna size becomes 2200 m and the beam collection efficiency becomes approximately 99%. By increasing the size of the transmitting antenna on Earth to 9500 m, the size of the receiving aperture in orbit can be reduced to 950 m while maintaining the same beam collection efficiency of 99%.

[0054] In the case of satellite-to-satellite beam propagation with the GEO configuration of this example, an emission aperture with a diameter of 950 m from the satellite allows beam propagation over a distance of 6700 km (between satellites) while maintaining a beam collection efficiency of 99%.

[0055] Due to the effect of beam focusing that becomes effective in the near field, the size of the receiving aperture (for example, the receiving aperture of a satellite in orbit) can be significantly reduced compared to the transmitting aperture, which can help significantly reduce the launch cost and the cost of placing hardware in space. This is embodied in the dimensionless ratio represented by parameter c in Equation 1, allowing the use of receiving and transmitting antennas of different sizes while still maintaining the value of c to match a high beam collection efficiency.

[0056] Therefore, the Worldwide Energy Matrix (WEM) may include the generation and control of steerable parallel microwave beams as a means to achieve efficient long-distance wireless power transmission between a transmission location and a reception location.

[0057] Embodiments of the present invention may include using an intermediate orbit repeater to transfer a power beam from one location to another. Each repeater may include at least one large aperture, such as a planar aperture, incorporating beam steering and beam forming functions in either reflection mode or transmission mode. Such a structure may be implemented using a plurality of nominally identical phase shift elements arranged in a periodic lattice spanning a plane. In various embodiments, the shape of the lattice is square or hexagonal, as shown in FIGS. 4A and 4B respectively. Assembling a plurality of elements into an array using a modular or element-by-element configuration facilitates in-space assembly (such as by unmanned means using robots) and can reduce the size of the payload (both in physical dimensions and mass), thereby reducing the launch cost and placement cost (such as launch fuel efficiency).

[0058] FIG. 5 schematically shows the components of a repeater according to some embodiments of the present invention. A repeater for a wireless power beam according to some embodiments of the present invention may include an array of coaxial waveguide elements 500. Each element 500 may include an input polarization section 510-a, an output polarization section 510-b, and a phase shift section 520 located between the input polarization section 510-a and the output polarization section 510-b, respectively. The input polarization section 510-a, the output polarization section 510-b, and the phase shift section 520 may be controllably rotatable around the longitudinal axis 530 of the coaxial waveguide element 500. A processor (e.g., the processor 805 described later in FIG. 8) may be used to control the rotation of the input polarization section 510-a, the output polarization section 510-b, and the phase shift section 520.

[0059] In some embodiments, the array of coaxial waveguide elements 500 is a hexagonal array (as shown, for example, in FIG. 4B). In some embodiments, the array of coaxial waveguide elements is a linear array (as shown, for example, in FIG. 4A). An array of a plurality of coaxial waveguide elements 500 may form a repeater for a wireless power beam. For example, the array may include from several hundred to hundreds of millions of coaxial waveguide elements 500.

[0060] In some embodiments, the distance between two adjacent coaxial waveguide elements (e.g., between the elements 500 of the array in FIGS. 4A and / or 4B) is from 5.0 mm to 10.0 mm. In some embodiments, the distance between two adjacent coaxial waveguide elements is from 6.0 mm to 7.0 mm. The distance between adjacent elements may be less than one free space wavelength, for example, half of the wavelength. This may ensure that the array does not generate additional diffraction orders (e.g., grating lobes) during operation.

[0061] When irradiated by an incident power beam, the relay according to some embodiments of the present invention may be used to change the beam direction and focus characteristics of the beam by controlling the phase of the reflected wavefront or transmitted wavefront. Each phase shift element in the relay array can be designed to be adjustable within a range of phase shifts from 0 to 360 degrees, thus providing complete control of the generated wavefront.

[0062] The phase distribution of a particular relay aperture can be determined by a pair of pilot beam waveforms radiated from the source aperture and the target aperture. Each pilot beam can irradiate one side of the relay surface. Each pilot beam may be generated by an electrically small radiating element disposed at the center of the receive / transmit aperture. Electrically small can mean an antenna having dimensions equivalent to or less than the operating wavelength. The electrically small radiating element can radiate a spherical wavefront whose frequency and polarization are the same as those of the power beam, but whose power is lower than that of the power beam and whose direction is nominally towards one surface of the relay aperture. Alternatively, the spherical wavefront of the pilot beam is in the far-field (Fraunhofer region) of the intended target aperture, i.e., can be realized using any antenna in the range of 2D2 / l or more, where D is the maximum dimension of the pilot beam radiating antenna and l is the wavelength.

[0063] The relay element can measure the polarization of the incident pilot beam. The relay can measure the phase difference between the two pilot beams at each element of the array and determine the correct phase shift information to transfer and / or refocus the power beam from the source to the intended target.

[0064] The relay can operate in a transmission mode (e.g., similar to a lens) of the relay operation, thereby implementing phase delay or phase advance distribution across the entire array of phase shifters while minimizing power loss within the relay. The latter requires advanced impedance matching to minimize reflection from the relay and the use of highly conductive materials (e.g., metals) to minimize heat dissipation.

[0065] The repeater can operate in reflection mode, whereby the output port of the phase shifter can be terminated (e.g., short-circuited) with a mere reflecting surface, whereby the outgoing wavefront is totally reflected, but different phase delays / phase advances are induced across the entire outgoing beam, steering the beam to different positions and refocusing it. In some embodiments, the repeater includes a reflecting surface at one end of each coaxial waveguide element.

[0066] In the transmission and / or reflection modes of operation of the repeater, an adjustable phase shift element may be required, which phase shift element has low loss (e.g., 0.1 dB transmission loss) and is sufficient to provide a phase shift at an incident microwave power level that can be tens to hundreds of watts per phase shift element, or up to 1 kW. To meet these design objectives, such a phase shift element may include a passive highly electrically conductive metal element disposed within an air or vacuum filled waveguide, and no active electronics (semiconductors) or lossy materials (e.g., ferrites or dielectrics) are disposed in the path of the microwave beam. Such a phase shift structure is described in the following chapter and may be based on a coaxial waveguide configuration. For satellite and aircraft mounted applications, it is desirable to have a lightweight and mechanically rigid structure. Such a structure can be realized by using substantially hollow elements (to reduce weight) and assembling them into a honeycomb-like array to provide mechanical rigidity. Honeycomb structures are common in aerospace applications where low weight and high rigidity are required characteristics within the same structure.

[0067] (Phase shifter element for coaxial waveguide) The operating principle of the phase shifter proposed according to an embodiment of the present invention is based on the length of a metal waveguide consisting of two circular coaxial cylinders. One advantage of using a coaxial waveguide element (e.g., element 500 shown in FIG. 5) as opposed to a conventional hollow cylinder is that it allows for a smaller element separation when forming a repeater structure by arranging a plurality of waveguides side by side into an array as needed.

[0068] When considering the limits of beam steering and beamforming performance of a periodic array of phase-shifting elements, the element spacing d with respect to the operating wavelength λ can be considered. Generally, the smaller the value of d / λ, the wider the range of possible repeater beam scanning angles without grating lobes.

[0069] In some embodiments, the repeater is configured to relay a radio power beam having a free-space wavelength λ, the ratio of d / λ is less than 0.7, and d represents the distance between two adjacent coaxial waveguide elements. In some embodiments, the ratio of d / λ is less than 0.6. In some embodiments, the distance between two adjacent coaxial waveguide elements (e.g., between elements 500 of the array) is 5.0 mm to 10.0 mm. In some embodiments, the distance between two adjacent coaxial waveguide elements is 6.0 mm to 7.0 mm. When arranged in a large periodic array (usually, for example, the square lattice or hexagonal lattice shown in FIGS. 4A and 4B), the cylindrical coaxial waveguide element can support a transverse electric mode with a mode index of m = n = 1 (e.g., TE11). This can be excited in the region between the inner conductor and the outer conductor. The TE11 mode is not the fundamental mode of this type of coaxial waveguide, but a transversely electromagnetic mode with rotational symmetry (e.g., TEM). However, when the array is irradiated with an incident plane wave, the symmetry of the array can prevent the excitation of TEM, and the higher-order TE11 mode can be generated in the space between the conductors.

[0070] FIG. 6A shows the electric and magnetic field lines of the TE11 mode of a circular coaxial waveguide according to some embodiments of the present invention. FIG. 6B shows the electric and magnetic field lines of the TE11 mode mainly with horizontal polarization according to some embodiments of the present invention.

[0071] The inner radius and outer radius of the coaxial waveguide, denoted by b and a respectively, can be set so that the TE11 mode can propagate through the waveguide without being cutoff at the operating frequency. The cutoff wavelength λ c11 of the TE11 mode of the circular coaxial waveguide is approximately given by the average circumference of the two cylindrical conductors, that is, λc11 It is approximately equal to π(a + b). The minimum element spacing within such an array of waveguides is approximately equal to the outer diameter, and as shown in FIG. 6A, d = 2a.

[0072] Assuming that a circular waveguide supporting the TE11 circular waveguide mode operates at the same frequency as a coaxial waveguide supporting its own TE11 coaxial mode and has the same waveguide wavelength, the diameter of the element for this circular waveguide is given by D = 1.841(a + b).

[0073] Therefore, the elements for the coaxial waveguide can provide a more compact array spacing with respect to the wavelength than circular waveguides having the same propagation characteristics. As an example, consider a frequency of 14 GHz (free - space wavelength = 21.4 mm) for a coaxial waveguide with a = 6.225 mm and b = 2.905 mm. In this case, the ratio d / λ = 0.58. The diameter of a circular waveguide having the same frequency and the same propagation constant is D = 16.8 mm, and the ratio D / λ = 0.77.

[0074] The TE11 mode can have two independent orthogonal polarization states within the coaxial waveguide. In one state, the electric field is mainly vertically polarized, with maximum values at 12 o'clock and 6 o'clock and zero electric field at 9 o'clock and 3 o'clock. In the other state, the electric field is mainly horizontally polarized, with maximum values at 3 o'clock and 9 o'clock and zero electric field at 12 o'clock and 6 o'clock (see FIGS. 6A and 6B). This dual - polarization mode spectrum can be useful for the operation of phase shifters.

[0075] In some embodiments, the region where the radius of the coaxial waveguide is smaller than the radius b of the inner conductor can remain completely hollow and does not need to be surrounded by a metal end - cap or made of a solid material. Mechanically, when the coaxial waveguide is incorporated into a densely packed array similar to a honeycomb structure, it can provide a very lightweight and rigid structure. Therefore, it is well - suited for aircraft - mounted and satellite - mounted applications where weight reduction is a strongly desired design goal.

[0076] From an electromagnetic perspective, the innermost hollow cylindrical region forms a circular waveguide that is blocked at the operating frequency. The diameter of the circular waveguide is too small to allow even the lowest-order waveguide mode to propagate. Only the coaxial region between the outer conductor and the inner conductor permits wave propagation. The center of the hollow region can be completely shielded from any incident microwave radiation. This can be advantageously used as it can provide an appropriate location for electronic devices, mechanical devices, or electromechanical devices that avoid interference by the incident microwave power beam.

[0077] For example, in some embodiments of the present invention, the coaxial waveguide element includes an inner portion defined by the inner diameter and an outer portion defined by the portion between the inner diameter and the outer diameter. The inner portion does not permit the propagation of an incident radio power beam having a free-space wavelength λ. In some embodiments, the inner portion is substantially hollow. In such embodiments where the inner portion is substantially hollow, a processor (for example, a processor that controls the rotation of the polarization section and the phase shift section) may be disposed within the inner portion of the coaxial waveguide element.

[0078] In contrast to using active semiconductor devices, implementing phase shifts using passive waveguide structures has the advantages of (1) being able to keep the insertion loss very low (less than 0.1 dB), for example, by using highly consistent metal elements, and (2) being able to handle high levels of incident microwave power (for example, tens to hundreds of watts, up to 1 kW) far exceeding what is possible with semiconductors.

[0079] To implement the phase shift element, the length of the coaxial waveguide can be divided into five portions connected in series in a cascade. As shown in FIG. 5, the above portions are (i) a "pilot wave analyzer" portion (502-a) including a polarization sensor and a phase detector for analyzing one (two) of the pilot waves incident on one side of the repeater, (ii) an input polarizer portion (510-a) that converts incident linear polarization into circular polarization, (iii) A central part (520) that imparts a phase shift to the circular polarization output from the input polarizer part according to the rotation angle with respect to other parts; (iv) An output polarizer part (510-b) that converts the phase-shifted circular polarization output from the central part back into a linearly polarized light having the same polarization as the input wave; (v) A second pilot wave analyzer part (502-b) that is the same as (i) but is intended to be used together with a second pilot wave that irradiates the opposite side of the repeater.

[0080] These components will be described in more detail below.

[0081] (Pilot Wave Analyzer) In some embodiments, the pilot wave is used to provide phase and polarization information for determining the angular orientation of the polarizer part and the phase shift part.

[0082] The pilot beam can be emitted by a low-power emitter that emits electromagnetic radiation generated by a small antenna disposed at the center of each repeater aperture, each ground transmitter and / or receiver aperture. The pilot beam can generate a spherical wavefront with the same frequency and polarization as the power beam that impinges on the adjacent repeater surface. The spherical wavefront irradiating one surface of the repeater can mimic the wavefront of a point source emitter located at the center of the radiating repeater / antenna aperture. This wavefront may include information regarding the polarization of the irradiating power beam and information regarding the phase shifter settings at the repeater aperture that can be imparted to the beam to focus and steer it to the intended target of the power beam.

[0083] Two separate pilot beams can be used for a single repeater. One pilot beam can irradiate one side of the repeater aperture, and the remaining pilot beam can irradiate the other side. FIG. 7 shows two pilot beams for each, and an example of a three-repeater configuration where both sides of the repeater are irradiated by the respective pilot beams.

[0084] The pilot beam analyzers 502-a and 502-b are incorporated into the first and last parts of the phase shifter device 500 and serve to determine the polarization of the incident pilot beam and the phase difference between the two pilot beams that irradiate either side of the repeater surface.

[0085] In some embodiments, a pair of directional couplers 505 built into the inner conductor of the coaxial waveguide are used throughout the structure. The directional coupler may include a small coupling aperture disposed within the waveguide wall, and the coupling aperture samples a small amount of the wave propagating in a single direction rather than in the reverse direction within the waveguide. The directional coupler can be a directional coupler known in the art.

[0086] For example, two directional couplers may be used within each pilot wave analyzer, and one coupler may be attached at 90 degrees to the other around the inner conductor so as to be sensitive to two orthogonal polarizations of the incident wave.

[0087] The output from each directional coupler may be supplied to a microwave circuit within the hollow interior of the inner conductor of the coaxial waveguide. The polarization of the incident pilot beam may be determined by measuring the relative amplitudes of each orthogonal pair of couplers. The polarization of the incident pilot beam may be used to control the rotational positions of two polarizer sections (e.g., 510-a, 510-b) so as to orient the polarizer at the correct 45-degree angle with respect to the incident electric field vector.

[0088] The phase difference between two pilot beams irradiating each face of the repeater may be measured by a microwave phase comparison circuit mounted within the hollow interior of the coaxial waveguide. The phase comparison circuit can determine the phase difference between the pilot beams using the microwave outputs from the directional couplers at each end of the coaxial structure. This phase difference information may be used to control the rotational movement of the central phase shifter section so as to correctly focus the incident power beam onto the intended target aperture. Focusing the beam may be equivalent to equalizing the path lengths through each coaxial waveguide element of the repeater, like a lens.

[0089] The repeater according to some embodiments of the present invention further includes an input pilot beam analyzer section 502-a adjacent to the input polarization section 510-a and an output pilot beam analyzer section 502-b adjacent to the output polarization section 510-b. The input pilot beam analyzer 502-a and the output pilot beam analyzer 502-b can each measure the characteristics of the incident pilot beam and can transmit at least one measured characteristic to the processor. The processor can control the rotation of the input polarization section 510-a, the output polarization section 510-b, and the phase shift section 520 based on at least one measured characteristic (e.g., is configured to do so).

[0090] (Polarizer) The two polarizer sections (ii) and (iv) (e.g., the input polarization section and the output polarization sections 510-a and 510-b) may have the same configuration (e.g., 512). The generation of a circularly polarized wave from a linearly polarized input is realized by introducing two pairs of diametrically opposed iris sections between the inner conductor and the outer conductor of the coaxial waveguide shown in FIG. 5.

[0091] For example, in the repeater according to some embodiments of the present invention, the input polarization section and the output polarization section each include two pairs of diametrically opposed polarization irises (collectively referred to as 512) that project (e.g., open) into the waveguide 500.

[0092] The iris 512 itself may include a narrow-angle wedge 515 that interacts with the TE11 mode in the waveguide in different ways depending on the polarization of the incident mode spectrum. As shown in FIG. 5, two pairs of diametrically opposed polarized irises can generate four (e.g., 2×2) narrow-angle wedges. The incident linearly polarized input may be decomposed into two orthogonally polarized TE11 modes, and the relative amplitude of each mode may be a function of the orientation of the incident electric field. When the polarization orientation of the incident linearly polarized light is determined by the pilot-wave analyzer described herein (see (i) and (v)), and the position of the input polarizer of the iris element is 45 degrees with respect to the incident wave, a circularly polarized output is obtained.

[0093] By arranging the iris at 45 degrees with respect to the incident polarization vector, the incident TE11 coaxial waveguide mode may be split into two orthogonally polarized states of equal magnitude. The two resulting modes may be oriented such that the electric field maximum in one mode coincides with the iris and the electric field zero in the orthogonal mode coincides with the iris.

[0094] In the latter case, the iris has substantially no effect on the TE11 mode, and the components of this wave propagate without being impeded by a phase shift determined only by the phase velocity of the coaxial waveguide and its length.

[0095] In the former case, the iris strongly interacts with the co-polarized component of the TE11 mode and may function as a shunt susceptance element whose effect is easily determined by a well-known transmission line model such as the ABCD matrix method. By carefully designing the shape of the iris element and correctly selecting the spacing between each pair of iris along the waveguide axis, the phase shift of this component of the TE11 mode can be phase-shifted by 90 degrees from the orthogonal TE11 mode component, and at the same time the impedance can be matched to avoid generating a reflected wave. As a result, since the two equal-amplitude waveguide modes are phase-shifted by 90 degrees, circular polarization is realized at the output of the polarizer section.

[0096] In FIG. 5, the individual iris 515 of the polarization iris (e.g., 512-a and 512-b) may be separated from each other by one-eighth (λg / 8) of the waveguide wavelength, and the equivalent normalized shunt susceptance of the iris pair is b1 = 2 for one polarization state and b1 = 0 for the orthogonal mode. Thereby, a non-reflective structure can be realized for both polarization states while generating a 90-degree phase difference between the two TE11 mode components.

[0097] In some embodiments, the repeater is configured to relay a wireless power beam having a free-space wavelength λ, the wireless power beam in the waveguide has a wavelength λg, and each pair of polarization irises in the input polarization section and the output polarization section are located at a longitudinal distance of λg / 8 from the other pair of polarization irises in their respective polarization sections.

[0098] In various embodiments, since three or more irises are used, the overall length of the device increases, the complexity increases, and / or the dissipation loss increases.

[0099] (Phase shift section) For example, the central portion 520 of the coaxial waveguide element gives a phase shift that can vary between 0 and 360 degrees by rotating the inner conductor with respect to the other portions. The phase shift can be realized by three pairs of antiparallel irises having a wedge shape 525 (e.g., the same or different) similar to those (e.g., wedge shape 515) each used for the polarizer section and connected to the inner conductor. As shown in FIG. 5, the three pairs of antiparallel irises generate six (e.g., 3×2) wedges 525. In the phase shifter shown in FIG. 5, the central iris (collectively referred to as 522) is a wedge (e.g., wedge 525) and is one-sixth (λ gThey are separated from each other by a distance equal to (e.g., / 6). The iris can cause different phase shifts for the electric field component parallel to the longitudinal section including the iris and the electric field component perpendicular to the longitudinal section. The iris can match the impedance for both the parallel polarization field and the perpendicular polarization field, and the purpose is to make the phase difference between the two states 180 degrees. In the case of parallel polarization, the equivalent normalized shunt susceptance of each iris pair is given by b2 = 2.31, and in the case of parallel polarization, b2 = 0. The output obtained from the central part is a non-reflecting circularly polarized light wave having a phase shift of θ / 2 degrees with respect to the circularly polarized input, where θ is the rotation angle of the inner cylinder.

[0100] In the repeater according to some embodiments of the present invention, the phase shift unit includes three pairs of phase shift irises protruding (e.g., opening) into the waveguide in opposite directions. In some embodiments, the repeater may be configured to relay a radio power beam having a free space wavelength λ, the radio power beam in the waveguide has a wavelength λg, and the central pair of phase shift irises in the phase shift unit are located at a longitudinal distance of λg / 6 from each of the other pairs of phase shift irises in the phase shift unit.

[0101] In various embodiments, other combinations of iris shunt susceptances are used for the central phase shift section. To maintain a non-reflecting (e.g., impedance-matched) structure, the outermost two pairs of the three irises have the same design, and the central iris is selected to have a susceptance that provides a matching state for a specific longitudinal separation between the irises. The design shown in FIG. 5 represents a particularly simple and compact structure over the entire length by using three pairs of identical irises arranged at intervals of λ g / 6.

[0102] In some embodiments, the rotation of the central phase shifter section 520 is realized by electromechanical means, for example, by using a brushless electric motor. The iris section within the coaxial region may be made of a magnetic material that forms the stator of a switched reluctance motor design. By applying an external magnetic field via small electromagnets that operate in a switching sequence and are attached around the outermost hollow region, means are provided to actuate the rotational movement required for the phase shifter. The rotational movement of the polarizer section may also be realized in a manner similar to the phase shifter section.

[0103] Any active components used in a phase shifter array element that require a DC power source, such as an electric motor and sensing electronics, can obtain the required power from various possible sources within the array. Examples include rectified microwave power collected from an incident power beam via a photovoltaic solar cell or a rectenna element built into the array. Thus, the need for a battery (which has a limited storage / recharge life) is eliminated, and the overall weight, which is an important consideration for aircraft / satellite-mounted platforms, is reduced.

[0104] FIG. 8 shows a block diagram of an exemplary computing device that may be used in an embodiment of the present invention. The computing device 800 may include a controller or computer processor 805, which may be a central processing unit processor (CPU), a chip, or any suitable computing device, an operating system 815, a memory 820, a storage device 830, an input device 835, and an output device 840, such as a computer display or monitor for displaying a computer desktop system and the like.

[0105] The operating system 815 may be code that performs tasks including adjusting, scheduling, arbitrating, or managing the operation of the computing device 800, such as scheduling the execution of programs, or it may include the same. The memory 820 may be, for example, a random access memory (RAM), a read-only memory (ROM), a flash memory, a volatile memory or a non-volatile memory, or other suitable memory unit or storage unit, or may include them. At least a part of the memory 820 may include data storage stored online in the cloud. The memory 120 may be a plurality of different memory units, or may include them. The memory 120 may store instructions (e.g., code 825) for executing the methods disclosed herein, such as controlling the rotation of one or more elements of the coaxial waveguide according to an embodiment of the present invention. The memory 820 may use a data store such as a database.

[0106] The executable code 825 may be any application, program, process, task, or script. The executable code 825 may be executed by the controller / processor 805, optionally under the control of the operating system 815. For example, the executable code 825 may be one or more applications that execute the methods disclosed herein, such as controlling the rotation of the input polarization unit, the output polarization unit, and the phase shift unit, and may execute such applications. In some embodiments, two or more computing devices 800 or components of the device 800 may be used. One or more processors 805 may be configured to execute embodiments of the present invention, for example, by executing software or code.

[0107] The memory device 830 may be, for example, a hard disk drive, a floppy disk drive, a compact disc (CD) drive, a universal serial bus (USB) device, or other suitable removable and / or fixed storage unit, and may include them. The data described herein may be stored in the memory device 830, may be loaded from the memory device 830 into the memory 820, and the data may be processed by the controller 805 in the memory 820. The memory device 830 may include a cloud storage device. The memory device 830 may include storing data in a database.

[0108] The input device 835 may be, for example, a mouse, a keyboard, a touch screen or pad, or any suitable input device or combination of devices, and may include them. The output device 840 may include one or more displays, speakers, and / or any other suitable output device, or combination of output devices. Any applicable input / output (I / O) device may be connected to the computing device 100. For example, a wired or wireless network interface card (NIC), a modem, a printer, a universal serial bus (USB) device, or an external hard drive may be included in the input device 835 and / or the output device 840.

[0109] Embodiments of the present invention may include one or more articles (e.g., the memory 820 or the memory device 830) such as a memory, a disk drive, or a USB flash memory, etc., which encode, include, or store instructions, e.g., computer-executable instructions, that when executed by a processor or a controller, perform the methods disclosed herein, or a non-transitory readable medium of a computer or a processor, or a non-transitory storage medium of a computer or a processor.

[0110] A processor for controlling the functions of one or more elements described in this specification, for example, for controlling the rotation of one or more elements, can be coupled to a computer-readable data storage device containing instructions (such as code) that facilitate one or more calculations necessary to determine the required rotation. Any combination of one or more computer-readable media can be utilized. The computer-readable media can be a computer-readable signal medium or a computer-readable storage medium. The computer-readable storage medium can be, for example, but not limited to, an electronic, magnetic, optical, electromagnetic, infrared, or semiconductor system, apparatus, or device, or any suitable combination thereof. More specific examples (non-exhaustive list) of computer-readable storage media include electrical connections having one or more wires, portable computer diskettes, hard disks, random access memory (RAM), read-only memory (ROM), erasable programmable read-only memory (EPROM or flash memory), optical fibers, portable compact disk read-only memory (CD-ROM), optical storage devices, magnetic storage devices, or any suitable combination thereof. In the context of this specification, a computer-readable storage medium can be any tangible expression medium that can contain or store a program for use by or in connection with an instruction execution system, apparatus, or device.

[0111] The computer-readable signal medium can include, for example, a propagated data signal having computer-readable program code embodied therein, either baseband or as part of a carrier wave. Such a propagated signal can take any of a variety of forms, including, but not limited to, electromagnetic, optical, or any suitable combination thereof. The computer-readable signal medium is not a computer-readable storage medium but can be any computer-readable medium that can communicate, propagate, or transmit a program for use by or in connection with an instruction execution system, apparatus, or device.

[0112] Program code embodied on a computer-readable medium may be transmitted using any appropriate medium, including but not limited to wireless, wired, fiber optic cable, RF, or any suitable combination thereof. The computer program code for performing the operations of aspects of the present invention may be written in any combination of one or more programming languages, including but not limited to object-oriented programming languages such as Java (registered trademark), Smalltalk (registered trademark), C++, and conventional procedural programming languages such as the "C" programming language or similar programming languages. The program code may execute entirely on the user's computer, partly on the user's computer, as a stand-alone software package, partly on the user's computer and partly on a remote computer, or entirely on the remote computer or server. In the latter scenario, the remote computer may be connected to the user's computer via any type of network, including a local area network (LAN) or a wide area network (WAN), or the connection may be made to an external computer (e.g., via the Internet using an Internet service provider).

[0113] In the above description, embodiments are examples or implementations of the present invention. The various expressions "one embodiment", "an embodiment", or "some embodiments" do not necessarily all refer to the same embodiment.

[0114] The various features of the present invention may be described in the context of a single embodiment, but the features may also be provided separately or in any suitable combination. Conversely, the present invention may be described herein in the context of separate embodiments for clarity, but the present invention may also be implemented in a single embodiment.

[0115] References to "some embodiments", "an embodiment", "one embodiment", or "another embodiment" in this specification mean that a particular feature, structure, or characteristic described in connection with the embodiment is included in at least some embodiments of the invention, but not necessarily all embodiments.

[0116] It should be understood that the expressions and terms used in this specification should not be construed as limiting, but are for illustrative purposes only. The principles and uses of the teachings of the present invention can be better understood with reference to the accompanying description, drawings, and examples.

[0117] It should be understood that the details described in this specification do not interpret limitations on the application of the present invention. Furthermore, the present invention can be implemented or executed in various ways, and it should be understood that the present invention can be implemented in embodiments other than those generally described in the above description.

[0118] The terms "including", "comprising", "consisting of" and their grammatical variations do not exclude the addition of one or more components, features, steps, or integers or groups thereof, and it should be understood that these terms are to be construed as identifying components, features, steps or integers. When referring to "additional" elements in the specification or claims, it does not exclude the possibility that there are one or more additional elements. When referring to "a" or "an" element in the claims or specification, it should be understood that such an expression should not be construed as meaning that there is only one such element. When a component, feature, structure or property is described in the specification as "may", "might", "can" or "could" be included, it should be understood that it is not necessarily required that the particular component, feature, structure or property be included. Where applicable, state diagrams, flow diagrams or both may be used to illustrate embodiments, but the invention is not limited to those diagrams or corresponding descriptions. For example, the flow need not proceed through each box or state shown or in exactly the same order as shown and described. The method of the present invention is implemented by performing or completing selected steps or tasks manually, automatically, or a combination thereof.

[0119] The term "method" relates to a method, means, technique and procedure for achieving a given task, and the given task includes, but is not limited to, methods, means, techniques and procedures known to those skilled in the art to which the present invention pertains or readily developed therefrom. The descriptions, examples, methods and materials shown in the claims and specification are for illustrative purposes only and should not be construed as limiting. The meanings of technical and scientific terms used herein should be broadly understood by those skilled in the art unless otherwise specified.

[0120] The present invention can be tested or implemented by methods and materials equivalent or similar to those described herein. Publications including patents, patent applications, and papers referenced or mentioned herein are hereby incorporated by reference in their entirety to the same extent as if each individual publication were specifically and individually indicated to be incorporated herein. Further, the citation or identification of reference documents in the description of some embodiments of the present invention should not be construed as an admission that such references are available as prior art to the present invention.

[0121] The present invention has been described with respect to a limited number of embodiments, which should not be construed as limitations on the scope of the present invention, but rather as exemplifications of some preferred embodiments. Other possible variations, modifications, and applications are also within the scope of the present invention. Accordingly, the scope of the present invention should not be limited by what has been described so far, but rather by the appended claims and their legal equivalents.

Claims

1. A repeater for a wireless power beam, an array of coaxial waveguide elements, each element having an input polarization section, an output polarization section, and a phase shift section located between the input polarization section and the output polarization section and including, an array of coaxial waveguide elements, wherein the input polarization section, the output polarization section, and the phase shift section are rotatable controllably about the longitudinal axis of the coaxial waveguide, and a processor for controlling the rotation of the input polarization section, the output polarization section, and the phase shift section, A repeater comprising.

2. The repeater according to claim 1, wherein the input polarization section and the output polarization section each include two pairs of diametrically opposed polarization irises protruding into the waveguide.

3. The repeater is configured to relay a wireless power beam having a free space wavelength λ, the wireless power beam in the waveguide has a wavelength λg, and each pair of polarization irises in the input polarization section and the output polarization section are located at a longitudinal distance of λg / 8 from the other pair of polarization irises in their respective polarization sections. The repeater according to claim 2.

4. The repeater according to claim 1, wherein the phase shift section includes three pairs of diametrically opposed phase shift irises protruding into the waveguide.

5. The repeater is configured to relay a wireless power beam having a free space wavelength λ, the wireless power beam in the waveguide has a wavelength λg, and the central pair of phase shift irises in the phase shift section are located at a longitudinal distance of λg / 6 from each of the other pairs of phase shift irises in the phase shift section. The repeater according to claim 4.

6. The element for the coaxial waveguide includes an inner portion defined by an inner diameter and an outer portion defined by a portion between the inner diameter and the outer diameter, and the inner portion does not permit the propagation of an incident radio power beam having a free space wavelength λ, the repeater according to claim 1.

7. The inner portion is substantially hollow, the repeater according to claim 6.

8. The processor is located within the inner portion of the element for the coaxial waveguide, the repeater according to claim 6.

9. The repeater further includes an input pilot beam analyzer adjacent to the input polarization section and an output pilot beam analyzer adjacent to the output polarization section, and the input pilot beam analyzer and the output pilot beam analyzer can each measure the characteristics of the incident pilot beam and can transmit the measured characteristics to the processor, and the processor can control the rotation of the input polarization section, the output polarization section, and the phase shift section based on the measured characteristics, the repeater according to claim 1.

10. The array of elements for the coaxial waveguide is a hexagonal array, the repeater according to claim 1.

11. The array of elements for the coaxial waveguide is a linear array, the repeater according to claim 1.

12. The distance between two adjacent elements for the coaxial waveguide is 5.0 mm to 10.0 mm, the repeater according to claim 1.

13. The distance between two adjacent elements for the coaxial waveguide is 6.0 mm to 7.0 mm, the repeater according to claim 1.

14. The repeater is configured to relay a radio power beam having a free space wavelength λ, and the ratio of d / λ is less than 0.7, where d represents the distance between two adjacent elements for the coaxial waveguide, the repeater according to claim 1.

15. The repeater is configured to relay a wireless power beam having a free-space wavelength λ, and the ratio of d / λ is less than 0.6, where d represents the distance between two adjacent coaxial waveguide elements. The repeater according to claim 1.

16. The repeater according to claim 1, further including a reflecting surface at one end of each coaxial waveguide element.

17. A low Earth orbit satellite including the repeater according to claim 1.

18. A satellite group including a plurality of low Earth orbit satellites according to claim 17.

19. A satellite including the repeater according to claim 1, wherein the satellite is one of a geostationary orbit (GEO) satellite, a medium Earth orbit (MEO) satellite, a polar orbit satellite, or a sun-synchronous orbit (SSO) satellite.

20. The phase shift unit includes three pairs of phase shift irises protruding from the waveguide and facing opposite directions. The repeater according to any one of claims 1 to 3.

21. The coaxial waveguide element includes an inner portion defined by an inner diameter and an outer portion defined by a portion between the inner diameter and an outer diameter. The inner portion does not permit the propagation of an incident wireless power beam having a free-space wavelength λ. The repeater according to any one of claims 1 to 5.

22. The processor is located within the inner portion of the coaxial waveguide element. The repeater according to any one of claims 6 to 7.

23. The repeater further includes an input pilot beam analyzer adjacent to the input polarization unit and an output pilot beam analyzer adjacent to the output polarization unit. The input pilot beam analyzer and the output pilot beam analyzer can each measure the characteristics of the incident pilot beam and transmit the measured characteristics to the processor. The processor can control the rotation of the input polarization unit, the output polarization unit, and the phase shift unit based on the measured characteristics. The repeater according to any one of claims 1 to 8.

24. The array of coaxial waveguide elements is a hexagonal array. The repeater according to any one of claims 1 to 9.

25. The array of coaxial waveguide elements is a linear array. The repeater according to any one of claims 1 to 9.

26. The distance between two adjacent coaxial waveguide elements is 5.0 mm to 10.0 mm. The repeater according to any one of claims 1 to 11.

27. The distance between two adjacent coaxial waveguide elements is 6.0 mm to 7.0 mm. The repeater according to any one of claims 1 to 11.

28. The repeater is configured to relay a radio power beam having a free space wavelength λ, and the ratio of d / λ is less than 0.7, where d represents the distance between two adjacent coaxial waveguide elements. The repeater according to any one of claims 1 to 13.

29. The repeater is configured to relay a radio power beam having a free space wavelength λ, and the ratio of d / λ is less than 0.6, where d represents the distance between two adjacent coaxial waveguide elements. The repeater according to any one of claims 1 to 13.

30. Each end of each coaxial waveguide element further includes a reflecting surface. The repeater according to any one of claims 1 to 15.

31. A low Earth orbit satellite comprising the repeater according to any one of claims 2 to 16 or claims 20 to 30.

32. A satellite group comprising a plurality of the low Earth orbit satellites according to claim 31.

33. A satellite comprising the repeater according to any one of claims 2 to 16 or claims 20 to 30, wherein the satellite is one of a geostationary orbit (GEO) satellite, a medium Earth orbit (MEO) satellite, a polar orbit satellite, or a sun-synchronous orbit (SSO) satellite.

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