Dual-polarization radiating element for antenna, antenna and antenna system

Abstract

The present disclosure relates to a dual-polarization radiation unit for an antenna, an antenna, and an antenna system. The dual-polarization radiation unit for an antenna according to the present disclosure includes: four dipoles, wherein the radiation arms of the four dipoles are planar structures and are symmetrical about two mutually perpendicular lines, wherein the two mutually perpendicular lines divide the radiation unit into four regions, and the central parts of the four regions are DC-conductive, and wherein each of the four regions has a hollow region.

Description

Technical Field

[0001] The present disclosure relates to the field of radio frequency communication technology, and in particular, to a dual-polarization radiation unit for an antenna, an antenna including the dual-polarization radiation unit for an antenna, and an antenna system including the antenna. Background Art

[0002] In the broad spectrum between 400MHz and 6GHz, the so-called sub-6GHz band, these spectrum ranges are allocated for telecommunications for communication. However, it is technically impossible to design analog components such as filters, phase shifters, radiating elements, and amplifiers for such a wide bandwidth. Therefore, the sub-6GHz band is further divided into multiple sub-bands and operated separately to enable the design of analog components. For example, the industry usually divides the sub-6GHz band into the following four separate operating sub-bands: 600MHz to 1GHz, 1.4GHz to 3GHz, 3GHz to 4.2GHz, and 5GHz-6GHz. Base station antennas for LTE, 5G or 3G communications consist of arrays of multiple radiating elements operating in different frequency bands.

[0003] These separated frequency bands require separate components such as filters, phase shifters, amplifiers, and radiating elements. All of these components must not interfere with each other, and the minimum isolation needs to be around 20dB, and the isolation between each signal channel is preferably 30dB. This goal is relatively easy to achieve for shielded channels such as filters and phase shifters, in which all signals are shielded by microstrip lines or strip lines. However, since the radiating elements radiate into the air and are very easy to couple, it is relatively difficult to isolate the radiating elements. If the isolation cannot reach this level, there will be serious mode distortion and port-to-port isolation problems. These problems will degrade network performance. If the radiating elements can be separated by more than two wavelengths at the lowest frequency, the isolation can be enhanced, but such a separation distance will reduce the integration of the antenna system and increase the size of the antenna system.

[0004] On the other hand, the space for mounting antennas on base station towers is very limited due to the need to cover multiple frequency bands, operators and sectors. Over the past five to seven years, the industry is moving towards combining multiple sub-band systems into the same radome or product, making isolation a challenge. Summary of the invention

[0005] As mentioned above, the following technical problems exist in the prior art, namely, interference will be generated between the existing radiation units of different frequency bands, and due to the existence of interference problems between the low-frequency radiation units and the high-frequency radiation units, there is a fixed positional relationship between the low-frequency radiation units and the high-frequency radiation units, and they cannot be decoupled from each other, thereby limiting the design of multi-band radiation units.

[0006] In order to solve the above technical problems, the inventors of the present disclosure proposed the following dual-polarization radiation unit for an antenna based on the above considerations, wherein the dual-polarization radiation unit comprises: four dipoles, wherein the radiation arms of the four dipoles are planar structures and are symmetrical about two mutually perpendicular line axes, wherein the two mutually perpendicular lines divide the radiation unit into four areas, and the central parts of the four areas are DC-conductive, and wherein each of the four areas has a hollow area.

[0007] The dual-polarization radiation unit proposed in accordance with the present disclosure has a hollow area, so that the interference with the electromagnetic wave signal generated by the radiation unit used in other frequency bands can be reduced, so that the dual-polarization radiation unit proposed in accordance with the present disclosure is more friendly to system integration, and the radiation performance of the integrated multi-band radiation unit will also be better than the radiation performance of the radiation unit in the prior art. In addition, since the central part of the dual-polarization radiation unit proposed in accordance with the present disclosure is DC-conductive, its manufacturing process is simpler and more convenient, and since the dual-polarization radiation unit according to the present disclosure can be constructed in an integrated manner, its product consistency is better, and its radiation performance can also be better ensured.

[0008] In one embodiment according to the present disclosure, the first side of the dual-polarization radiation unit is perpendicular to the corresponding line of the two mutually perpendicular lines, wherein the first side is the side intersecting the corresponding line. In a traditional dual-polarization radiation unit, the two mutually perpendicular lines are usually diagonal lines, that is, the edge of the dual-polarization radiation unit to which the diagonal line extends is usually a corner of the dual-polarization radiation unit, not an edge. In the dual-polarization radiation unit proposed in the present disclosure, the edge of the dual-polarization radiation unit to which the two mutually perpendicular lines extend is an edge of the dual-polarization radiation unit, and the edge is perpendicular to the corresponding line of the two mutually perpendicular lines. Figuratively speaking, compared with the traditional dual-polarization radiation unit, the dual-polarization radiation unit according to the present disclosure adopts a corner cutting processing method, so that the dual-polarization radiation unit proposed in the present disclosure has a smaller area than the traditional dual-polarization radiation unit, thereby saving more materials and reducing manufacturing costs.

[0009] Preferably, in an embodiment according to the present disclosure, the dual-polarization radiation unit has an octagonal shape. Compared with the conventional dual-polarization radiation unit having, for example, a quadrilateral shape, the dual-polarization radiation unit according to the present disclosure adopts a corner-cutting processing method, so that the dual-polarization radiation unit proposed according to the present disclosure has, for example, an octagonal shape. Compared with the conventional dual-polarization radiation unit, the area is smaller, thereby saving more materials and reducing the manufacturing cost.

[0010] In one embodiment according to the present disclosure, the dual-polarized radiation unit further includes: four slots, and the four slots are respectively located at the junction of two adjacent areas among the four areas. Two of the four slots point to one polarization direction, such as a polarization direction of +45°, and the other two of the four slots point to another polarization direction, such as a polarization direction of -45°. Although the size of the slot, such as the length of the slot, is reduced by the aforementioned cutting angle treatment, the resonant frequency of the current loop can be moved higher until the resonance exceeds the working range of the antenna, thereby reducing the influence of other frequency bands on the dual-polarized radiation unit proposed according to the present disclosure.

[0011] In one embodiment according to the present disclosure, the dual-polarization radiation unit further includes: four feed lines, the four feed lines are associated with the four slots, and each of the four feed lines extends from a middle area of ​​the dual-polarization radiation unit to a feeding point of the slot associated therewith, wherein the length of the feed line is associated with the matching impedance.

[0012] Preferably, in one embodiment according to the present disclosure, the dual-polarized radiation unit further includes: a common-mode choke circuit, which is configured to be arranged near the feeding point and associated with one of the four slots. Further preferably, in one embodiment according to the present disclosure, the common-mode choke circuit further includes a first track and a second track, wherein the first track and the second track are configured in parallel on both sides of the radiation arm in the form of inductor coils, and wherein the electrical lengths of the first track and the second track are equal, and the winding directions of the coils of the first track and the second track are consistent.

[0013] Optionally or additionally, in one embodiment according to the present disclosure, the dual-polarization radiation unit further comprises: a parallel filter, wherein the parallel filter is constructed as a metal wire extending inwardly from the edge of the hollow area. Preferably, in one embodiment according to the present disclosure, the parallel filter is constructed as an open line.

[0014] In an embodiment according to the present disclosure, the dual-polarized radiation unit further includes: an inductor element, wherein the inductor element extends from an edge of the hollow area away from the central area of ​​the dual-polarized radiation unit toward the central area.

[0015] In addition, a second aspect of the present disclosure provides an antenna, comprising: at least one dual-polarization radiation unit according to the first aspect of the present disclosure; and a radiation unit matching circuit.

[0016] Furthermore, the third aspect of the present disclosure proposes an antenna system, which includes: the antenna proposed according to the second aspect of the present disclosure; and at least one second antenna, wherein the operating frequency band of the at least one second antenna is higher than the operating frequency band of the antenna.

[0017] In one embodiment of the present disclosure, the antenna and the second antenna are arranged alternately. Optionally, in one embodiment of the present disclosure, the number of columns of the antenna is equal to the number of columns of the second antenna, or the number of columns of the second antenna is twice the number of columns of the antenna.

[0018] In summary, the dual-polarization radiation unit proposed in accordance with the present disclosure has a hollow area, so that the interference with the electromagnetic wave signal generated by the radiation unit used in other frequency bands can be reduced, so that the dual-polarization radiation unit proposed in accordance with the present disclosure is more friendly to system integration, and the radiation performance of the integrated multi-band radiation unit will also be better than the radiation performance of the radiation unit in the prior art. In addition, since the central part of the dual-polarization radiation unit proposed in accordance with the present disclosure is DC-conductive, its manufacturing process is simpler and more convenient, and since the dual-polarization radiation unit according to the present disclosure can be constructed in an integrated manner, its product consistency is better, and its radiation performance can also be better ensured. BRIEF DESCRIPTION OF THE DRAWINGS

[0019] The features, advantages and other aspects of the embodiments of the present disclosure will become more apparent with reference to the following detailed description in conjunction with the accompanying drawings, in which several embodiments of the present disclosure are shown in an exemplary and non-limiting manner. In the accompanying drawings:

[0020] Figure 1A A perspective view of an antenna system 100 including a dual-polarization radiation unit 110 and a high-frequency radiation unit 120 according to an embodiment of the prior art is shown;

[0021] Figure 1B A side view of an antenna system 100 including a dual-polarization radiation unit 110 and a high-frequency radiation unit 120 according to an embodiment of the prior art is shown;

[0022] Figure 2A A schematic diagram of a dual-polarization radiation unit 210 for an antenna according to an embodiment of the present disclosure is shown;

[0023] Figure 2B A partially enlarged schematic diagram of a common mode choke circuit of a dual-polarized radiation unit 210 for an antenna according to an embodiment of the present disclosure is shown;

[0024] Figure 2C shows a side view of a dual polarized radiating element 210 for an antenna according to one embodiment of the present disclosure;

[0025] Figure 2D A side perspective view of a dual polarized radiating element 210 for an antenna according to one embodiment of the present disclosure is shown;

[0026] Figure 2E A bottom perspective view of a dual polarized radiating element 210 for an antenna according to one embodiment of the present disclosure is shown;

[0027] Figure 2F An exploded view of a dual-polarized radiating element 210 for an antenna according to one embodiment of the present disclosure is shown;

[0028] Figure 3 A schematic diagram of an antenna system 300 according to an embodiment of the present disclosure is shown;

[0029] Figure 4A A schematic diagram showing an antenna system 400A according to another embodiment of the present disclosure; and

[0030] Figure 4B A schematic diagram of an antenna system 400B according to another embodiment of the present disclosure is shown. DETAILED DESCRIPTION

[0031] The various exemplary embodiments of the present disclosure are described in detail below with reference to the accompanying drawings. Although the exemplary methods and devices described below include software and / or firmware executed on hardware among other components, it should be noted that these examples are merely illustrative and should not be considered restrictive. For example, it is considered that any or all hardware, software, and firmware components can be implemented exclusively in hardware, exclusively in software, or in any combination of hardware and software. Therefore, although exemplary methods and devices have been described below, it should be readily understood by those skilled in the art that the examples provided are not intended to limit the manner in which these methods and devices are implemented.

[0032] In addition, the flowcharts and block diagrams in the accompanying drawings illustrate the possible architectures, functions and operations of the methods and systems according to various embodiments of the present disclosure. It should be noted that the functions marked in the boxes may also occur in an order different from that marked in the accompanying drawings. For example, two boxes represented in succession may actually be executed substantially in parallel, or they may sometimes be executed in the opposite order, depending on the functions involved. It should also be noted that each box in the flowchart and / or block diagram, and the combination of boxes in the flowchart and / or block diagram, may be implemented using a dedicated hardware-based system that performs a specified function or operation, or may be implemented using a combination of dedicated hardware and computer instructions.

[0033] As mentioned above, the prior art has the following technical problem, that is, interference will be formed between existing radiation units in different frequency bands. The purpose of the present invention is to provide a dual-polarized low-band radiation unit or element operating below 1 GHz, which can well isolate the interference of other high-frequency bands (sub-bands 2, 3, and 4 as described above) even if two or three different elements overlap to a large extent (height in different dimensions), so that the high-frequency radiation pattern remains unchanged, just like there is no low-frequency unit on the top. In addition, the impact on the performance of the low-frequency band unit itself (such as radiation pattern and return loss) is minimized.

[0034] WO2015 / 124573A discloses a similar form of radiation unit. Figure 1A 1 shows a perspective view of an antenna system 100 including a dual-polarization radiation unit 110 and a high-frequency radiation unit 120 according to an embodiment of the prior art. Figure 1B A side view of an antenna system 100 including a dual-polarized radiating element 110 and a high-frequency radiating element 120 according to an embodiment of the prior art is shown. As can be seen from the two figures of FIG1 , the antenna system 100 disclosed in WO2015 / 124573A outlines a low-band radiating element 110 constructed using a four-slot feeding method. It further outlines a method of obtaining a multi-band antenna system 100 by placing a high-band radiating element 120 on top of the low-band element 110 and using an additional metal sheet 130 as a reflector for the high-band element 120. In this way, the high-band array 120 will be in line with the low-band array 110, with half of the high-frequency elements 120 on top of the low-frequency elements 110 and the other half of the high-frequency elements 120 between the low-frequency elements 110. In the design of the radiating elements 110 and 120 of the antenna system 100, the designer did not try to make the high-band radiating element 120 invisible to the low-band radiating element 110, but arranged the high-band radiating element 120 in such a way that the low-band radiating element 110 would not obscure the high-band radiating element 120. However, this method has some disadvantages:

[0035] First, the vertical element spacing of the radiating elements 120 of the high-band array is limited to half the spacing of the radiating elements 110 of the low-band array. The spacing of the radiating elements 110 of the low-band array is typically about 0.7λ, which can achieve reasonable grating lobe levels at larger down-tilt angles, where a grating lobe is a side lobe that increases as the angle of the scanning beam increases, and is proportional to the ratio of the spacing between radiating elements to the wavelength of the radiating elements of the array. Larger spacing between radiating elements results in higher grating lobes. Grating lobes reduce the gain of the radiating elements of the array and cannot be reduced by adjusting the amplitude or phase taper of the radiating elements of the array.

[0036] Secondly, because the spectrum of high frequency is wider, it is more sensitive to the influence of grating lobes at higher frequencies in the band. The actual spacing between radiating elements used in industry is 0.78λ to 0.85λ. If the spacing between radiating elements in the high frequency band is half of the spacing between radiating elements in the low frequency band, it is greater than 0.9λ in the high frequency, resulting in significant grating lobes. The grating lobes of the radiating elements of a 0.78λ array tilted downward by 10 degrees are about 13.5dB, while the grating lobes of the radiating elements of a 0.91λ array tilted downward by 10 degrees are about 7.5dB.

[0037] In view of the above problems, the inventors of the present disclosure have innovatively thought of a method to improve the grating lobes of the radiating elements of the high frequency band, that is, to allow the spacing between the radiating elements of the high frequency band array to be liberalized (usually less than 0.7 wavelengths). This can only be achieved by placing the radiating elements of the high frequency band array side by side with the radiating elements of the low frequency band array. However, since the radiating elements of the conventional low frequency band elements are not hidden at the high frequency band frequencies, if the radiating elements of the high frequency band array are very close to the radiating elements of the low frequency band array, the pattern of the high frequency band will be severely distorted.

[0038] To obtain good high frequency vertical and horizontal pattern performance with conventional low frequency band array radiators, the high frequency band array radiators must be placed side by side with the low frequency band array radiators and at a greater distance from the low frequency band array radiators. This limits the possibility of having multiple high frequency band array radiators and low frequency band array radiators in a narrow width antenna.

[0039] In the design according to the present disclosure, the radiating elements of the low-band array are not visible to the high-band frequencies, which provides flexibility for interleaving the radiating elements of the high-band array with the radiating elements of the low-band array. In addition, there is no restriction on the spacing between the radiating elements of the high-band array, which provides freedom to obtain the best grating lobe and gain performance.

[0040] The following combination Figure 2A and Figure 2BTo introduce the dual-polarization radiation unit 210 proposed according to the present disclosure, wherein: Figure 2A FIG. 2 shows a schematic diagram of a dual-polarization radiation unit 210 for an antenna according to an embodiment of the present disclosure. Figure 2B FIG. 2 shows a partially enlarged schematic diagram of a common mode choke circuit of a dual-polarized radiation unit 210 for an antenna according to an embodiment of the present disclosure. Figure 2C FIG. 2 shows a side view of a dual-polarization radiating element 210 for an antenna according to an embodiment of the present disclosure. Figure 2A It can be seen that the dual-polarization radiation unit 210 for the antenna proposed in the present disclosure includes four dipoles, namely Figure 2A A diagonal line in the figure forms a pair of dipoles, for example, two dipoles along one end of the diagonal line 211 form a dipole, and two dipoles at both ends of the diagonal line 211 form a pair of dipoles, and two dipoles along one end of the diagonal line 213 form a dipole, and two dipoles at both ends of the diagonal line 213 form a pair of dipoles. In other words, four dipoles together form two pairs of dipoles along the two diagonals 211 and 213, wherein the radiation arms of the four dipoles (i.e., the most extended gray area in the figure) are planar structures and are axially symmetrical about two mutually perpendicular lines 211 and 213, wherein the two mutually perpendicular lines 211 and 213 divide the dual-polarization radiation unit 210 into four regions, and the central parts of the four regions are DC-conductive, that is, the four regions are DC-conductive in the intersection area of ​​the two diagonals 211 and 213, rather than being hollow and unconnected, and wherein each of the four regions has a hollow area. That is, the middle of each area divided by the two diagonal lines 211 and 213 of the dual-polarization radiation unit 210 has a hollow area which is blank in the figure. Since the dual-polarization radiation unit 210 is provided with the hollow area, the high-frequency signal is allowed to pass through, so that the dual-polarization radiation unit 210 has less shielding on the high-frequency oscillator, thereby minimizing diffraction. In other words, the dual-polarization (e.g., +45°, -45°) radiation unit 210 operating in the low frequency band (sub-band 1) is designed to be invisible to the high-frequency radiation unit operating in the high frequency band (sub-band 2, 3, 4). The dual-polarization radiation unit 210 has inherent good radiation performance under the return loss bandwidth on sub-band 1. In addition, the dual-polarization radiation unit 210 can be implemented by PCB, for example, but can also be formed by metal plate or die-cast plate, because the main body of the dual-polarization radiation unit 210 in the low frequency band is DC conductive, which means that the dual-polarization radiation unit 210 in the low frequency band can be integrated by metal casting or sheet metal processing.

[0041] Here, the dielectric plate is omitted in Figure 2, that is, the microstrip transmission line 214 and the microstrip transmission line 216 are shown on one plane, and the plane 223 where the dipole is located represented by the gray area is on another plane. The two planes can be parallel to each other, and the dielectric plate can be located between the two parallel planes, for example.

[0042] Since the central part of the dual-polarized radiation unit 210 proposed in the present disclosure is DC-conductive, its manufacturing process is simpler and more convenient. Moreover, since the dual-polarized radiation unit 210 proposed in the present disclosure can be constructed in an integrated manner, its product consistency is better, and its radiation performance can also be better ensured. In addition, the dual-polarized radiation unit 210 proposed in the present disclosure has a hollow area, so that its interference with the electromagnetic wave signal generated by the radiation unit for other frequency bands is reduced, so that the dual-polarized radiation unit 210 proposed in the present disclosure is more friendly to system integration, and the radiation performance of the integrated multi-band radiation unit will also be better than that of the radiation unit in the prior art. Compared with the traditional design, the size of the slot 212 is reduced by about 1 / 4 of the high-frequency wavelength, for example, by cutting the edge angle. When the high-frequency band radiation unit is blocked by the low-frequency band radiation unit (such as the dual-polarized radiation unit 210 here), a current loop of the high-frequency band frequency is established at the slot 212 and the edge of the slot 212. By reducing the size of slot 212, such as a slot, the resonant frequency of the current loop can be moved higher until the resonance is outside the operating range of the antenna. Despite the reduction in slot size, other features of the geometry are adjusted to maintain impedance bandwidth (return loss better than 12 dB) at low band frequencies.

[0043] from Figure 2AIt can be seen that: the first side (e.g., 211a or 211b) of the dual-polarized radiation unit 210 is perpendicular to the corresponding line (e.g., diagonal line 211) of the two mutually perpendicular lines; and the other side (e.g., 213a or 213b) of the dual-polarized radiation unit 210 is perpendicular to the other corresponding line (e.g., diagonal line 213) of the two mutually perpendicular lines, wherein the first side (e.g., 211a or 211b) is the side intersecting the corresponding line (e.g., diagonal line 211). In a conventional dual-polarized radiation unit 110, the two mutually perpendicular lines are usually diagonal lines, that is, the edge of the dual-polarized radiation unit 110 to which the diagonal line extends is usually a corner of the dual-polarized radiation unit 110, not an edge. The edge of the dual-polarization radiation unit 210 to which the two mutually perpendicular lines 211 and 213 of the dual-polarization radiation unit 210 proposed in the present disclosure extend is an edge of the dual-polarization radiation unit 210, and the edge is perpendicular to the corresponding line of the two mutually perpendicular lines 211 and 213. Figuratively speaking, compared with the traditional dual-polarization radiation unit 110, the dual-polarization radiation unit 210 according to the present disclosure adopts a corner cutting processing method, so that the dual-polarization radiation unit 210 proposed in the present disclosure is smaller in area than the traditional dual-polarization radiation unit 110, thereby saving more materials and reducing manufacturing costs. Preferably, as Figure 2A As shown, the dual-polarization radiation unit 210 has an octagonal shape.

[0044] Specifically, the structure of the radiation unit 210 is composed of a conductive plate with four slots 212 on diagonal lines 211 and 213. Each slot 212 is in the form of a slot, wherein the two slots on the diagonal line 213 point to the +45° vector, and the two slots on the diagonal line 211 point to the -45° vector, and the two polarizations together constitute the expected polarization direction of the dual-polarization radiation unit 210. Figure 2A As shown, each slot uses a microstrip transmission line 214 and a corresponding microstrip transmission line 216 to feed the other slot to form the polarization of the antenna. Figure 2A In the embodiment shown, the feed point connected to the microstrip transmission line 214 will produce +45° polarized radiation when viewed from the top, while the feed point connected to the microstrip transmission line 216 will produce -45° polarized radiation. The position of the feed point along the slot 212 determines the impedance of the feed point, and the impedance of the circuit can be matched to 50 ohms using impedance transformation lines and power dividers. The two slots of each polarization are fed with equal amplitude and phase. The support structure is as shown in FIG. Figure 2CAs shown. The current design is made of two mutually crossed PCBs 215 and 222, each of which is fed with polarization through a power divider. The output of the power divider is connected to the microstrip line on the radiating element 210. The feeding structure includes an equal power divider and a section of impedance transformation line, which can be matched to 50 ohms, for example, or to 75 ohms in other embodiments or to other values ​​as required by the specific application. These are implemented through microstrip circuits, in which the back of the feeding structure also acts as a balanced-unbalanced converter for the radiating element. The feeding structure and the radiating element do not have to use PCBs, and alternative versions can also be implemented using metal plates or die-cast metals.

[0045] In summary, the dual-polarization radiation unit 210 includes four slots 212, and the four slots 212 are respectively located at the junction of two adjacent areas of the four areas. Two slots of the four slots 212 (two slots on the same diagonal line) point to one polarization direction, for example, a polarization direction of +45°, and the other two slots of the four slots (two slots on another diagonal line) point to another polarization direction, for example, a polarization direction of -45°. Although the size of the slot, such as the length of the slot, is reduced by the aforementioned cutting angle treatment, the resonant frequency of the current loop can be moved higher until the resonance exceeds the working range of the antenna, thereby reducing the influence of other frequency bands on the dual-polarization radiation unit proposed according to the present disclosure. Preferably, the dual-polarization radiation unit 210 includes four feed lines 214 and 216, the four feed lines 214 and 216 are associated with the four slots 212, and each of the four feed lines 214 and 216 extends from a middle area of ​​the dual-polarization radiation unit 210 (for example, an area where two diagonal lines 211 and 213 intersect) to a feeding point of the slot 212 associated therewith, wherein the length of the feed lines 214 and 216 is associated with the matching impedance.

[0046] In addition, from Figure 2AIt can also be seen that the dual-polarization radiating unit 210 also includes a common-mode choke circuit 218, which is configured to be arranged near the feeding point and associated with one of the four slots. Optionally or additionally, the dual-polarization radiating unit 210 also includes a parallel filter 219, which is configured as a metal wire extending inward from the edge of the hollow area. Preferably, these parallel filters 219 are configured as a symmetrical structure. A parallel filter 219 is added to the hollow area of ​​the interior. The parallel filter 219 is connected to the body of the dual-polarization radiating unit 210, and an impedance disturbance is generated at the connection position. The frequency at which the impedance disturbance occurs is controlled by the electrical length of the parallel filter 219. The electrical length is usually greater than λ / 6 and less than or equal to λ / 4. The parallel filter 219 acts as a band-stop filter. The position of the parallel filter 219 is optimized to suppress the local high-frequency band current flowing around the hollow hollow area of ​​the hollow. Since the lines of the parallel filter 219 are added to a continuous conductive track, the parallel filter 219 acts as a parallel circuit. Further preferably, the parallel filter 219 is constructed as an open line.

[0047] In addition, optionally, the dual-polarization radiation unit 210 further includes an inductor element 217, which extends from an edge (e.g., an outer edge) of the hollow region away from the central region of the dual-polarization radiation unit 210 toward the central region. A high impedance portion is created at the outer edge. Due to the reduced size of the slots 212 on the diagonal, the resonant frequency of the low-frequency radiation unit (e.g., the dual-polarization radiation unit 210) oscillates to a frequency higher than the frequency of the designed low-frequency band working center. In order to rebalance the resonant frequency of the low-frequency band, the reactance portion 217 is added. Although the diagonal size is smaller than the ideal size, this feature increases the electrical length of the radiation unit.

[0048] Although only one open-circuit parallel filter 219 and one inductor element 217 are marked here, those skilled in the art should understand that each hollow area may have one open-circuit parallel filter 219 and one inductor element 217 .

[0049] Furthermore, Figure 2B FIG. 2 shows a partially enlarged schematic diagram of a common mode choke circuit 218 of a dual-polarized radiation unit 210 for an antenna according to an embodiment of the present disclosure. Figure 2BIt can be seen that: preferably, the common mode choke circuit 218 further includes a first track 2181 and a second track 2182, wherein the first track 2181 and the second track 2182 are connected to the radiation arm in parallel in the form of inductor coils and the winding directions of the first track 2181 and the second track 2182 are consistent. Since they are constructed on both sides of the radiation arm, there are multiple vias on the radiation arm, that is, Figure 2B The via 2183 shown in FIG. 1 is a via hole 2183, and the electrical lengths of the first track 2181 and the second track 2182 are equal. The common mode choke circuit 218 such as a common mode choke is implemented on the balun, such as Figure 2B As shown. The high-band frequencies in the range of 1.4 GHz to 2.7 GHz set the common mode at the low-band balun. The low-band currents in this region are differential, so a common mode choke circuit 218 is used to suppress the high-band currents without adversely affecting the low-band impedance. Figure 2B A close-up of the structure is shown. Two conductive tracks 2181 and 2182 loop parallel to each other on two layers of the PCB. The two tracks act as coupled inductors. When a common-mode current passes through the structure, the magnetic flux produced by each branch is added, resulting in a large inductance. The differential current produces magnetic fluxes that cancel each other out, so the inductance seen by the differential mode is very small. Therefore, the high-frequency band current is effectively choked, while the low-frequency band current passing through is relatively unaffected. The upper and lower layers of the common-mode filter circuit 218 should be wound as closely as possible to increase the common-mode choking effect and the differential conduction mechanism. The length of the common-mode choke circuit 218 is at least 1 / 8 wavelength of the high frequency. The choking effect is more obvious when the length is longer.

[0050] In order to more vividly illustrate the dual-polarization radiation unit 210 according to the present disclosure. Figure 2D 1 shows a side perspective view of a dual-polarization radiating element 210 for an antenna according to an embodiment of the present disclosure. Figure 2E 2 shows a bottom perspective view of a dual-polarization radiating element 210 for an antenna according to an embodiment of the present disclosure, and Figure 2F An exploded view of a dual polarized radiating element 210 for an antenna according to one embodiment of the present disclosure is shown.

[0051] from Figure 2D It can be seen that the microstrip transmission line 214 and the microstrip transmission line 216 and the common mode choke circuit 218 can be located on one side of the dielectric board 221, and the dielectric board 221 can be supported by two PCB circuit boards 215 and 222. Figure 2E It can be seen that the plane 223 where the dipole is located can be located, for example, on the other side of the dielectric plate 221. Figure 2FIt can be seen that the common mode choke circuit 218 includes a first track 2181 and a second track 2182 located on two different planes, wherein the first track 2181 can be located in the plane 223 where the dipole is located, and the second track 2182 can be located in the plane where the microstrip transmission line 214 and the microstrip transmission line 216 are located, and the two tracks 2181 and 2182 are connected by a via passing through the dielectric plate 221. The two tracks 2181 and 2182 can be connected to the radiation arm in the form of an inductor coil, and the winding directions of the first track 2181 and the second track 2182 are consistent, and the electrical lengths of the first track 2181 and the second track 2182 are equal.

[0052] In addition, a second aspect of the present disclosure provides an antenna, wherein the antenna comprises at least one Figure 2A , Figure 2B or Figure 2C The dual-polarized radiation unit 210 and the radiation unit matching circuit are shown. Since the dual-polarized radiation unit 210 proposed according to the present disclosure does not have to be overlapped with the radiation units of other frequency bands, the height d of the multi-band antenna system formed by the dual-polarized radiation unit according to the present disclosure can be significantly smaller than the height of the multi-band antenna system constructed according to the prior art.

[0053] Furthermore, the third aspect of the present disclosure provides an antenna system, the antenna system comprising: the antenna provided according to the second aspect of the present disclosure; and at least one second antenna, wherein the operating frequency band of the at least one second antenna is higher than the operating frequency band of the antenna. Preferably, the antenna and the second antenna are arranged alternately. Figure 3 The antenna system proposed according to the present disclosure is described. Figure 3 FIG. 3 is a schematic diagram of an antenna system 300 according to an embodiment of the present disclosure. Figure 3 It can be seen that the antenna system 300 proposed according to the present disclosure includes at least antennas for radiating radio frequency signals of two different frequency bands, wherein, for example, the first antenna 310 is configured to radiate signals of frequency band 1, that is, the first antenna 310 is configured as a low-frequency antenna; correspondingly, for example, the second antenna 320 is configured to radiate signals of frequency band 2, frequency band 3 or frequency band 4, that is, the second antenna 320 is configured as a high-frequency antenna. Here, the first antenna 310 and the second antenna 320 are arranged in an alternating manner, that is, for example, a column of low-frequency antennas 310 is arranged first, then two columns of high-frequency antennas 320 are arranged, and then another column of low-frequency antennas 310 is arranged, and so on. Preferably, the first antenna 310 at least partially covers the second antenna 320 to reduce the distance between two adjacent columns of high-frequency antennas 320.

[0054] Optionally, in an embodiment according to the present disclosure, the number of columns of the antenna is equal to the number of columns of the second antenna, or the number of columns of the second antenna is twice the number of columns of the antenna. Figure 4A and Figure 4B The invention will be described as follows: a multi-band antenna system is constructed by means of the dual-polarization radiation unit 210 according to the present disclosure. Figure 4A 4 is a schematic diagram showing an antenna system 400A according to another embodiment of the present disclosure. Figure 4B A schematic diagram of an antenna system 400B according to another embodiment of the present disclosure is shown.

[0055] from Figure 4A It can be seen that the antenna system 400a according to the present disclosure includes two columns of low-frequency antennas 410a and two columns of high-frequency antennas 420a, that is, the number of columns of the low-frequency antennas 410a is equal to the number of columns of the high-frequency antennas 420a; Figure 4B It can be seen that the antenna system 400b according to the present disclosure includes two columns of low-frequency antennas 410b and four columns of high-frequency antennas 420b, that is, the number of columns of the low-frequency antennas 410a and the number of columns of the high-frequency antennas 420a are not equal, and the number of columns of the high-frequency antennas 420b is twice the number of columns of the low-frequency antennas 420a. Preferably, the low-frequency antennas 410b at least partially cover the two columns of high-frequency antennas 420b to reduce the distance between two adjacent columns of high-frequency antennas 420b.

[0056] In compact multi-band antennas, the radiating elements of the low-band array and the radiating elements of the high-band array are placed very close together, causing the radiating elements of the low-band array to partially block the radiating elements of the high-band array. Therefore, if the radiating elements of the low-band array are not designed to be transparent to the high-band, the radiation pattern of the high-band will be distorted. The distortion is the result of two mechanisms: diffraction and resonance. Diffraction occurs when electromagnetic waves interact with obstacles, causing the electromagnetic waves to bend around the object. In this case, if the radiating element of the low-band array is a continuous piece of metal, it will cause a high degree of diffraction. Diffraction occurring in the near field of the radiating element can cause significant distortion of the far-field pattern.

[0057] When the high-band radiation excites the radiating elements of the low-band array, the radiating elements of the low-band array will resonate locally in the high-band. The currents are sensitive to the geometry of the local structure in terms of electrical length and impedance. These currents themselves can cause unwanted radiation, which can cause distortion of the high-band far-field pattern.

[0058] The radiating elements of the low-band array according to the present invention adopt various means to solve the above distortion mechanisms. In order to minimize diffraction, the radiating elements of the low-band array have a hollow portion in the structure to allow high-band energy to pass through (the maximum size of the hollow portion should be greater than 1 / 2 wavelength). Compared with traditional radiating elements, the low-band radiating elements according to the present disclosure, such as the dipole radiating elements according to the present disclosure, are cut at four corners, so that the low-band radiating elements have less shielding on the high-band array.

[0059] To solve the resonance problem, several methods are used. High impedance points are introduced at certain locations of the low-frequency radiating element geometry to suppress high-frequency resonance. The high impedance is frequency selective and is adjusted to suppress high-frequency current without adversely affecting low-frequency current. Common mode chokes are used to suppress high-frequency common mode resonance at certain locations of low-frequency radiating elements. The first is a common mode filter used on a low-frequency vibrator. The filter is formed by two tightly wound inductors in the same direction, creating high reactance at high frequencies, and the resistance of the high reactance is used to reduce the high-frequency resonance generated on the low-frequency vibrator. It can also conduct differential low-frequency current. The filter circuit is longer than 1 / 8 wavelength of the choke frequency. The longer it is, the more obvious the effect. The second is a filter formed by a high-frequency 1 / 4 wavelength impedance line connected in parallel to the low-frequency vibrator. It has the characteristics of the above two filter circuits. The low-frequency vibrator with hollow features can reduce diffraction to the high-frequency vibrator.

[0060] In summary, the dual-polarization radiation unit 210 proposed in the present disclosure has a hollow area, so that the interference with the electromagnetic wave signal generated by the radiation unit for other frequency bands (such as the radiation unit 220 of the high frequency band) can be reduced, so that the dual-polarization radiation unit 210 proposed in the present disclosure is more friendly to system integration, and the radiation performance of the integrated multi-band radiation unit will also be better than the radiation performance of the radiation unit in the prior art. In addition, since the central part of the dual-polarization radiation unit 210 proposed in the present disclosure is DC-conductive, its manufacturing process is simpler and more convenient, and since the dual-polarization radiation unit 210 according to the present disclosure can be constructed in an integrated manner, its product consistency is better, and its radiation performance can also be better ensured.

[0061] The above is only an optional embodiment of the embodiment of the present disclosure, and is not intended to limit the embodiment of the present disclosure. For those skilled in the art, the embodiment of the present disclosure may have various changes and variations. Any modification, equivalent replacement, improvement, etc. made within the spirit and principle of the embodiment of the present disclosure shall be included in the protection scope of the embodiment of the present disclosure.

[0062] Although the embodiments of the present disclosure have been described with reference to several specific embodiments, it should be understood that the embodiments of the present disclosure are not limited to the specific embodiments disclosed. The embodiments of the present disclosure are intended to cover various modifications and equivalent arrangements included in the spirit and scope of the appended claims. The scope of the claims is consistent with the broadest interpretation, thereby including all such modifications and equivalent structures and functions.

Claims

1. A dual-polarization radiating unit for an antenna, characterized in that: The dual-polarization radiation unit comprises: Four dipoles, wherein the radiation arms of the four dipoles are planar structures and are symmetrical about two mutually perpendicular lines, wherein the two mutually perpendicular lines divide the radiation unit into four regions, and the central parts of the four regions are DC-conductive, four gaps, wherein the four gaps are respectively located at the junction of two adjacent areas among the four areas; Four feed lines, the four feed lines and the four regions are respectively located on both sides of the dielectric plate, the four feed lines are associated with the four slots, and each of the four feed lines extends from the middle region of the dual-polarized radiation unit to the feeding point of the slot associated therewith, And wherein each of the four regions has a hollow region.

2. The dual-polarization radiation unit according to claim 1, characterized in that: A first side of the dual-polarized radiation unit is perpendicular to a corresponding line of the two mutually perpendicular lines, wherein the first side is a side intersecting the corresponding line.

3. The dual-polarization radiation unit according to claim 2, characterized in that: The dual-polarization radiation unit has an octagonal shape.

4. The dual-polarization radiation unit according to claim 1, characterized in that: The length of the feed line is associated with a matching impedance.

5. The dual-polarization radiation unit according to claim 4, characterized in that: The dual-polarization radiation unit also includes: A common mode choke circuit is configured to be disposed proximate the feed point and associated with one of the four slots.

6. The dual-polarization radiation unit according to claim 5, characterized in that: The common mode choke circuit further includes a first track and a second track, wherein the first track and the second track are constructed in parallel with each other on both sides of the radiation arm in the form of inductor coils, and wherein the electrical lengths of the first track and the second track are equal, and the coil winding directions of the first track and the second track are consistent.

7. The dual-polarization radiation unit according to claim 1, characterized in that: The dual-polarization radiation unit also includes: A parallel filter is constructed as a metal wire extending inwardly from an edge of the hollow area.

8. The dual-polarization radiation unit according to claim 7, characterized in that: The parallel filter is designed as an open circuit.

9. The dual-polarization radiation unit according to claim 1, characterized in that: The dual-polarization radiation unit also includes: An inductor element extends from an edge of the hollow area away from the central area of ​​the dual-polarized radiation unit toward the central area.

10. An antenna, characterized in that: The antenna comprises: At least one dual-polarized radiating element according to any one of claims 1 to 9; and Radiating element matching circuit.

11. An antenna system, characterized in that: The antenna system comprises: The antenna according to claim 10; and At least one second antenna, wherein the operating frequency band of the at least one second antenna is higher than the operating frequency band of the antenna.

12. The antenna system according to claim 11, characterized in that The antenna and the second antenna are arranged alternately.

13. The antenna system according to claim 12, characterized in that The number of columns of the first antenna is equal to the number of columns of the second antenna, or the number of columns of the second antenna is twice the number of columns of the first antenna.

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