Power supply module and computing device

Abstract

The embodiment of the invention provides a power supply module and computing equipment, the power supply module comprises a controller, an LLC resonant circuit and a phase-shifted full-bridge circuit, the controller is connected with the LLC resonant circuit and the phase-shifted full-bridge circuit, the input end of the LLC resonant circuit is connected with the input end of the phase-shifted full-bridge circuit in parallel and is connected with a power supply, and the input end of the LLC resonant circuit is connected with the input end of the phase-shifted full-bridge circuit. The output end of the LLC resonant circuit is connected in series with the output end of the phase-shifted full-bridge circuit and is connected with a load; and the controller is used for controlling the output voltage of the phase-shifted full-bridge circuit according to the input voltage of the power supply and the constant voltage of the load under the condition that the input voltage of the power supply changes, so that the output voltage of the power supply module is constant. According to the power supply module and the computing equipment, the output voltage of the power supply module can be ensured to be stable under the condition that the input voltage is changed, so that the power supply stability of the power supply module to a load can be ensured, and the conversion efficiency of the power supply module can be improved.

Description

Technical Field

[0001] The embodiments of the present application relate to the technical field of servers, and in particular, to a power supply module and a computing device. Background Art

[0002] A power supply unit (PSU) can be used to convert the voltage input by a power supply into the operating voltage required by a load. It can be understood that the voltage input by the power supply may fluctuate up and down, so that the voltage input to the power supply module can have a wide input range. For example, the wide input range can be 90V to 400V.

[0003] In the related art, in order to ensure the power supply stability of the power supply module in a wide input range, the power supply module can adopt a structure in which two-stage topology circuits are connected in series. Among them, the first-stage topology circuit can include a buck (Buck) circuit and / or a boost (Boost) circuit, and the second-stage topology circuit can be an LLC topology circuit.

[0004] However, the structure in which two-stage topology circuits are connected in series will result in a low conversion efficiency of the power supply module. For example, the conversion efficiency of the first-stage topology circuit is 90%, and the conversion efficiency of the second-stage topology circuit is 90%. After these two-stage topology circuits are connected in series, the total conversion efficiency of the power supply module is reduced to 81%. Summary of the Invention

[0005] The embodiments of the present application provide a power supply module and a computing device, which are beneficial to improving the conversion efficiency of the power supply module.

[0006] In a first aspect, the embodiments of the present application provide a power supply module, including: a controller, an LLC resonant circuit, and a phase-shifted full-bridge circuit, where

[0007] the controller is respectively connected to the LLC resonant circuit and the phase-shifted full-bridge circuit. The input ends of the LLC resonant circuit and the phase-shifted full-bridge circuit are connected in parallel and connected to a power supply. The output ends of the LLC resonant circuit and the phase-shifted full-bridge circuit are connected in series and connected to a load;

[0008] The controller is configured to, when the input voltage of the power supply changes, control the output voltage of the phase-shifted full-bridge circuit according to the input voltage of the power supply and the constant voltage of the load, so that the output voltage of the power supply module is constant.

[0009] In the above technical solution, the power supply module can adopt a structure in which two primary topology circuits (LLC resonant circuit and phase-shifted full-bridge circuit) are connected in parallel. By controlling the open-loop processing of the LLC resonant circuit and the closed-loop processing of the phase-shifted full-bridge circuit through a controller, when the input voltage of the power supply changes, the controller controls the working process of the phase-shifted full-bridge circuit to ensure that both the LLC resonant circuit and the phase-shifted full-bridge circuit work at a relatively high conversion efficiency, so that the output voltage of the power supply module remains constant under the condition of input voltage fluctuation, thereby ensuring the power supply stability of the power supply module in a wide input range with large input voltage changes, and being beneficial to improving the conversion efficiency of the power supply module.

[0010] In a possible implementation manner, the LLC resonant circuit includes a first switching circuit, a resonant cavity, a first transformer, and a first rectifying circuit, where

[0011] The first switching circuit is respectively connected to the controller and the resonant cavity, and the first switching circuit is also connected to the power supply;

[0012] The primary side of the first transformer is connected to the resonant cavity;

[0013] The first end of the first rectifying circuit is connected to the secondary side of the first transformer, and the second end of the first rectifying circuit is connected to the load.

[0014] In the above technical solution, the first switching circuit can be used to drive the resonant cavity, and the first switching circuit can convert the input voltage of the power supply into a square wave voltage and transmit it to the resonant cavity; the resonant cavity can eliminate the harmonics of the square wave voltage and output a sine wave voltage to the primary side of the first transformer; the primary side of the first transformer transmits the sine wave voltage to the secondary side and boosts or buck-boosts the sine wave voltage according to the load demand to obtain a sine wave voltage after boost or buck-boost processing; the first rectifying circuit can perform rectifying and filtering processing on the sine wave voltage after boost or buck-boost processing to convert the sine wave voltage into a stable output voltage.

[0015] In a possible implementation manner, the resonant cavity includes: a resonant inductor, an exciting inductor, and a resonant capacitor, where

[0016] The first end of the resonant capacitor is connected to the first switching circuit, and the second end of the resonant capacitor is connected to the first end of the resonant inductor;

[0017] The second end of the resonant inductor is respectively connected to the first end of the exciting inductor and the first end of the primary side of the first transformer;

[0018] The second end of the exciting inductor is respectively connected to the second end of the primary side of the first transformer and the first switching circuit.

[0019] In the above technical solution, the resonant cavity can be used to generate a resonant current, so that the LLC resonant circuit operates at the resonant frequency, thereby enabling each switching transistor in the first switching circuit to turn on and off under soft-switching conditions, and enabling each switching transistor to turn on and off under zero-voltage / zero-current conditions, so as to reduce the power loss of each switching transistor and improve the efficiency of each switching transistor.

[0020] In a possible implementation, the first rectifying circuit includes a first diode, a second diode, and a first filter capacitor, where

[0021] The anode of the first diode is connected to the first end of the secondary side of the first transformer, and the cathode of the first diode is respectively connected to the first end of the first filter capacitor and the first end of the load;

[0022] The anode of the second diode is connected to the second end of the secondary side of the first transformer, and the cathode of the second diode is respectively connected to the cathode of the first diode and the first end of the first filter capacitor;

[0023] The second end of the first filter capacitor is respectively connected to the second end of the load and the third end of the secondary side of the first transformer.

[0024] In the above technical solution, the first rectifying circuit can be used to filter the AC square-wave voltage output from the secondary side of the first transformer to obtain a stable output voltage.

[0025] In a possible implementation, the phase-shifted full-bridge circuit includes a second switching circuit, a first inductor, a second transformer, and a second rectifying circuit, where

[0026] The second switching circuit is respectively connected to the controller, the first end of the first inductor, and the second end of the primary side of the second transformer, and the second switching circuit is also connected to the power supply;

[0027] The second end of the first inductor is also connected to the first end of the primary side of the second transformer;

[0028] The input end of the second rectifying circuit is connected to the secondary side of the second transformer, and the output end of the second rectifying circuit is also connected to the load.

[0029] In the above technical solution, the second switching circuit 131 can convert the input voltage into a square-wave voltage, the second inductor can convert the square-wave voltage into an AC square-wave voltage and output the AC square-wave voltage to the primary side of the second transformer; the second transformer can step down and isolate the AC square-wave voltage; the second rectifying circuit can filter the AC square-wave voltage output from the secondary side of the second transformer to obtain a stable output voltage.

[0030] In a possible implementation, the second rectifying circuit includes a third diode, a fourth diode, a second inductor, and a second filter capacitor, where

[0031] The anode of the third diode is connected to the first end of the secondary side of the second transformer, and the cathode of the third diode is connected to the first end of the second inductor;

[0032] The anode of the fourth diode is connected to the second end of the secondary side of the second transformer, and the cathode of the fourth diode is respectively connected to the cathode of the third diode and the first end of the second inductor;

[0033] The second end of the second inductor is respectively connected to the first end of the second filter capacitor and the first end of the load;

[0034] The second end of the second filter capacitor is respectively connected to the third end of the secondary side of the second transformer and the second end of the load.

[0035] In the above technical solution, the second rectifying circuit can be used to filter the AC square-wave voltage output by the secondary side of the second transformer to obtain a stable output voltage.

[0036] In a possible implementation manner, the controller is specifically configured to:

[0037] When the input voltage is equal to the rated input voltage, output a first control signal to the LLC resonant circuit to control the LLC resonant circuit to output a first voltage through the first control signal, and the first control signal is used to control the LLC resonant circuit to operate in a resonant state;

[0038] Determine a second voltage according to the first voltage and the constant voltage of the load;

[0039] Determine a second control signal according to the second voltage, and output the second control signal to the phase-shifted full-bridge circuit to control the phase-shifted full-bridge circuit to output a second voltage through the second control signal, and the duty cycle of the second control signal is a preset duty cycle.

[0040] In the above technical solution, the controller can, when the input voltage is equal to the rated input voltage, make the LLC resonant circuit operate in a resonant state with the minimum loss and the maximum output power by controlling the frequency of the first control signal to be equal to the resonant frequency of the LLC resonant circuit and operate at the best conversion efficiency; and adjust the duty cycle of the second control signal to the preset duty cycle so that the output voltage of the phase-shifted full-bridge circuit is the second voltage, thereby enabling the total output voltage of the power supply module to be constant and still equal to the constant voltage of the load. In this process, the controller can adjust the output voltage of the phase-shifted full-bridge circuit so that the overall output voltage of the power supply module is still the constant voltage of the load, which is beneficial to ensuring the power supply stability of the power supply module.

[0041] In a possible implementation manner, the controller is specifically configured to:

[0042] When the input voltage is less than or greater than the rated input voltage, a first control signal is output to the LLC resonant circuit to control the LLC resonant circuit to output a third voltage corresponding to the input voltage through the first control signal. The first control signal is used to control the LLC resonant circuit to operate in a resonant state;

[0043] Determine a fourth voltage according to the third voltage and the constant voltage of the load;

[0044] Determine a second control signal according to the fourth voltage and output the second control signal to the phase-shifted full-bridge circuit to control the phase-shifted full-bridge circuit to output the fourth voltage through the second control signal;

[0045] When the input voltage is less than the rated input voltage, the duty cycle of the second control signal is greater than a preset duty cycle;

[0046] When the input voltage is greater than the rated input voltage, the duty cycle of the second control signal is less than the preset duty cycle.

[0047] In the above technical solution, the controller can still control the LLC resonant circuit to operate in a resonant state through the first control signal when the input voltage is less than or greater than the rated input voltage, with the minimum loss and the maximum output power, and operate at the best conversion efficiency; when the input voltage is less than the rated input voltage, by increasing the duty cycle of the second control signal to above the preset duty cycle to achieve the purpose of increasing the fourth voltage, so that even when the third voltage decreases, the total output voltage can still be kept constant by increasing the fourth voltage and still be equal to the constant voltage of the load; and, when the input voltage is greater than the rated input voltage, by reducing the duty cycle of the second control signal to below the preset duty cycle to achieve the purpose of reducing the fourth voltage, so that even when the third voltage increases, the total output voltage can still be kept constant by reducing the fourth voltage and still be equal to the constant voltage of the load.

[0048] In a possible implementation manner, the controller is further specifically configured to:

[0049] Adjust the phase of the second control signal to make the phase-shifted full-bridge circuit operate in a soft-switching state.

[0050] In the above technical solution, by adjusting the phase of the second control signal, the phase difference between the control signals of each switch tube in the phase-shifted full-bridge circuit can be adjusted, so that each switch tube in the phase-shifted full-bridge circuit turns on and off under soft-switching conditions, which is beneficial to reducing the switching loss and realizing the operation of the phase-shifted full-bridge circuit at the best conversion efficiency, and further making the overall power supply module have a high conversion efficiency.

[0051] In a second aspect, an embodiment of the present application provides a computing device, which includes the power supply module as described in any item of the first aspect.

[0052] In the above technical solution, the power supply module can adopt a structure in which two primary topology circuits (LLC resonant circuit and phase-shifted full-bridge circuit) are connected in parallel. By controlling the open-loop processing of the LLC resonant circuit and the closed-loop processing of the phase-shifted full-bridge circuit through a controller, when the input voltage of the power supply changes, the controller controls the working processes of the LLC resonant circuit and the phase-shifted full-bridge circuit to ensure that both the LLC resonant circuit and the phase-shifted full-bridge circuit work at a relatively high conversion efficiency, so that the output voltage of the power supply module remains constant under the condition of input voltage fluctuation, thereby ensuring the power supply stability of the power supply module in a wide input range with a large change in the input voltage, and being beneficial to improving the conversion efficiency of the power supply module. Moreover, in high-power scenarios, by improving the conversion efficiency of the power supply module, when the output power is a fixed value and the output power of each power supply module is the same, the number of power supply modules arranged can be reduced, which is beneficial to reducing the layout density of the power supply modules, thereby resulting in a reduction in the overall heat of the power supply modules, being beneficial to reducing the heat dissipation requirements of the power supply modules, improving the power supply reliability of the power supply modules, making the power supply modules supply power to the computing device more stably, and thus ensuring the stable operation of the computing device.

[0053] The power supply module and the computing device provided by the embodiments of the present application adopt a structure in which two primary topology circuits, namely an LLC resonant circuit and a phase-shifted full-bridge circuit, are connected in parallel. When the input voltage changes, according to the input voltage and the constant voltage of the load, the controller flexibly adjusts the output voltage of the phase-shifted full-bridge circuit, so that the output voltage of the power supply module remains constant, thereby ensuring the power supply stability of the power supply module for the load in a wide input range of the input voltage of the power supply. Moreover, the power supply module can also adjust the working processes of the LLC resonant circuit and the phase-shifted full-bridge circuit through the controller to ensure that both the LLC resonant circuit and the phase-shifted full-bridge circuit have a relatively high conversion efficiency, which is beneficial to improving the conversion efficiency of the power supply module. Description of the Drawings

[0054] In order to more clearly illustrate the technical solutions in the embodiments of the present application or the prior art, the following will briefly introduce the drawings required for use in the description of the embodiments or the prior art. Obviously, the following drawings are only some embodiments of the embodiments of the present application. For those of ordinary skill in the art, without creative efforts, other drawings can also be obtained based on these drawings.

[0055] Figure 1 One of the structural schematic diagrams of the power supply module provided by the embodiments of the present application;

[0056] Figure 2A A structural schematic diagram of an LLC resonant circuit provided by the embodiments of the present application;

[0057] Figure 2B Another structural schematic diagram of the LLC resonant circuit provided by the embodiment of the present application;

[0058] Figure 3 A waveform schematic diagram of an LLC resonant circuit provided by the embodiment of the present application;

[0059] Figure 4 A structural schematic diagram of a phase-shifted full-bridge circuit provided by the embodiment of the present application;

[0060] Figure 5 A waveform schematic diagram of a phase-shifted full-bridge circuit provided by the embodiment of the present application;

[0061] Figure 6 The second structural schematic diagram of the power module provided by the embodiment of the present application;

[0062] Figure 7 The third structural schematic diagram of the power module provided by the embodiment of the present application;

[0063] Figure 8 The fourth structural schematic diagram of the power module provided by the embodiment of the present application;

[0064] Figure 9 A flowchart of a control method provided by the embodiment of the present application;

[0065] Figure 10 A structural schematic diagram of a computing device provided by the embodiment of the present application. Detailed implementation manners

[0066] Here, the exemplary embodiments will be described in detail, and the examples are shown in the accompanying drawings. When the following description refers to the accompanying drawings, unless otherwise indicated, the same numbers in different drawings represent the same or similar elements. The implementation manners described in the following exemplary embodiments do not represent all implementation manners consistent with the embodiments of the present application. On the contrary, they are merely examples of devices and methods consistent with some aspects of the embodiments of the present application as detailed in the appended claims.

[0067] It should be noted that in the embodiments of the present application, the term "at least one" means one or more, and "a plurality" means two or more.

[0068] An embodiment of the present application provides a power module. The power module can adopt a structure in which two primary topology circuits (LLC resonant circuit and phase-shifted full-bridge circuit) are connected in parallel. The controller controls the open-loop processing of the LLC resonant circuit and the closed-loop processing of the phase-shifted full-bridge circuit. When the input voltage of the power supply changes, the controller controls the working processes of the LLC resonant circuit and the phase-shifted full-bridge circuit to ensure that both the LLC resonant circuit and the phase-shifted full-bridge circuit operate at a relatively high conversion efficiency, so that the output voltage of the power module remains constant under the condition of input voltage fluctuation. Thus, the power supply stability of the power module can be ensured in a wide input range with a large change in input voltage (for example, 90V to 400V), and it is beneficial to improve the conversion efficiency of the power module. Moreover, in a high-power scenario, by improving the conversion efficiency of the power module, when the output power is a fixed value and the output power of each power module is the same, the number of power module arrangements can be reduced, which is beneficial to reducing the layout density of the power module, thereby reducing the overall heat of the power module, being beneficial to reducing the heat dissipation requirement of the power module, and improving the power supply reliability of the power module.

[0069] The conversion efficiency of the power module can be the efficiency of converting the voltage input by the power supply into the working voltage required by the load by the power module. This conversion efficiency can be the ratio between the input power and the output power of the power module. Assuming the input power of the power module is P1 and the output power is P2, the conversion efficiency = P2 / P1.

[0070] The power module provided by the embodiment of the present application can be applied to the following scenarios: high-power scenarios; or scenarios where the power module needs to have a wide input range and a wide output range; or scenarios with high heat dissipation requirements.

[0071] Next, in conjunction with Figures 1 to 8 , the structure of the power module provided by the embodiment of the present application will be introduced in detail through specific embodiments. It should be noted that the following several embodiments can exist independently or be combined with each other. For the same or similar content, it will not be repeated in different embodiments.

[0072] Figure 1 is one of the structural schematic diagrams of the power module provided by the embodiment of the present application. Please refer to Figure 1 , the power module 10 can include: a controller 11, an LLC resonant circuit 12, and a phase-shifted full-bridge circuit 13. Among them,

[0073] The controller 11 is respectively connected to the LLC resonant circuit 12 and the phase-shifted full-bridge circuit 13. The input ends of the LLC resonant circuit 12 and the phase-shifted full-bridge circuit 13 are connected in parallel and connected to the power supply 20. The output ends of the LLC resonant circuit 12 and the phase-shifted full-bridge circuit 13 are connected in series and connected to the load 30.

[0074] The controller 11 can be used to control the output voltage of the phase-shifted full-bridge circuit 13 according to the input voltage of the power supply 20 and the constant voltage of the load when the input voltage of the power supply 20 changes, so as to make the output voltage of the power module constant. When the output voltage of the power module reaches a constant value, the output voltage of the power module is equal to the constant voltage of the load.

[0075] It should be noted that the output voltage of the power module here is the working voltage of the load. When the input voltage changes (increases or decreases), the working voltage of the load will also change and cannot be stabilized. The constant voltage of the load is the constant voltage that the power module needs to output, which is a fixed value. For example, it can be 50V, 100V or other constants. Generally, the constant voltage of the load is the voltage when the load 30 works normally. When the power module supplies power to the load, the output voltage of the power module is the working voltage of the load. When the input voltage of the power module is constant, such as the rated input voltage, the load works in a normal state. At this time, the working voltage of the load is the constant voltage of the load. However, if there is a fluctuation in the input voltage, the working voltage of the load will change accordingly, which will affect the operation of the load. Therefore, it is necessary to control the power module to make the working voltage of the load return to the constant voltage of the load again, so that the load can work normally.

[0076] In this power module, a structure in which two first-level topology circuits, namely the LLC resonant circuit 12 and the phase-shifted full-bridge circuit 13, are connected in parallel is adopted. When the input voltage changes, according to the input voltage and the constant voltage of the load, the controller flexibly controls the output voltage of the phase-shifted full-bridge circuit 13, so that the output voltage of the power module is constant, thereby ensuring the stability of the power module to supply power to the load within a wide input range of the input voltage of the power supply. For example, when the input voltage of the power supply fluctuates within a wide input range of 90V to 400V, the power module can still adjust the output voltage of the phase-shifted full-bridge circuit through the controller to make the total output voltage of the power module constant, thereby ensuring the stability of the power module to supply power to the load. Moreover, the power module can also adjust the working processes of the LLC resonant circuit 12 and the phase-shifted full-bridge circuit 13 through the controller to ensure that both the LLC resonant circuit 12 and the phase-shifted full-bridge circuit 13 have high conversion efficiencies, which is beneficial to improving the conversion efficiency of the power module.

[0077] To facilitate the understanding of the control process of the controller 11 for the LLC resonant circuit 12 and the phase-shifted full-bridge circuit 13, first, the LLC resonant circuit 12 and the phase-shifted full-bridge circuit 13 will be introduced in detail respectively.

[0078] (1) LLC resonant circuit 12

[0079] The LLC resonant circuit 12 may include a first switching circuit 121, a resonant cavity 122, a first transformer 123, and a first rectifying circuit 124.

[0080] First, the connection relationships of the first switching circuit 121, the resonant cavity 122, the first transformer 123, and the first rectifying circuit 124 will be described.

[0081] The first switching circuit 121 is respectively connected to the controller 11 and the resonant cavity 122; the first switching circuit 121 is also connected to the power supply 20.

[0082] The primary side of the first transformer 123 is connected to the resonant cavity 122.

[0083] The first end of the first rectifying circuit 124 is connected to the secondary side of the first transformer 123, and the second end of the first rectifying circuit 124 is connected to the load 30.

[0084] Secondly, the structures of the first switching circuit 121, the first switching circuit 121, the resonant cavity 122, the first transformer 123, and the first rectifying circuit 124 will be described.

[0085] The first switching circuit 121 may include a plurality of switching tubes. These plurality of switching tubes may form a full-bridge topology circuit or a half-bridge topology circuit. The switching tube may be a Metal-Oxide-Semiconductor Field-Effect Transistor (MOSFET, simply referred to as MOS), or the switching tube may also be other switching tubes for controlling the on / off of the circuit. The embodiments of the present application are not limited thereto.

[0086] The resonant cavity 122 may include a resonant inductor, an exciting inductor, and a resonant capacitor. Wherein, the first end of the resonant capacitor is connected to the first switching circuit, and the second end of the resonant capacitor is connected to the first end of the resonant inductor; the second end of the resonant inductor is respectively connected to the first end of the exciting inductor and the first end of the primary side of the first transformer; the second end of the exciting inductor is respectively connected to the second end of the primary side of the first transformer and the first switching circuit.

[0087] The first transformer 123 may include a primary side and a secondary side, and the primary side and the secondary side may include at least one winding.

[0088] The first rectifier circuit 124 may include a diode and a filter capacitor. Optionally, the first rectifier circuit 124 may include a first diode, a second diode, and a first filter capacitor. Wherein, the anode of the first diode is connected to the first end of the secondary side of the first transformer, and the cathode of the first diode is respectively connected to the first end of the first filter capacitor and the first end of the load 30; the anode of the second diode is connected to the second end of the secondary side of the first transformer, and the cathode of the second diode is respectively connected to the cathode of the first diode and the first end of the first filter capacitor; the second end of the first filter capacitor is respectively connected to the second end of the load 30 and the third end of the secondary side of the first transformer.

[0089] Next, with reference to Figure 2A and Figure 2B , an exemplary description of the structure of the LLC resonant circuit provided in the embodiments of the present application will be given.

[0090] Figure 2A For a schematic diagram of the structure of an LLC resonant circuit provided in an embodiment of the present application, please refer to Figure 2A , the LLC resonant circuit 12 may include a first switch circuit 121, a resonant cavity 122, a first transformer 123, and a first rectifier circuit 124, where:

[0091] The first switch circuit 121 may be a half-bridge topology circuit composed of a switching tube S1 and a switching tube S2 connected in series. The first switch circuit 121 may be connected between the positive connection end and the negative connection end of the power supply 20. Specifically, the first end of the switching tube S1 is connected to the positive connection end of the power supply 20, the second end of the switching tube S2 is connected to the negative connection end of the power supply 20, and the second end of the switching tube S1 is connected to the first end of the switching tube S2.

[0092] The resonant cavity 122 may include a resonant capacitor Cr, a resonant inductor Lr, and an exciting inductor Lm. Wherein, the first end of the resonant capacitor Cr is respectively connected to the second end of the switching tube S1 and the first end of the switching tube S2, and the second end of the resonant capacitor Cr is connected to the first end of the resonant inductor Lr; the second end of the resonant inductor Lr is respectively connected to the first end of the primary side of the first transformer 123 and the first end of the exciting inductor Lm; the second end of the exciting inductor Lm is respectively connected to the second end of the switching tube S2 and the second end of the primary side of the first transformer 123.

[0093] The primary side of the first transformer 123 includes 1 winding, and the secondary side includes 2 windings. It should be noted that in Figure 2A , in the embodiments of the present application, an example is given where the primary side includes one winding and the secondary side includes 2 windings. In other embodiments, the number of windings on the primary side and the secondary side can be any number set according to the user's power consumption requirements, and the embodiments of the present application do not limit this.

[0094] The first rectifier circuit 124 may include a diode D1, a diode D2, and a filter capacitor Co. Among them, the anode of the diode D1 is connected to the first end of the secondary side of the first transformer 123, and the cathode of the diode D1 is respectively connected to the first end of the load 30 and the first end of the filter capacitor Co; the anode of the diode D2 is connected to the second end of the secondary side of the first transformer 123, and the cathode of the diode D2 is respectively connected to the cathode of the diode D1 and the first end of the load 30; the first end of the filter capacitor Co is respectively connected to the cathode of the diode D1 and the first end of the load 30, the second end of the filter capacitor Co is respectively connected to the third end of the secondary side of the first transformer 123 and the second end of the load 30, and the second end of the load is also connected to the third end of the secondary side of the first transformer 123.

[0095] Figure 2B For a schematic diagram of another LLC resonant circuit provided by an embodiment of the present application, please refer to Figure 2B , the LLC resonant circuit 12 may include a first switching circuit 121, a resonant cavity 122, a first transformer 123, and a first rectifier circuit 124, where:

[0096] The first switching circuit 121 may include 4 switching tubes, namely: a first switching tube Q1, a second switching tube Q2, a third switching tube Q3, and a fourth switching tube Q4. Among them, the first switching tube Q1 and the third switching tube Q3 are connected in series to form a first bridge arm 121-1, the second switching tube Q2 and the fourth switching tube Q4 are connected in series to form a second bridge arm 121-2, and the first bridge arm 121-1 and the second bridge arm 121-2 are connected in parallel and connected between the positive connection end and the negative connection end of the power supply 20.

[0097] In the embodiment of the present application, Figure 2B Taking the 4 switching tubes in

[0098] The resonant cavity 122 may include a resonant capacitor Cr, a resonant inductor Lr, and an exciting inductor Lm. Among them, the first end of the resonant capacitor Cr is respectively connected to the source of the first switching transistor Q1 and the drain of the third switching transistor Q3. The second end of the resonant capacitor Cr is connected to the first end of the resonant inductor Lr. The second end of the resonant inductor Lr is respectively connected to the first end of the primary side of the first transformer 123 and the first end of the exciting inductor Lm. The second end of the exciting inductor Lm is respectively connected to the drain of the fourth switching transistor Q4 and the second end of the primary side of the first transformer 123.

[0099] The primary side of the first transformer 123 includes one winding, and the secondary side includes two windings. It should be noted that, in this embodiment of the present application, the case where the primary side includes one winding and the secondary side includes two windings is taken as an example for illustration. In other embodiments, the number of windings on the primary side and the secondary side can be any number set according to the user's power consumption requirements, and this embodiment of the present application does not limit this.

[0100] The first rectifier circuit 124 may include a first diode D1, a second diode D2, and a first filter capacitor Cout1. Among them: the anode of the first diode D1 is connected to the first end of the secondary side of the first transformer 123, and the cathode of the first diode D1 is respectively connected to the first end of the first filter capacitor Cout1 and the first end of the load 30; the anode of the second diode D2 is connected to the second end of the secondary side of the first transformer 123, and the cathode of the second diode D2 is respectively connected to the cathode of the first diode D1 and the first end of the first filter capacitor Cout1; the second end of the first filter capacitor Cout1 is respectively connected to the second end of the load 30 and the third end of the secondary side of the first transformer 123.

[0101] Next, the working principle of the LLC resonant circuit 12 will be described.

[0102] In the LLC resonant circuit 12, the first switching circuit 121 can be used to drive the resonant cavity 122. The first switching circuit 121 can convert the input voltage (DC voltage) of the power supply into a square wave voltage and transmit it to the resonant cavity 122; the resonant cavity 122 can eliminate the harmonics of the square wave voltage and output a sine wave voltage to the primary side of the first transformer 123; the primary side of the first transformer 123 transmits the sine wave voltage to the secondary side and boosts or buck-boosts the sine wave voltage according to the load demand to obtain a sine wave voltage after boost or buck-boost processing; the first rectifier circuit 124 can perform rectification and filtering on the sine wave voltage after boost or buck-boost processing to convert the sine wave voltage into a stable output voltage.

[0103] The resonant cavity 122 can be used to generate a resonant current to enable the LLC resonant circuit 12 to operate at the resonant frequency, so that each switching transistor in the first switching circuit 121 can be turned on and off under soft-switching conditions. Soft switching means that during the turn-on and turn-off processes of the power transistors (each switching transistor in the first switching circuit 121), the voltage and current are zero, or at least one of them is zero, and there is no overlapping of the non-zero parts of the voltage and current simultaneously during the switching process of the power transistors. For example, soft-switching methods can include: Zero Voltage Switching (ZVS) and Zero Current Switching (ZCS). Usually, approximate ZVS or ZCS can also be referred to as soft switching. The first switching circuit 121 is turned on and off under soft-switching conditions, which can enable each switching transistor to be turned on and off under zero-voltage / zero-current conditions, thereby reducing the power loss of each switching transistor and improving the efficiency of each switching transistor.

[0104] The resonant cavity 122 has two resonant frequencies, and these two resonant frequencies can satisfy the following formula:

[0105]

[0106] where f r1 and f r2 represent the resonant frequencies, L m represents the magnetizing inductance, L r represents the resonant inductance, C r represents the resonant capacitance. At the resonant frequency f r1 , the inductive reactance of the resonant inductance L r and the capacitive reactance of the resonant capacitance C r cancel each other out; at the resonant frequency f r2 , the total inductive reactance of the resonant inductance L r and the magnetizing inductance L m and the capacitive reactance of the resonant capacitance C r cancel each other out, minimizing the energy loss of the LLC resonant circuit, thereby improving the efficiency of the LLC resonant circuit.

[0107] In the embodiments of the present application, the controller 11 can control the frequency and phase of the conduction signals of each switching transistor in the LLC resonant circuit 12, so that the LLC resonant circuit 12 operates at the resonant frequency, thereby ensuring that the LLC resonant circuit 12 is in a resonant state. After phase shifting, each switching transistor (for example, Figure 2A S1 and S2 in Figure 2BQ1 to Q4) can achieve that the voltage and current are approximately zero during the turn-on and turn-off processes. During the switching process, there is no overlap of the non-zero parts of the voltage and current at the same time, enabling each switching tube to turn on and off under soft-switching conditions, reducing the losses of each switching tube, increasing the output power of the LLC resonant circuit, and thus improving the conversion efficiency of the LLC resonant circuit.

[0108] To facilitate the understanding of the working process of the LLC resonant circuit, hereinafter, in conjunction with Figure 3 , taking Figure 2A the working process of the LLC resonant circuit 12 shown as an example, the working process of the LLC resonant circuit will be described in detail.

[0109] Figure 3 This is a waveform schematic diagram of an LLC resonant circuit provided by an embodiment of the present application. Please refer to Figure 3 , under the variable-frequency modulation scheme with a fixed duty cycle of 50% in the LLC resonant circuit, Figure 2A the waveform change process of the LLC resonant circuit 12 shown can include the following 6 stages:

[0110] Stage 1 (t0 - t1 stage): The controller outputs a control signal V gs2 , causing the switching tube S1 in the first switching circuit 121 to turn off and the switching tube S2 to turn on. At this time, since S1 is off, the voltage V ds1 between the drain and source of S1 is equal to the input voltage V in , S2 is conducting, and the conduction voltage drop V ds2 of S2 is approximately zero; by controlling the conduction frequency of S1 and S2, the resonant capacitor Cr and the resonant inductor Lr in the resonant cavity 122 resonate, the resonant cavity 122 becomes resistive, and there is energy transfer between the primary and secondary sides of the first transformer 123, causing the magnetizing inductor Lm to be in a clamped state and not participate in the resonance; after the t0 moment, the current flowing direction in the primary side of the first transformer 123 is: the primary side of the first transformer 123 → Lr → Cr → S2 → Lm; the diode D1 in the first rectifier circuit is off and the diode D2 is on, and the current flowing direction in the secondary side of the first transformer 123 is: the secondary side of the first transformer 123 → D2 → load 30; in this stage, the current Ir on the resonant inductor Lr gradually decreases, and the current Im on the magnetizing inductor Lm gradually increases until at the t1 moment Im = Ir, causing the energy transfer between the primary and secondary sides of the first transformer 123 to stop, Id2 gradually decreases until it drops to 0, and Id1 is 0, realizing the zero-current turn-off of the diode D2.

[0111] Stage 2 (t1 - t2 stage): The controller does not need to output the control signals V gs1 and V gs2, both the switching transistors S1 and S2 in the first switching circuit 121 are turned off; at the moment t1, since Im = Ir, the energy transfer between the primary and secondary sides of the first transformer 123 stops, and the exciting inductor Lm is no longer in the clamped state. Thus, in this stage, the resonant capacitor Cr, the resonant inductor Lr, and the exciting inductor Lm in the resonant cavity 122 can participate in resonance together; after the switching transistor S2 is turned off, the resonant cavity 122 remains in the resonant state. The current flowing directions in the primary side of the first transformer 123 are: the negative connection terminal of the power supply 20 → Lm → Lr → Cr → S2, the negative connection terminal of the power supply 20 → Lm → Lr → Cr → S1 → the positive connection terminal of the power supply 20. Ir and Im will discharge the capacitor in the switching transistor S1, causing Vds1 to gradually decrease until it is approximately 0, and charge the capacitor in the switching transistor S2, causing Vds2 to gradually increase until it is approximately Vin, creating conditions for the zero-voltage turn-on of the switching transistor S1 at the moment t2 and realizing the soft-switching treatment of the switching transistor S1; in this stage, both the diodes D1 and D2 in the first rectifier circuit are turned off, and Id1 and Id2 are 0.

[0112] Stage 3 (from t2 to t3): The controller outputs a control signal V gs1 , causing the switching transistor S1 in the first switching circuit 121 to turn on and the switching transistor S2 to turn off; since S1 conducts, the conduction voltage drop V ds1 of S1 is approximately 0, and S2 is turned off, with the drain-source voltage V ds2 of S2 = Vin. This causes the resonant capacitor Cr and the resonant inductor Lr in the resonant cavity 122 to resonate, and there is energy transfer between the primary and secondary sides of the first transformer 123. The exciting inductor Lm is in the clamped state and does not participate in resonance; the current flowing direction in the primary side of the first transformer 123 is: the negative connection terminal of the power supply 20 → the primary side of the first transformer 123 → Lr → Cr → S1 → the positive connection terminal of the power supply 20; in the first rectifier circuit, the diode D1 conducts and the diode D2 turns off. The current flowing direction in the secondary side of the first transformer 123 is: the secondary side of the first transformer 123 → D1 → the load 30; in this stage, in the first rectifier circuit, the diode D1 conducts and the diode D2 turns off. Due to the energy transfer between the primary and secondary sides of the first transformer 123, Id1 gradually increases, and Id2 remains 0.

[0113] Stage 4 (from t3 to t4): The controller still controls through the control signal V gs1Turn on the switch tube S1 and turn off the switch tube S2 in the first switch circuit 121. The states of Vgs1, Vgs2, Vds1, and Vds2 in this stage are the same as those of Vgs1, Vgs2, Vds1, and Vds2 in stage 3, which will not be elaborated here; at time t3, since Im drops to 0, Ir reverses, and the flowing direction of the current in the primary side of the first transformer 123 becomes: the positive connection terminal of the power supply 20 → S1 → Cr → Lr → the primary side of the first transformer 123 → the negative connection terminal of the power supply 20. Ir gradually decreases and Im gradually increases until at time t4, Im = Ir, there is no energy transfer between the primary and secondary sides of the first transformer, and Id1 drops to 0 to achieve zero-current turn-off of the diode D1; the flowing direction of the current in the secondary side of the first transformer 123 is the same as that of the current in the secondary side of the first transformer 123 in stage 3.

[0114] Stage 5 (t4 - t5 stage): The controller does not need to output the control signals V gs1 and V gs2 , both the switch tube S1 and the switch tube S2 in the first switch circuit 121 are turned off; at time t4, after the switch tube S1 is turned off, since Im = Ir, there is no energy transfer between the primary and secondary sides of the first transformer, and the excitation inductor Lm is no longer in the clamped state. Thus, in this stage, the resonant capacitor Cr, the resonant inductor Lr, and the excitation inductor Lm in the resonant cavity 122 can participate in resonance together. The flowing direction of the current in the primary side of the first transformer 123 is respectively: the positive connection terminal of the power supply 20 → S1 → Cr → Lr → Lm → S2. Ir and Im will charge the capacitor in the switch tube S1 to make Vds1 gradually rise until it is approximately Vin, and discharge the capacitor in the switch tube S2 to make Vds2 gradually drop until it is approximately 0, creating conditions for zero-voltage turn-on of the switch tube S2 at time t5 and achieving soft-switching processing of the switch tube S2; in this stage, both the diode D1 and the diode D2 in the first rectifier circuit are turned off, and Id1 and Id2 are 0.

[0115] Stage 6 (t5 - t6 stage): The controller outputs the control signal V gs2 , making the switch tube S1 in the first switch circuit 121 turn off and the switch tube S2 turn on. At this time, since S1 is turned off, the voltage V ds1 between the drain and source of S1 is equal to the input voltage V in , and S2 is conducting. Under the action of stage 5, the conduction voltage drop V ds2Approximately 0; by controlling the conduction frequencies of S1 and S2, the resonant capacitor Cr and the resonant inductor Lr in the resonant cavity 122 resonate, the resonant cavity 122 becomes resistive, and there is energy transfer between the primary and secondary sides of the first transformer 123, so that the exciting inductor Lm is in a clamped state and does not participate in the resonance; after the moment t5, the flowing direction of the current on the primary side of the first transformer 123 is: S2 → Cr → Lr → the primary side of the first transformer 123; the diode D1 in the first rectifier circuit is turned off and the diode D2 is turned on, and the flowing direction of the current on the secondary side of the first transformer 123 is: the secondary side of the first transformer 123 → D2 → the load 30; at the moment t6, Im = 0, so that the Ir current reverses, and the process of stage 1 is repeated.

[0116] It should be noted that, in some embodiments, terms such as "turn on" and "conduct" can be replaced with each other, and terms such as "turn off" and "non-conduct" can be replaced with each other.

[0117] The power supply module provided by the embodiment of the present application can control the on-off timings of the switching tubes in the LLC resonant circuit 12 through the controller 11 to implement soft switching processing of the switching tubes in the LLC resonant circuit, which is beneficial to reducing the conduction loss and switching loss of the switching tubes, improving the efficiency of the switching tubes and the system reliability of the LLC resonant circuit; moreover, this control method is relatively simple, can support the use of components with a lower rated voltage, and has a lower control cost.

[0118] (2) Phase-shifted full-bridge circuit

[0119] The phase-shifted full-bridge circuit 13 may include a second switching circuit 131, a first inductor 132, a second transformer 133, and a second rectifier circuit 134.

[0120] First, the connection relationships among the second switching circuit 131, the first inductor 132, the second transformer 133, and the second rectifier circuit 134 are described.

[0121] The second switching circuit 131 is respectively connected to the controller 11, the first end of the first inductor 132, and the second end of the primary side of the second transformer 133, and the second switching circuit 131 is also connected to the power supply 20.

[0122] The second end of the first inductor 132 is also connected to the first end of the primary side of the second transformer 133.

[0123] The input end of the second rectifier circuit 134 is connected to the secondary side of the second transformer 133, and the output end of the second rectifier circuit 134 is also used to be connected to the load 30.

[0124] Secondly, the structures of the second switching circuit 131, the first inductor 132, the second transformer 133, and the second rectifier circuit 134 are described.

[0125] The second switching circuit 131 may include four switching tubes, which may be MOS tubes or other switching tubes for controlling the on / off of a circuit. The embodiments of the present application are not limited thereto.

[0126] The first inductor 132 may be a resonant inductor. The first inductor may be an inductor independent of the primary leakage inductance of the second transformer 133, or the first inductor may also be coupled in the primary leakage inductance of the second transformer 133.

[0127] The second transformer 133 may include a primary side and a secondary side, and the primary side and the secondary side may include at least one winding.

[0128] The second rectifying circuit 134 may include a third diode, a fourth diode, a second inductor, and a second filter capacitor. Among them, the anode of the third diode is connected to the first end of the secondary side of the second transformer 133, and the cathode of the third diode is connected to the first end of the second inductor; the anode of the fourth diode is connected to the second end of the secondary side of the second transformer 133, and the cathode of the fourth diode is respectively connected to the cathode of the third diode and the first end of the second inductor; the second end of the second inductor is respectively connected to the first end of the second filter capacitor and the first end of the load 30; the second end of the second filter capacitor is respectively connected to the third end of the secondary side of the second transformer 133 and the second end of the load 30.

[0129] Next, in combination with Figure 4 , an exemplary description of the structure of the phase-shifted full-bridge circuit 13 provided by the embodiments of the present application will be given.

[0130] Figure 4 It is a schematic structural diagram of a phase-shifted full-bridge circuit provided by an embodiment of the present application. Please refer to Figure 4 , the phase-shifted full-bridge circuit 13 may include a second switching circuit 131, a first inductor 132, a second transformer 133, and a second rectifying circuit 134, where:

[0131] The second switching circuit 131 includes four switching tubes, namely switching tubes Q5 to Q8; each of these four switching tubes is configured with a corresponding parasitic capacitor (or an externally added resonant capacitor) and a corresponding parasitic diode (or an externally added freewheeling diode). The parasitic capacitors (or externally added resonant capacitors) corresponding to the switching tubes Q5 to Q8 are C5 to C8 respectively, and the parasitic diodes (or externally added freewheeling diodes) corresponding to the switching tubes Q5 to Q8 are D5 to D8 respectively.

[0132] Among them, the switching transistor Q5 and the switching transistor Q7 can be connected in series to form the third bridge arm 131-1, and the switching transistor Q6 and the switching transistor Q8 can be connected in series to form the fourth bridge arm 131-2. The third bridge arm 131-1 and the fourth bridge arm 131-2 can be used to connect between the positive connection terminal and the negative connection terminal of the power supply 20. Specifically, the drain of the switching transistor Q5 in the third bridge arm 131-1 and the drain of the Q6 in the fourth bridge arm 131-2 are respectively connected to the positive connection terminal of the power supply 20. The source of the switching transistor Q5 is connected to the drain of the switching transistor Q7, and the source of the switching transistor Q6 is connected to the drain of the switching transistor Q8. The sources of the switching transistor Q7 and the switching transistor Q8 are also respectively connected to the negative connection terminal of the power supply 20. The gates of the switching transistor Q5, the switching transistor Q6, the switching transistor Q7, and the switching transistor Q8 are also respectively connected to the controller 11. The upper and lower switching transistors of the same bridge arm can conduct alternately, and the switching transistors in different bridge arms usually conduct simultaneously in a diagonal manner. For example, if the switching transistor Q5 in the third bridge arm 131-1 conducts, the switching transistor Q7 in the third bridge arm 131-1 turns off, and the switching transistor Q6 in the fourth bridge arm 131-2 turns off and the switching transistor Q8 conducts. If the switching transistor Q7 in the third bridge arm 131-1 conducts, the switching transistor Q5 in the third bridge arm 131-1 turns off, and the switching transistor Q6 in the fourth bridge arm 131-2 conducts and the switching transistor Q5 turns off.

[0133] The second inductor 132 may include a resonant inductor Lk. The first end of the resonant inductor Lk may be connected to point A between the switching transistor Q5 and the switching transistor Q7. The second end of the resonant inductor Lk is connected to the first end of the primary side of the second transformer 133. The second end of the primary side of the second transformer 133 is connected to point B between the switching transistor Q6 and the switching transistor Q8.

[0134] The primary side of the second transformer 133 includes one winding, and the secondary side includes two windings. It should be noted that in this embodiment of the present application, the case where the primary side of the second transformer includes one winding and the secondary side includes two windings is taken as an example for description. In other embodiments, the number of windings on the primary side and the secondary side can be any number set according to the user's power consumption requirements, and this embodiment of the present application is not limited thereto.

[0135] The second rectifier circuit 134 may include a third diode D3, a fourth diode D4, a second inductor Lf, and a second filter capacitor Cout2. Among them, the anode of the third diode D3 is connected to the first end of the secondary side of the second transformer 133, and the cathode of the third diode D3 is connected to the first end of the second inductor Lf; the anode of the fourth diode D4 is connected to the second end of the secondary side of the second transformer 133, and the cathode of the fourth diode D4 is respectively connected to the cathode of the third diode D3 and the first end of the second inductor Lf; the second end of the second inductor Lf is respectively connected to the first end of the second filter capacitor Cout2 and the first end of the load 30; the second end of the second filter capacitor Cout2 is respectively connected to the third end of the secondary side of the second transformer 133 and the second end of the load 30.

[0136] Next, the working principle of the phase-shifted full-bridge circuit 13 will be described in detail.

[0137] In the phase-shifted full-bridge circuit 13, the power supply 20 inputs a DC voltage Vi to the second switching circuit 131. The second switching circuit 131 can convert Vi into a high-frequency square-wave voltage with an average value of D×Vi, where D is the duty cycle of the switching tube; the second inductor 132 can convert the high-frequency square-wave voltage into an AC square-wave voltage with an average value of D×Vi and output the AC square-wave voltage to the primary side of the second transformer 133; the second transformer 133 can step down and isolate the AC square-wave voltage to obtain an AC square-wave voltage with an amplitude of n×D×Vi, where n is the turns ratio of the second transformer. For example, if the number of turns of the primary side of the second transformer is N1 and the number of turns of the secondary side is N2, then n = N1 / N2; the second rectifier circuit 132 can filter the AC square-wave voltage output from the secondary side of the second transformer 133 to obtain an output voltage with an amplitude of n×D×Vi and output the output voltage to the load 30. Based on the above working principle, the controller 11 can adjust the output voltage by controlling the duty cycle of the phase-shifted full-bridge circuit 13.

[0138] The conduction phase difference between two diagonal switching tubes in the phase-shifted full-bridge circuit can be called the phase-shift angle (0° to 180°). For example, Figure 4 There is a phase-shift angle between the switching tube Q5 and the switching tube Q8, and a phase-shift angle between the switching tube Q7 and the switching tube Q6 in the shown phase-shifted full-bridge circuit. In the embodiment of the present application, the controller 11 can adopt a pulse width modulation (PWM) control method to control the phase-shift angle of the phase-shifted full-bridge circuit 13 by controlling the PWM control signals of two diagonal switching tubes in the phase-shifted full-bridge circuit, so as to adjust the pulse width of the output voltage waveform of the phase-shifted full-bridge circuit 13, and further realize the adjustment of the output voltage of the phase-shifted full-bridge circuit 13.

[0139] The smaller the losses of each switch tube in the phase-shifted full-bridge circuit, the higher the conversion efficiency of the phase-shifted full-bridge circuit. The phase-shifted full-bridge circuit 13 can adopt a phase-shift control method through the controller 11, so that each switch tube in the second switch circuit 131 is turned on and off under soft-switching conditions, and the parasitic capacitance in each switch tube in the second switch circuit 131 (for example, Figure 4 C5 to C8 in) and the resonance of the first inductor (for example, Figure 4 Lk in) are used to reduce the losses of each switch tube, improve the output power of the phase-shifted full-bridge circuit 13, and further improve the conversion efficiency of the phase-shifted full-bridge circuit 13. Moreover, by performing soft-switching processing on each switch tube in the second switch circuit 131, the second switch circuit 131 can support the use of components with a lower rated voltage, which is beneficial to reducing costs.

[0140] To facilitate the understanding of the working process of the phase-shifted full-bridge circuit 13, hereinafter, in combination with Figure 5 , the Figure 4 working process of the phase-shifted full-bridge circuit 13 shown will be described in detail.

[0141] Figure 5 This is a waveform schematic diagram of a phase-shifted full-bridge circuit provided by an embodiment of the present application. Please refer to Figure 5 , the waveform change process of the phase-shifted full-bridge circuit 1 during the working process may include the following several stages:

[0142] Stage 1 (t0 - t1): The controller 11 outputs PWM drive signals to the switch tubes Q5 and Q8 in the second switch circuit 131 respectively, so that the switch tubes Q5 and Q8 are turned on, and the switch tubes Q6 and Q7 are turned off. The VAB between point A and point B is in a constant state and VAB is equal to the input voltage Vin of the power supply. The current Ip in the primary side of the second transformer 133 flows as follows: the positive connection end of the power supply 20 → Q5 → point A → Lk → the primary side of the second transformer 133 → point B → Q8 → the negative connection end of the power supply 20. Ip can supply power to the load on the secondary side of the third transformer 132 through Q5 and the first inductor Lk. At the same time, Ip can also charge the parasitic capacitances C6 and C7; the third diode D3 in the second rectifier circuit 134 is turned on, and the fourth diode D4 is turned off. D3, the second inductor Lf and the load 30 form a power supply loop. The current in the secondary side of the second transformer 133 flows as follows: the secondary side of the second transformer 133 → D3 → Lf → the load 30. The output voltage Vrect of the secondary side of the second transformer 133 = Vin / N, where N is the turns ratio of the second transformer 133.

[0143] Stage 2 (t1 - t2): The controller 11 outputs a PWM drive signal to the switching transistor Q8 in the second switching circuit 131, causing the switching transistor Q8 to conduct, while the remaining switching transistors are all turned off. The parasitic capacitance C5 of the switching transistor Q5 and the parasitic capacitance C7 of the switching transistor Q7 resonate with Lk, thereby enabling the switching transistor Q5 to turn off with zero voltage. Under the combined action of Lk, the inductance of the primary side and the inductance of the secondary side of the second transformer 133, the primary side of the second transformer 133 can be regarded as a constant current source, that is, Ip only slightly decreases without sudden change. The flow direction of Ip is: the positive connection terminal of the power supply 20 → C5 → point A → Lk → the primary side of the second transformer 133 → point B → Q8 → the negative connection terminal of the power supply 20. During the process of flowing through C5, C5 can be charged, causing the voltage across C5 to rise rapidly until it reaches Vin at time t2. C7 starts to discharge, causing the voltage of C7 to drop rapidly until it drops to 0 at time t2, thereby clamping the voltage at point A to 0V, and further causing VAB and Vrect to rapidly drop to zero.

[0144] Stage 3 (t2 - t3): In this stage, the switching transistors Q5 and Q6 remain off, the switching transistor Q8 remains on, and the switching transistor Q7 conducts after time t2. Since the charging of C5 and the discharging of C7 end at time t2 and the voltage across C7 is 0, D7 conducts for freewheeling, clamping the voltage between the drain and source of the switching transistor Q7 to 0, so that the switching transistor Q7 can achieve zero voltage turn-on after time t2. In this stage, the flow direction of IP is: point A → Lk → the primary side of the second transformer 133 → point B → Q8 → D7 → point A, and VAB and Vrect remain 0.

[0145] Stage 4 (t3 - t4): In this stage, the controller 11 outputs a PWM drive signal to the switching transistor Q7 in the second switching circuit 131, causing the switching transistor Q7 to conduct, while the remaining switching transistors are all turned off. At time t3, the voltage across the diode D8 is 0, and the switching transistor Q8 turns off with zero voltage. After the switching transistor Q8 turns off, under the combined action of Lk, the inductance of the primary side and the inductance of the secondary side of the second transformer 133, the primary side of the second transformer 133 can be regarded as a constant current source, that is, Ip only slightly decreases without sudden change. The flow direction of Ip is: the positive connection terminal of the power supply 20 → C6 → point B → C8 → Q7 → point A → Lk → the primary side of the second transformer 133 → point B. When Ip flows through C8, C8 can be charged until the voltage across C8 gradually rises to Vin, that is, the voltage at point B is Vin. At this time, the voltage at point A is still clamped to 0, making VAB = -Vin, and C6 starts to discharge, causing the voltage of C6 to drop rapidly. Since VAB of the primary side of the second transformer 133 is reversed, D3 and D4 in the second rectifying circuit 134 conduct simultaneously, resulting in a short circuit of the winding on the secondary side of the transformer 133, causing the waveform of Vrect to be lost in this stage ( Figure 5The area shown by the shadow).

[0146] Phase 5 (t4 - t5): In this phase, switch Q5 and Q8 remain off, switch Q7 remains on, and switch Q6 turns on after time t4. At time t4, the charging of C8 is completed, the voltage across C8 is Vin, VAB = -Vin, the resonance ends, and the flow direction of Ip is: the negative connection terminal of power supply 20 → D7 → point A → Lk → the primary side of the second transformer 133 → point B → D6 → the positive connection terminal of power supply 20. Since Ip no longer flows through C6 and C8 but conducts freewheeling through D6, the voltage between the drain and source of switch Q6 is clamped to 0, enabling switch Q6 to achieve zero-voltage turn-on after time t4. Also, due to the freewheeling of D6 and D7, the energy stored in Lk is fed back to the power supply, causing Ip to decrease rapidly. In this phase, D3 and D4 in the second rectifier circuit 134 still conduct simultaneously, and the winding of the secondary side of transformer 133 remains in a short-circuit state, so that the waveform of Vrect continues to be lost ( Figure 5 The area shown by the shadow).

[0147] Phase 6 (t5 - t6): In this phase, switch Q5 and Q8 remain off, and switches Q6 and Q7 remain on. At time t5, Ip drops to 0. Due to the absence of current, D6 and D7 in the second switch circuit 131 turn off naturally. After time t5, the flow direction of Ip is: the positive connection terminal of power supply 20 → Q6 → point B → the primary side of the second transformer 133 → Lk → point A → Q7 → the negative connection terminal of power supply 20. Since the voltage of the winding on the primary side of the second transformer 133 is still zero, Vin is fully applied across Lk, causing Ip to increase in the reverse direction. D3 and D4 in the second rectifier circuit 134 still conduct simultaneously, and the winding of the secondary side of transformer 133 remains in a short-circuit state, so that the waveform of Vrect continues to be lost ( Figure 5 The area shown by the shadow).

[0148] Stage 7 (t6 - t7): The controller 11 outputs PWM drive signals to the switching transistors Q6 and Q7 in the second switching circuit 131 respectively, causing the switching transistors Q6 and Q7 to conduct and the switching transistors Q5 and Q8 to turn off. The current Ip in the primary side of the second transformer 133 flows as follows: the positive connection terminal of the power supply 20 → Q6 → point B → the primary side of the second transformer 133 → Lk → point A → Q7 → the negative connection terminal of the power supply 20. The VAB between point A and point B is in a constant state and VAB = -Vin. In this stage, since the inductance reflected from the secondary side of the second transformer 133 is much larger than Lk, Ip increases slowly in the reverse direction. The third diode D3 in the second rectifier circuit 134 turns off and the fourth diode D4 conducts. D4, the second inductor Lf, and the load 30 form a power supply loop. The current in the secondary side of the second transformer 133 flows as follows: the secondary side of the second transformer 133 → D4 → Lf → load 30. The output voltage Vrect of the secondary side of the second transformer 133 is Vrect = Vin / N, where N is the turns ratio of the second transformer 133.

[0149] Stage 8 (t7 - t8): The controller 11 outputs a PWM drive signal to the switching transistor Q6 in the second switching circuit 131, causing the switching transistor Q6 to conduct and the other switching transistors to turn off. The parasitic capacitance C6 of the switching transistor Q5 and the parasitic capacitance C7 of the switching transistor Q7 resonate with Lk, causing the switching transistor Q7 to turn off at zero voltage. Under the combined action of Lk and the inductance reflected from the secondary side of the second transformer 133, the primary side of the second transformer 133 can be regarded as a constant current source, that is, Ip only decreases slightly without sudden change. The current direction of Ip is: the positive connection terminal of the power supply 20 → Q6 → point B → the primary side of the second transformer 133 → Lk → point A → C7 → the negative connection terminal of the power supply 20. During the process of flowing through C7, C7 can be charged, causing the voltage across C7 to rise rapidly until it reaches Vin at time t8. C5 starts to discharge, causing the voltage of C5 to drop rapidly until it drops to 0 at time t8, thereby clamping the voltage at point A to Vin, causing VAB and Vrect to drop to zero at time t8.

[0150] Stage 9 (t8 - t9): In this stage, the switching transistors Q7 and Q8 remain off, the switching transistor Q6 remains on, and the switching transistor Q5 conducts after time t8. Since the charging of C7 and the discharging of C5 end at time t8 and the voltage across C5 is 0, D5 conducts for freewheeling, clamping the voltage between the drain and source of the switching transistor Q5 to 0, enabling the switching transistor Q5 to turn on at zero voltage after time t8. In this stage, the current direction of IP is: the positive connection terminal of the power supply 20 → Q6 → point B → the primary side of the second transformer 133 → Lk → point A → D5 → Q6, and VAB and Vrect are still 0.

[0151] Phase 10 (t9 - t10): In this phase, the controller 11 outputs a PWM drive signal to the switching transistor Q5 in the second switching circuit 131, causing the switching transistor Q5 to conduct and the other switching transistors to turn off. At time t9, the voltage across the diode D6 is 0, and the switching transistor Q6 achieves zero-voltage turn-off. After the switching transistor Q6 turns off, under the combined action of Lk, the inductance of the primary side and the inductance of the secondary side of the second transformer 133, the primary side of the second transformer 133 can be regarded as a constant current source, that is, Ip only slightly decreases and does not change abruptly. The flow direction of Ip is: the negative connection terminal of the power supply 20 → C8 → point B → the primary side of the second transformer 133 → Lk → point A → D5 → C6 → point B. When Ip flows through C6, it can charge C6 until the voltage across C6 gradually rises to Vin. At this time, the voltage at point A is still clamped to Vin, and C8 starts to discharge, causing the voltage of C8 to quickly drop to 0, and VAB = Vin. Since VAB on the primary side of the second transformer 133 is reversed, D3 and D4 in the second rectifying circuit 134 conduct simultaneously, which in turn causes the windings on the secondary side of the transformer 133 to short-circuit, resulting in the loss of the Vrect waveform in this phase ( Figure 5 as shown by the shaded area). Moreover, when the windings on the secondary side are short-circuited, the inductance reflected back from the secondary side of the second transformer 133 disconnects and no longer participates in resonance. Since the inductance reflected back from the secondary side of the second transformer 133 is much larger than Lk, the inductance participating in resonance rapidly decreases, leading to a rapid decrease in Ip.

[0152] Phase 11 (t10 - t11): In this phase, the switching transistors Q6 and Q7 remain off, the switching transistor Q5 remains on, and the switching transistor Q8 conducts after time t10. At time t10, the charging of C6 is completed, the voltage across C6 is Vin, VAB = Vin, and the resonance ends. The flow direction of Ip is: the negative connection terminal of the power supply 20 → D8 → point B → the primary side of the second transformer 133 → Lk → point A → D5 → the positive connection terminal of the power supply 20. Since Ip no longer flows through C6 and C8 but conducts through D8 for freewheeling, the voltage between the drain and source of the switching transistor Q8 is clamped to 0, enabling the switching transistor Q8 to achieve zero-voltage conduction after time t10. Moreover, due to the freewheeling of D8 and D5, the energy stored in Lk is fed back to the power supply, resulting in a rapid decrease in Ip. In this phase, D3 and D4 in the second rectifying circuit 134 still conduct simultaneously, and the windings on the secondary side of the transformer 133 remain in a short-circuit state, causing the Vrect waveform in this phase to continue to be lost ( Figure 5 as shown by the shaded area).

[0153] Phase 12 (t11 - t12): In this phase, switch transistors Q6 and Q7 remain off, and switch transistors Q5 and Q8 remain on. At time t11, Ip drops to 0. Since there is no current, D5 and D8 in the second switch circuit 131 turn off naturally. After time t11, the flow direction of Ip is: the positive connection terminal of the power supply 20 → Q5 → point A → Lk → the primary side of the second transformer 133 → point B → Q8 → the negative connection terminal of the power supply 20. Since the winding voltage of the primary side of the second transformer 133 is still zero, Vin is fully applied across Lk, causing Ip to increase again. D3 and D4 in the second rectifier circuit 134 still conduct simultaneously, and the winding of the secondary side of the transformer 133 remains in a short - circuit state, causing the waveform of Vrect to continue to be lost ( Figure 5 in the shaded area shown).

[0154] Figure 6 This is the second structural schematic diagram of the power module provided by the embodiment of the present application. Please refer to Figure 6 , the power module 10 may include: a controller 11, an LLC resonant circuit 12, and a phase - shifted full - bridge circuit 13, where,

[0155] The LLC resonant circuit 12 may include a first switch circuit 121, a resonant cavity 122, a first transformer 123, and a first rectifier circuit 124. The phase - shifted full - bridge circuit 13 includes a second switch circuit 131, a first inductor 132, a second transformer 133, and a second rectifier circuit 134.

[0156] The first switch circuit 121 may include 4 switch transistors, namely the first switch transistor Q1, the second switch transistor Q2, the third switch transistor Q3, and the fourth switch transistor Q4. The resonant cavity 122 may include a resonant capacitor Cr, a resonant inductor Lr, and an exciting inductor Lm. The first rectifier circuit 124 may include a first diode D1, a second diode D2, and a first filter capacitor Cout1. Among them, the connection manner between the first switch circuit 121, the resonant cavity 122, the first transformer 123, and the first rectifier circuit 124 may refer to Figure 2B the connection manner in, and will not be elaborated here.

[0157] The first switch circuit 131 may include 4 switch transistors, namely the fifth switch transistor Q5, the sixth switch transistor Q6, the seventh switch transistor Q7, and the eighth switch transistor Q8. The first inductor 132 may be a resonant inductor Lk. The second rectifier circuit 124 may include a third diode D3, a fourth diode D4, a second inductor Lf, and a second filter capacitor Cout2. Among them, the connection manner between the second switch circuit 131, the first inductor 132, the second transformer 133, and the second rectifier circuit 134 may refer to Figure 4 the connection manner in, and will not be elaborated here.

[0158] Wherein, the drains of the fifth switching transistor Q5 and the sixth switching transistor Q6 are connected in series and then respectively connected to the drain of the first switching transistor Q1 and the positive connection terminal of the power supply 20.

[0159] In some embodiments, the power supply module 10 may further include a third filter capacitor Cin, which may be connected in parallel between the positive connection terminal and the negative connection terminal of the power supply 20, and the third filter capacitor Cin may be used to filter the voltage input by the power supply 20. The power supply is direct current.

[0160] The power supply module provided by the embodiments of the present application may adopt a structure in which an LLC resonant circuit and a phase-shifted full-bridge circuit are connected in parallel. By controlling the open-loop processing of the LLC resonant circuit and the closed-loop processing of the phase-shifted full-bridge circuit through a controller, and when the input voltage changes, the controller controls the working processes of the LLC resonant circuit and the phase-shifted full-bridge circuit to ensure that both the LLC resonant circuit and the phase-shifted full-bridge circuit work at a relatively high conversion efficiency, so that the output voltage of the power supply module is constant under the condition of input voltage fluctuation, thereby realizing improving the conversion efficiency of the power supply module on the basis of ensuring the power supply stability of the power supply module within a wide input range.

[0161] Figure 7 This is the third schematic diagram of the structure of the power supply module provided by the embodiments of the present application. Please refer to Figure 7 , in Figure 6 Based on the shown power supply module 10, the power supply module 10 may further include a voltage sampling circuit. The first end of the voltage sampling circuit is respectively connected to the cathode of the first diode D1, the first end of the first wave capacitor Cout1, and the first end of the load 30. The second end of the voltage sampling circuit is respectively connected to the second end of the first filter capacitor Cout1, the third end of the secondary side of the first transformer 123, and the second end of the load 30. The second end of the load 30 is connected to the second end of the second filter capacitor Cout2 of the phase-shifted full-bridge circuit 13 and the third end of the second transformer. The third end of the voltage sampling circuit is connected to the controller 11.

[0162] Please refer to Figure 7 , in the embodiments of the present application, the phase-shifted full-bridge circuit 13 is controlled in a closed loop. The output voltage V1 of the LLC resonant circuit 12 can be collected, and the output voltage V1 of the power supply module is fed back to the controller 11. The controller 11 calculates the duty cycle that the phase-shifted full-bridge circuit needs to adjust at this time according to the actual voltage V1, the input voltage Vi, the output voltage Vo of the power supply module that the load needs to be constant, and the turns ratio n of the second transformer Output a second control signal corresponding to the output voltage of the power supply module to the switching circuit 131 with the duty cycle, so that the output voltage of the power supply module reaches the required constant voltage Vo.

[0163] It is understandable that before designing the power supply module, the designer can obtain user requirement information. For example, the user requirement information may include the input voltage range that the power supply module can support. The designer can configure the LLC resonant circuit and the phase-shifted full-bridge circuit in the power supply module based on the user requirement information. For example, the number and connection relationship of the components in the first switch circuit, resonant cavity, first transformer, and first rectifying circuit in the LLC resonant circuit can be configured, and the number and connection relationship of the components in the second switch circuit, first inductor, second transformer, and second rectifying circuit in the phase-shifted full-bridge circuit can be configured; the turns ratio and input range of the first transformer in the LLC resonant circuit, and the turns ratio and input range of the second transformer in the phase-shifted full-bridge circuit can be configured.

[0164] Figure 8 This is the fourth structural schematic diagram of the power supply module provided by the embodiment of the present application. Please refer to Figure 8 , the power supply module 10 may include a controller 11, an LLC resonant circuit 12, a phase-shifted full-bridge circuit 13, a first collector 14, a second collector 15, and a third collector 16. Among them, the input ends of the LLC resonant circuit 12 and the phase-shifted full-bridge circuit 13 are connected in parallel and connected to the power supply 20, and the output ends of the LLC resonant circuit 12 and the phase-shifted full-bridge circuit 13 are connected in series and connected to the load 30.

[0165] The LLC resonant circuit 12 may include a first switch circuit 121, a resonant cavity 122, a first transformer 123, and a first rectifying circuit 124. The phase-shifted full-bridge circuit 13 may include a second switch circuit 131, a first inductor 132, a second transformer 133, and a second rectifying circuit 134. Among them, the specific connection manner among the first switch circuit 121, the resonant cavity 122, the first transformer 123, and the first rectifying circuit 124 can refer to Figure 6 the connection manner of the first switch circuit 121, the resonant cavity 122, the first transformer 123, and the first rectifying circuit 124 in the LLC resonant circuit 12 in Figure 6 ; the specific connection manner among the second switch circuit 131, the first inductor 132, the second transformer 133, and the second rectifying circuit 134 can refer to the connection manner of the second switch circuit 131, the first inductor 132, the second transformer 133, and the second rectifying circuit 134 in the phase-shifted full-bridge circuit 13 in

[0166] The controller 11 is also respectively connected to a first switch circuit 121, a second switch circuit 131, a first collector 14, a second collector 15, and a third collector 16. The first collector 14 is further connected to the input end of the power supply 20. The second collector 15 is further connected to the output end of the LLC resonant circuit 12. The third collector 15 is further connected to the output end of the phase-shifted full-bridge circuit 13.

[0167] The first collector 14 can be used to collect the input voltage of the power supply 20 and send the input voltage to the controller 11.

[0168] The second collector 15 can be used to collect the output voltage of the LLC resonant circuit 12 and send the output voltage to the controller 11.

[0169] The third collector 16 can be used to collect the output voltage of the phase-shifted full-bridge circuit 13.

[0170] The controller 11 can be used to perform closed-loop control on the phase-shifted full-bridge circuit 13 according to the input voltage of the power supply 20 and the output voltage of the LLC resonant circuit 12, so that the output voltage of the power module 10 is constant under the condition that the input voltage of the power supply 20 fluctuates.

[0171] Next, in combination with Figure 9 , the control process of the controller 11 in the power module will be described in detail.

[0172] Figure 9 It is a schematic flowchart of a control method provided by an embodiment of the present application. This control method can be executed by a controller in a power module. Please refer to Figure 9 , this control method may include the following steps:

[0173] S901. Obtain the input voltage of the power supply.

[0174] As Figure 7 shown, the power module may be provided with a first collector 14, and the controller 11 can obtain the input voltage of the power supply through the first collector 14.

[0175] S902. Control the output voltage of the phase-shifted full-bridge circuit according to the input voltage of the power supply and the constant voltage of the load, so that the output voltage of the power module is constant.

[0176] It can be understood that the input voltage of the power supply may have the following three situations: the input voltage is equal to the rated input voltage, the input voltage is less than the rated input voltage, and the input voltage is greater than the rated input voltage. Next, the control processes of the controller in these three situations will be described in detail.

[0177] Situation 1: The input voltage is equal to the rated input voltage.

[0178] If the input voltage is equal to the rated input voltage, it indicates that the power supply module 10 can operate under the rated working voltage state. In this case, both the LLC resonant circuit and the phase-shifted full-bridge circuit are in the normal working state, making the output voltages of the LLC resonant circuit and the phase-shifted full-bridge circuit stable, and the output voltage of the power supply module equal to the working voltage of the load, thereby ensuring the stability of the output voltage of the power supply module.

[0179] When the input voltage is equal to the rated input voltage, the controller can control the LLC resonant circuit and the phase-shifted full-bridge circuit in the following manner:

[0180] (1) Output a first control signal to the LLC resonant circuit to control the LLC resonant circuit to output a first voltage through the first control signal.

[0181] The first control signal may include the PWM control signals of each switching tube in the LLC resonant circuit, and the controller can output corresponding PWM control signals to each switching tube in the LLC resonant circuit.

[0182] The first control signal can be used to control the LLC resonant circuit to operate in the resonant state. It can be understood that by controlling the LLC resonant circuit to be in the resonant state, the reactive power of the LLC circuit can be reduced and the loss can be lowered; in addition, by controlling the phases of the PWM signals for the four switching tubes Q1-Q4 included in the first control signal, soft switching of the LLC circuit can be achieved, further reducing the switching loss to ensure the highest conversion efficiency of the LLC resonant circuit.

[0183] Optionally, the controller can generate the first control signal by setting parameters in the internal code, so that the frequency of the first control signal is equal to the resonant frequency of the LLC resonant circuit, and the first control signal is a PWM signal (square wave signal). In this way, by controlling the conduction or cutoff of each switching tube in the LLC resonant circuit 12 through the first control signal, the LLC resonant circuit 12 operates at the resonant frequency. It should be noted that this frequency modulation method can be a method of making the LLC resonant circuit operate in the resonant state by arbitrarily setting the frequency of the LLC resonant circuit, and the embodiments of the present application do not limit the frequency modulation method.

[0184] In the embodiments of the present application, since the LLC resonant circuit adopts open-loop control, after the circuit design and construction are completed, regardless of how the power supply (the magnitude of direct current) or the load changes, the duty cycle and frequency of the first control signal will not change. Since the frequency of the first control signal is equal to the LLC resonant frequency, therefore, the LLC resonant circuit will always operate in the resonant state, and the magnitude of the output voltage of the LLC resonant circuit is positively correlated with the magnitude of the input voltage.

[0185] (2) Determine the second voltage based on the first voltage and the constant voltage of the load.

[0186] To ensure that the output voltage provided by the power supply module to the load is the constant voltage of the load, the second voltage can be the difference between the constant voltage of the load and the first voltage, that is, the second voltage = the constant voltage of the load - the first voltage.

[0187] Reference Figure 8 As shown, the power supply module can be provided with a second collector 15, and the controller 11 can obtain the first voltage actually output at the output end of the LLC resonant circuit 12 through the second collector 15, so that the controller can timely adjust the second voltage based on the first voltage actually output by the LLC resonant circuit 12 and the constant voltage of the load.

[0188] (3) Determine the second control signal according to the second voltage, and output the second control signal to the phase-shifted full-bridge circuit to control the phase-shifted full-bridge circuit to output the second voltage through the second control signal.

[0189] The duty cycle of the second control signal is a preset duty cycle. The second control signal can include the PWM control signals of each switching tube in the phase-shifted full-bridge circuit, and the controller can output the corresponding PWM control signals to each switching tube in the phase-shifted full-bridge circuit.

[0190] In some embodiments, the preset duty cycle can be determined by the designer through experiments. Exemplarily, after the power supply module is assembled, under the rated input voltage, the designer can obtain the first voltage output by the LLC resonant circuit at the highest conversion efficiency through the second collector 15, and determine the second voltage based on the constant voltage of the load and the first voltage. The output voltage Vo of the phase-shifted full-bridge circuit = n × D × Vi, where n is the turns ratio of the second transformer, D is the duty cycle of the second control signal, Vi is the input voltage, and Vo is the output voltage. When n is a fixed value, the duty cycle corresponding to the phase-shifted full-bridge circuit under the rated input voltage can be calculated based on the second voltage and the constant voltage of the load, and this duty cycle can be determined as the preset duty cycle. For example, the preset duty cycle can be between 0 and 50%.

[0191] When the input voltage is the rated voltage, assuming that the output voltage of the LLC resonant circuit is the same as that of the phase-shifted full-bridge circuit, that is, the load shared by the LLC resonant circuit is the same as the load shared by the phase-shifted full-bridge circuit, the operating frequency (e.g., 70K - 300K) of each switching tube in the LLC resonant circuit can be adjusted by the controller in the power supply module to be equal to the resonant frequency of the LLC resonant circuit, enabling the LLC resonant circuit to operate in the resonant state, thereby reducing the reactive power of the LLC circuit and the losses of the LLC circuit. In addition, by controlling the phases of the PWM signals for the four switching tubes Q1 - Q4 included in the first control signal, soft switching of the LLC circuit can be achieved, further reducing the switching losses to ensure the highest conversion efficiency of the LLC resonant circuit. For example, the conversion efficiency of the LLC resonant circuit > 99%. The controller 11 is also used to adjust the phase of the second control signal to make the phase-shifted full-bridge circuit operate in the soft-switching state. Specifically, the controller 11 can adjust the phase of the PWM signal sent by the controller to the phase-shifted full-bridge circuit to adjust the phase difference between the control signals of each switching tube in the phase-shifted full-bridge circuit (e.g., making Figure 6 the phase difference between the control signals of the switching tubes Q6 and Q7 and the switching tubes Q5 and Q8 in Figure 6 be 100°), enabling each switching tube in the phase-shifted full-bridge circuit to turn on and off under soft-switching conditions, and achieving control of the phase-shifted full-bridge circuit to operate at the optimal conversion efficiency. For example, the optimal conversion efficiency of the phase-shifted full-bridge circuit > 99%.

[0192] Referring to Figure 8 As shown, the power supply module can be provided with a second collector 15. The controller 11 can collect the first voltage actually output by the LLC resonant circuit through the second collector 15, calculate the difference between the first voltage (the actual output voltage of the LLC resonant circuit 12) and the constant voltage of the load, and adjust the voltage actually output by the phase-shifted full-bridge circuit 13 to ensure that the overall output voltage of the power supply module is still the constant voltage of the load, which is beneficial to ensuring the power supply stability of the power supply module. Specifically, assuming that the difference between the constant voltage of the load and the first voltage is V r , according to the input-output voltage formula of the phase-shifted full-bridge circuit, the duty cycle of the phase-shifted full-bridge circuit is: This duty cycle is the preset duty cycle corresponding to the phase-shifted full-bridge circuit when the input voltage is equal to the rated input voltage, where n is the turns ratio of the primary and secondary sides of the second transformer.

[0193] In the power module provided by the embodiment of the present application, when the input voltage is equal to the rated input voltage, the controller can make the LLC resonant circuit operate in the resonant state with the minimum loss and the maximum output power by controlling the frequency of the first control signal to be equal to the resonant frequency of the LLC resonant circuit, and operate at the best conversion efficiency; and adjust the duty cycle of the second control signal to a preset duty cycle through the first voltage, so that the output voltage of the phase-shifted full-bridge circuit is the second voltage, thereby enabling the total output voltage of the power module to be constant and still equal to the constant voltage of the load. In this process, the controller adaptively adjusts the output voltage of the phase-shifted full-bridge circuit through the first voltage output by the LLC resonant circuit, so that the overall output voltage of the power module is still the constant voltage of the load, which is beneficial to ensuring the power supply stability of the power module. The controller can also adjust the phases of the control signals corresponding to each switching tube in the second control signal to adjust the phase difference between the control signals of each switching tube, so that each switching tube in the phase-shifted full-bridge circuit turns on and off under soft-switching conditions, reducing the switching loss, and realizing the operation of the phase-shifted full-bridge circuit at the best conversion efficiency, so that the overall power module has a high conversion efficiency.

[0194] Case 2: The input voltage is less than the rated input voltage.

[0195] If the input voltage is less than the rated input voltage, it means that the power module 10 is not operating at the rated working voltage state. In this case, since the LLC resonant circuit adopts an open-loop control method, the output voltage of the LLC resonant circuit will decrease as the input voltage decreases, resulting in a decrease in the voltage provided by the LLC resonant circuit for the load. To ensure that the overall power module provides a constant voltage for the load and avoid voltage undervoltage, the controller can increase the output voltage of the phase-shifted full-bridge circuit so that the sum of the output voltage of the LLC resonant circuit and the output voltage of the phase-shifted full-bridge circuit is still the constant voltage of the load.

[0196] When the input voltage is less than the rated input voltage, the controller can control the LLC resonant circuit and the phase-shifted full-bridge circuit in the following manner:

[0197] (1) Output a first control signal to the LLC resonant circuit to control the LLC resonant circuit to output a third voltage corresponding to the input voltage through the first control signal.

[0198] The first control signal can be used to control the LLC resonant circuit to operate in the resonant state.

[0199] It can be understood that when the input voltage is lower than the rated input voltage, the controller 11 can make the LLC resonant circuit 12 still operate at the resonant frequency and in the soft-switching mode by means of the phases of the PWM signals for the four switching transistors Q1 - Q4 included in the first control signal, so that each switching transistor in the first switching circuit of the LLC resonant circuit and each diode in the first rectifying circuit can still be turned on and off under soft-switching conditions, thereby ensuring that the LLC resonant circuit still has a high conversion efficiency when the input voltage decreases.

[0200] (2) Determine the fourth voltage according to the third voltage and the constant voltage of the load.

[0201] It can be understood that in order to ensure that the output voltage provided by the power supply module to the load is the constant voltage of the load, the fourth voltage can be the difference between the constant voltage of the load and the third voltage, that is, the fourth voltage = the constant voltage of the load - the third voltage. It can be understood that the third voltage can be less than the first voltage, and the fourth voltage can be greater than the second voltage.

[0202] Reference Figure 8 As shown, the power supply module can be provided with a second collector 15, and the controller 11 can collect the third voltage actually output at the output end of the LLC resonant circuit 12 through the second collector 15, so as to accurately determine the fourth voltage that the phase-shifted full-bridge circuit should output when the input voltage is less than the rated input voltage based on the constant voltage of the load and the third voltage actually output by the LLC resonant circuit 12.

[0203] (3) Determine the second control signal according to the fourth voltage, and output the second control signal to the phase-shifted full-bridge circuit to control the phase-shifted full-bridge circuit to output the fourth voltage through the second control signal.

[0204] The duty cycle corresponding to the second control signal is greater than the preset duty cycle. The second control signal can include the PWM control signals of the respective switching transistors in the phase-shifted full-bridge circuit, and the controller can output the corresponding PWM control signals to the respective switching transistors in the phase-shifted full-bridge circuit.

[0205] It can be understood that when the output voltage of the LLC resonant circuit decreases, it is necessary to increase the output voltage of the phase-shifted full-bridge circuit to ensure that the output voltage of the power supply module remains unchanged. The output voltage Vo of the phase-shifted full-bridge circuit = n×D×Vi, where n is the turns ratio of the second transformer, D is the duty cycle, Vi is the input voltage, and Vo is the output voltage. In the embodiments of the present application, n is a fixed value. When Vi decreases, the controller 11 can increase the output voltage Vo of the phase-shifted full-bridge circuit 13 by increasing the duty cycle D in the phase-shifted full-bridge circuit 13.

[0206] There is a conduction phase difference (0° to 180°) between two diagonal switching transistors in the phase-shifted full-bridge circuit. For example, Figure 6 in the phase-shifted full-bridge circuit shown, there is a conduction phase difference between switching transistor Q5 and switching transistor Q8, and there is also a conduction phase difference between switching transistor Q7 and switching transistor Q6. In some embodiments, the controller may adopt a pulse width modulation (PWM) control method to increase the output voltage by increasing the duty cycle of the second control signal of the phase-shifted full-bridge circuit.

[0207] The controller can use the second control signal to control the phases of two diagonal switching transistors in the phase-shifted full-bridge circuit, so as to adjust the phase difference between the two diagonal switching transistors in the phase-shifted full-bridge circuit, and further enable each switching transistor in the phase-shifted full-bridge circuit to turn on and off under soft-switching conditions, so as to ensure that the four switching transistors in the phase-shifted full-bridge circuit can still achieve zero-voltage turn-on when the input voltage decreases, reduce the switching transistor loss, and is beneficial to improving the conversion efficiency and reliability of the phase-shifted full-bridge circuit.

[0208] Refer to Figure 8 as shown, the power supply module may be provided with a third collector 16. The controller 11 can collect the actual fourth voltage output from the output end of the phase-shifted full-bridge circuit 13 through the third collector 16, and compare the actual fourth voltage with the fourth voltage calculated based on the third voltage and the constant voltage of the load, and adjust the duty cycle of the second control signal to ensure that the overall output voltage of the power supply module is still the constant voltage of the load when the input voltage decreases, which is beneficial to ensuring the power supply stability of the power supply module.

[0209] Specifically, since the input voltage Vi drops at this time, then when the duty cycle of the first control signal of the LLC resonant circuit and the turns ratio of the primary and secondary sides of the first transformer remain unchanged, the third voltage actually output by the LLC resonant circuit must be less than the first voltage it output before. Assume that the difference between the constant voltage of the load and the third voltage is V r . At this time, because the input voltage decreases, therefore, both the third voltage actually output by the LLC resonant circuit 12 and the fourth voltage actually output by the phase-shifted full-bridge circuit decrease. In this case, it is necessary to increase the duty cycle of the second control signal of the phase-shifted full-bridge circuit 13 to increase the output voltage of the phase-shifted full-bridge circuit 13, so as to compensate for the part of the output voltage attenuation of the LLC resonant circuit 12.

[0210] In the power supply module provided by the embodiment of the present application, when the input voltage is lower than the rated input voltage, the controller can make the LLC resonant circuit operate in the resonant state with the minimum loss and the maximum output power by controlling the frequency of the first control signal to be equal to the resonant frequency of the LLC resonant circuit, and operate at the best conversion efficiency; and, by increasing the duty cycle of the second control signal to increase the fourth voltage, so that even when the third voltage decreases, the total output voltage can still be kept constant and still be equal to the constant voltage of the load. By adjusting the phase of the second control signal and the phase difference between the control signals of each switching tube, the switching tubes in the phase-shifted full-bridge circuit can be turned on and off under the soft-switching condition, reducing the switching loss, and making the phase-shifted full-bridge circuit operate at the best conversion efficiency, so that the overall power supply module has a high conversion efficiency.

[0211] Case 3: The input voltage is greater than the rated input voltage.

[0212] If the input voltage is greater than the rated input voltage, it means that the power supply module 10 is not operating at the rated working voltage. In this case, since the LLC resonant circuit adopts an open-loop control method, the output voltage of the LLC resonant circuit will increase as the input voltage increases, resulting in an increase in the voltage provided by the LLC resonant circuit for the load. To ensure that the overall power supply module still provides a constant voltage for the load and avoid voltage overload, the controller can reduce the output voltage of the phase-shifted full-bridge circuit so that the sum of the output voltage of the LLC resonant circuit and the output voltage of the phase-shifted full-bridge circuit is the constant voltage of the load.

[0213] When the input voltage is greater than the rated input voltage, the controller can control the LLC resonant circuit and the phase-shifted full-bridge circuit in the following manner:

[0214] (1) Output a first control signal to the LLC resonant circuit to control the LLC resonant circuit to output a third voltage corresponding to the input voltage through the first control signal.

[0215] The first control signal can be used to control the LLC resonant circuit to operate in the resonant state.

[0216] It can be understood that when the input voltage increases compared to the rated input voltage, the controller 11 can make the LLC resonant circuit 12 still operate in the soft-switching mode through the phases of the PWM signals for the four switching tubes Q1-Q4 included in the first control signal, so that each switching tube in the first switching circuit of the LLC resonant circuit and each diode in the first rectifying circuit can still be turned on and off under the soft-switching condition, ensuring that the LLC resonant circuit still has a high conversion efficiency when the input voltage increases.

[0217] (2) Determine the fourth voltage based on the third voltage and the constant voltage of the load.

[0218] It can be understood that the fourth voltage can be the difference between the constant voltage of the load and the third voltage, that is, the fourth voltage = the constant voltage of the load - the third voltage.

[0219] Different from the case where the input voltage is less than the rated input voltage, when the input voltage is greater than the rated input voltage, the third voltage can be greater than the first voltage, and the fourth voltage can be less than the second voltage.

[0220] Reference Figure 8 As shown, the power supply module can be provided with a second collector 15, and the controller 11 can collect the third voltage actually output at the output end of the LLC resonant circuit 12 through the second collector 15, so as to accurately determine the fourth voltage that the phase-shifted full-bridge circuit should output when the input voltage is greater than the rated input voltage based on the constant voltage of the load and the third voltage.

[0221] (3) Determine the second control signal according to the fourth voltage, and output the second control signal to the phase-shifted full-bridge circuit to control the phase-shifted full-bridge circuit to output the fourth voltage through the second control signal.

[0222] The duty cycle corresponding to the second control signal is less than the preset duty cycle. The second control signal can include the PWM control signals of each switching tube in the phase-shifted full-bridge circuit, and the controller can output the corresponding PWM signals to each switching tube in the phase-shifted full-bridge circuit.

[0223] It can be understood that when the output voltage of the LLC resonant circuit increases, it is necessary to reduce the output voltage of the phase-shifted full-bridge circuit to ensure that the output voltage of the power supply module remains unchanged. In some embodiments, the output voltage of the phase-shifted full-bridge circuit is positively correlated with the input voltage and the duty cycle. When the input voltage increases, the controller can reduce the output voltage of the phase-shifted full-bridge circuit by reducing the duty cycle of the phase-shifted full-bridge circuit.

[0224] In some embodiments, the controller can adopt the PWM control method to reduce the output voltage by reducing the duty cycle of the second control signal in the phase-shifted full-bridge circuit. The controller can adjust the phases of the PWM signals corresponding to the two diagonal switching tubes in the phase-shifted full-bridge circuit, so that each switching tube in the phase-shifted full-bridge circuit can still turn on and off under the soft-switching condition when the input voltage increases, reducing the switching tube loss, which is beneficial to improving the conversion efficiency and reliability of the phase-shifted full-bridge circuit.

[0225] Such as Figure 8As shown, the power supply module may be provided with a third collector 16. When the input voltage is greater than the rated input voltage, the controller 11 may collect the actual fourth voltage output from the output end of the phase-shifted full-bridge circuit 13 through the third collector 16, and compare the actual fourth voltage with the fourth voltage calculated based on the third voltage and the constant voltage of the load, and dynamically adjust the duty cycle of the second control signal to ensure that the overall output voltage of the power supply module is still the constant voltage of the load when the input voltage decreases, which is beneficial to ensuring the power supply stability of the power supply module.

[0226] Specifically, since the input voltage Vi increases at this time, then when the duty cycle of the first control signal of the LLC resonant circuit and the turns ratio of the primary and secondary sides of the first transformer remain unchanged, the third voltage actually output by the LLC resonant circuit must be greater than the first voltage output by it before. Assume that the difference between the constant voltage of the load and the third voltage is V r At this time, since the input voltage increases, therefore, both the third voltage actually output by the LLC resonant circuit 12 and the fourth voltage actually output by the phase-shifted full-bridge circuit increase. In this case, it is necessary to reduce the duty cycle of the second control signal of the phase-shifted full-bridge circuit 13 to make the output voltage of the phase-shifted full-bridge circuit 13 decrease, so as to offset the increased part of the output voltage of the resonant circuit 12.

[0227] In the power supply module provided by the embodiment of the present application, the controller can, when the input voltage is higher than the rated input voltage, make the frequency of the first control signal equal to the resonant frequency of the LLC resonant circuit, so that the LLC resonant circuit works in the resonant state, with the minimum loss and the maximum output power, and works at the best conversion efficiency; and, reduce the fourth voltage by reducing the duty cycle of the second signal, so that even when the third voltage increases, the total output voltage can still be kept constant, still equal to the constant voltage of the load, and by adjusting the phase of the second control signal, adjust the phase difference between the control signals of each switch tube in the phase-shifted full-bridge circuit, so that each switch tube in the phase-shifted full-bridge circuit turns on and off under the soft-switching condition, reduce the switching loss, and realize the operation of the phase-shifted full-bridge circuit at the best conversion efficiency, so that the overall power supply module has a high conversion efficiency.

[0228] In summary, see Figure 8, the input ends of the LLC resonant circuit 12 and the phase-shifted full-bridge circuit 13 are connected in parallel, and the output ends are connected in series to jointly supply power to the load 30. When the input voltage changes and fluctuates, it is still necessary to provide a stable output voltage for the load 30. In the embodiment of the present application, the LLC resonant circuit is designed for open-loop control, which means that the duty cycle of each switching tube in the LLC resonant circuit is a fixed value and will not change. Then, when the input voltage changes, in order to keep the voltage of the load constant, assume that: the input voltage of the power supply is Vi, the output voltage of the LLC resonant circuit 12 is V1, and the constant voltage of the load is Vo. Then, the duty cycle of the phase-shifted full-bridge circuit 13 where n is the turns ratio of the primary winding and the secondary winding of the second transformer, which is a fixed value. For the change situation of the input voltage Vi:

[0229] Situation 1: When the input voltage Vi is the rated input voltage, D is the preset duty cycle;

[0230] Situation 2: When the input voltage Vi is less than the rated input voltage, since the Vi of the input voltage decreases and V1 decreases accordingly, the duty cycle D needs to be increased to ensure that Vo remains unchanged;

[0231] Situation 3: When the input voltage Vi is greater than the rated input voltage, since the Vi of the input voltage increases and V1 increases accordingly, the duty cycle needs to be decreased to ensure that Vo remains unchanged;

[0232] When controlling the phase-shifted full-bridge circuit, the constant voltage of the load is a fixed value. It is known that the actual output voltage V1 of the LLC resonant circuit 12 can be collected by the second collector 15, and this voltage value V1 is fed back to the controller 11. The controller 11 is based on the formula Calculate the duty cycle that needs to be adjusted at this time, adjust the parameters in the internal code, adjust the duty cycle of the second control signal, and output the second control signal that meets the voltage constant demand of the load, so as to realize the adjustment of the output voltage of the phase-shifted full-bridge circuit, to compensate or offset the decreased output voltage or increased output voltage of the LLC resonant circuit, so as to realize the constancy of the output voltage of the power supply module.

[0233] In addition, in the embodiments of the present application, since the switching tubes of the LLC resonant circuit operate at the resonant frequency, the reactive power of the circuit can be minimized, the output loss can be minimized, and by adjusting the phase of the control signal of the switching tubes, the four switching tubes (Q1-Q4) can operate in the soft-switching state, further reducing the loss of the circuit. When the input voltage changes, the output voltage V1 of the LLC resonant circuit increases or decreases following the input voltage. The closed-loop control of the phase-shifted full-bridge circuit can adjust the output voltage V2 by adjusting the duty cycle of the control signal of its own switching tubes (Q5-Q8). Moreover, the phase-shifted full-bridge circuit can also operate in the soft-switching state. Therefore, when the input voltage changes within a wide range, not only is the output voltage constant, but the loss of the entire circuit is also minimized, and the entire circuit operates at the optimal efficiency point.

[0234] In some other embodiments, when the input voltage changes, the constant output voltage of the power supply module can also be achieved by adjusting the turn ratio of the first transformer or the second transformer.

[0235] Figure 10 It is a schematic structural diagram of a computing device provided by an embodiment of the present application. Please refer to Figure 10 , the computing device may include a power supply module 10, and the power supply module 10 can be used to supply power to the computing device.

[0236] The computing device can be a server. From an architectural perspective, the server can be a rack server, a high-density server, a tower server, or a whole-cabinet server; from a functional perspective, the server can be a general-purpose server or an artificial intelligence server (AI (artificial intelligence) server), etc. Exemplarily, the artificial intelligence server can be an image processing server (GPU (graphics processing unit) server).

[0237] It should be noted that the detailed structure and beneficial effects of the power supply module 10 can refer to the detailed structure and beneficial effects of the power supply module 10 shown in the above embodiments, and will not be elaborated here.

[0238] An embodiment of the present application provides a computer-readable storage medium, on which computer-executable instructions are stored; when the computer-executable instructions are executed by a processor, they are used to implement the control method as described in the above embodiments.

[0239] An embodiment of the present application provides a computer program product, the computer program product includes a computer program, and when the computer program is executed by a processor, it causes the computer to execute the control method as described in the above embodiments.

[0240] Embodiments of the present application are described with reference to the flowcharts and / or block diagrams of methods, apparatuses (systems), and computer program products according to embodiments of the present application. It should be understood that each process and / or block in the flowchart and / or block diagram, and the combination of processes and / or blocks in the flowchart and / or block diagram, can be implemented by computer program instructions. These computer program instructions can be provided to the processing unit of a general-purpose computer, a special-purpose computer, an embedded processor, or other programmable devices to generate a machine, so that the instructions executed by the processing unit of the computer or other programmable devices generate means for implementing the functions specified in one process Figure 1 one process or multiple processes and / or blocks Figure 1 or means for implementing the functions specified in multiple blocks.

[0241] These computer program instructions can also be stored in a computer-readable memory that can direct a computer or other programmable devices to work in a specific manner, so that the instructions stored in the computer-readable memory generate a manufactured article including instruction means, and the instruction means implement the functions specified in one process Figure 1 one process or multiple processes and / or blocks Figure 1 or means for implementing the functions specified in multiple blocks.

[0242] These computer program instructions can also be loaded onto a computer or other programmable devices, so that a series of operation steps are executed on the computer or other programmable devices to generate a computer-implemented process, and thus the instructions executed on the computer or other programmable devices provide steps for implementing the functions specified in one process Figure 1 one process or multiple processes and / or blocks Figure 1 or means for implementing the functions specified in multiple blocks.

[0243] Finally, it should be noted that the above embodiments are only used to illustrate the technical solutions of the embodiments of the present application, and are not intended to limit them; although the embodiments of the present application have been described in detail with reference to the foregoing embodiments, those of ordinary skill in the art should understand that they can still modify the technical solutions recorded in the foregoing embodiments, or perform equivalent replacements on some or all of the technical features; and these modifications or replacements do not cause the essence of the corresponding technical solutions to deviate from the scope of the technical solutions of the embodiments of the present application.

Claims

1. A power supply module, characterized in that, Comprising: A controller, an LLC resonant circuit, and a phase-shifted full-bridge circuit, where The controller is respectively connected to the LLC resonant circuit and the phase-shifted full-bridge circuit. The input ends of the LLC resonant circuit and the phase-shifted full-bridge circuit are connected in parallel and connected to a power supply. The output end of the LLC resonant circuit and the output end of the phase-shifted full-bridge circuit are connected in series and connected to a load; The controller is configured to, when the input voltage of the power supply changes, control the output voltage of the phase-shifted full-bridge circuit according to the input voltage of the power supply and the constant voltage of the load, so that the output voltage of the power module is constant.

2. The power supply module according to claim 1, wherein The LLC resonant circuit includes a first switch circuit, a resonant cavity, a first transformer, and a first rectifier circuit, where The first switch circuit is respectively connected to the controller and the resonant cavity, and the first switch circuit is also connected to the power supply; The primary side of the first transformer is connected to the resonant cavity; The first end of the first rectifier circuit is connected to the secondary side of the first transformer, and the second end of the first rectifier circuit is connected to the load.

3. The power module according to claim 2, wherein The resonant cavity includes: a resonant inductor, an exciting inductor, and a resonant capacitor, where The first end of the resonant capacitor is connected to the first switch circuit, and the second end of the resonant capacitor is connected to the first end of the resonant inductor; The second end of the resonant inductor is respectively connected to the first end of the exciting inductor and the first end of the primary side of the first transformer; The second end of the exciting inductor is respectively connected to the second end of the primary side of the first transformer and the first switch circuit.

4. The power supply module according to claim 3, wherein The first rectifier circuit includes a first diode, a second diode, and a first filter capacitor, where The anode of the first diode is connected to the first end of the secondary side of the first transformer, and the cathode of the first diode is respectively connected to the first end of the first filter capacitor and the first end of the load; The anode of the second diode is connected to the second end of the secondary side of the first transformer, and the cathode of the second diode is respectively connected to the cathode of the first diode and the first end of the first filter capacitor; The second end of the first filter capacitor is respectively connected to the second end of the load and the third end of the secondary side of the first transformer.

5. The power supply module according to any one of claims 1-4, characterized in that, The phase-shifted full-bridge circuit includes a second switch circuit, a first inductor, a second transformer, and a second rectifier circuit, where The second switch circuit is respectively connected to the controller, the first end of the first inductor, and the second end of the primary side of the second transformer, and the second switch circuit is also connected to the power supply; The second end of the first inductor is also connected to the first end of the primary side of the second transformer; The input end of the second rectifier circuit is connected to the secondary side of the second transformer, and the output end of the second rectifier circuit is also connected to the load.

6. The power module according to claim 5, characterized in that The second rectifier circuit includes a third diode, a fourth diode, a second inductor, and a second filter capacitor, where The anode of the third diode is connected to the first end of the secondary side of the second transformer, and the cathode of the third diode is connected to the first end of the second inductor; The anode of the fourth diode is connected to the second end of the secondary side of the second transformer, and the cathode of the fourth diode is respectively connected to the cathode of the third diode and the first end of the second inductor; The second end of the second inductor is respectively connected to the first end of the second filter capacitor and the first end of the load; The second end of the second filter capacitor is respectively connected to the third end of the secondary side of the second transformer and the second end of the load.

7. The power supply module according to any one of claims 1-6, characterized in that, The controller is specifically configured to: When the input voltage is equal to the rated input voltage, output a first control signal to the LLC resonant circuit to control the LLC resonant circuit to output a first voltage through the first control signal, and the first control signal is used to control the LLC resonant circuit to operate in a resonant state; Determine a second voltage according to the first voltage and the constant voltage of the load; Determine a second control signal according to the second voltage, and output the second control signal to the phase-shifted full-bridge circuit to control the phase-shifted full-bridge circuit to output the second voltage through the second control signal, and the duty cycle of the second control signal is a preset duty cycle.

8. The power supply module according to any one of claims 1-6, characterized in that, The controller is specifically configured to: When the input voltage is less than or greater than the rated input voltage, output a first control signal to the LLC resonant circuit to control the LLC resonant circuit to output a third voltage corresponding to the input voltage through the first control signal, and the first control signal is used to control the LLC resonant circuit to operate in a resonant state; Determine a fourth voltage according to the third voltage and the constant voltage of the load; Determine a second control signal according to the fourth voltage, and output the second control signal to the phase-shifted full-bridge circuit to control the phase-shifted full-bridge circuit to output the fourth voltage through the second control signal; When the input voltage is less than the rated input voltage, the duty cycle of the second control signal is greater than the preset duty cycle; When the input voltage is greater than the rated input voltage, the duty cycle of the second control signal is less than the preset duty cycle.

9. The power supply module according to claim 7 or 8, characterized in that The controller is further configured to: Adjust the phase of the second control signal to make the phase-shifted full-bridge circuit operate in a soft-switching state.

10. A computing device, characterized in that, It includes the power supply module according to any one of claims 1-9.

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