Adjustable-ratio voltage converter, power supply chip, and electronic device

Abstract

The present disclosure provides a variable-ratio voltage converter, a power supply chip and an electronic device, comprising a switched-capacitor conversion circuit and a buck-boost conversion circuit. When working in a voltage regulation mode, the switched-capacitor conversion circuit boosts a first output voltage to obtain a voltage doubler of the first output voltage, and the buck-boost conversion circuit converts an input voltage into the first output voltage based on the voltage doubler of the first output voltage, which is related to both a charging time of the switched-capacitor conversion circuit and a charging time of the buck-boost conversion circuit, to achieve large-ratio voltage regulation. In addition, the switched-capacitor conversion circuit contributes to the variable-ratio voltage converter, which can reduce the variable ratio of the buck-boost conversion circuit, i.e. reduce the charging current of the buck-boost conversion circuit, to improve the efficiency, thereby achieving high-efficiency large-ratio voltage regulation.

Description

Technical Field

[0001] Embodiments of this disclosure relate to the field of integrated circuit technology, and more particularly to adjustable ratio voltage converters, power supply chips, and electronic devices. Background Technology

[0002] Switched-capacitor converters and buck-boost converters are two common types of DC-DC voltage converters. Switched-capacitor converters utilize the energy stored in capacitors for DC-DC voltage conversion. For example, a 2:1 turnaround switched-capacitor converter includes a flying capacitor and multiple switching transistors. By controlling the on / off state of these transistors, the energy stored in the flying capacitor is used to achieve a 2:1 step-down ratio. Buck-boost converters utilize the energy stored in inductors for DC-DC voltage conversion. For example, a two-level buck-boost converter includes an inductor and multiple switching transistors. By controlling the on / off state of these transistors, the energy stored in the inductor is used to achieve step-up / step-down conversion.

[0003] With the rapid development of fast charging services for mobile devices, higher requirements have been placed on the efficiency and voltage ratio of voltage converters. However, the existing buck-boost conversion circuits have low efficiency when adjusting voltage ratios, and the existing switched capacitor conversion circuits cannot achieve voltage regulation, resulting in the inability to balance large-ratio voltage regulation and high efficiency. Summary of the Invention

[0004] This disclosure provides an adjustable ratio voltage converter, power chip, and electronic device that can achieve high-efficiency, high-ratio voltage regulation.

[0005] In a first aspect, this disclosure provides an adjustable ratio voltage converter, including a buck-boost conversion circuit and a switched capacitor conversion circuit. The input terminal of the switched capacitor conversion circuit and the input terminal of the buck-boost conversion circuit are connected to a voltage input terminal. The input and output terminals of the switched capacitor conversion circuit are connected to the input and output terminals of the buck-boost conversion circuit. The output terminal of the switched capacitor conversion circuit 110 is connected to a voltage output terminal.

[0006] The switched capacitor conversion circuit is configured to boost the first output voltage of the adjustable ratio voltage converter when the adjustable ratio voltage converter is operating in voltage regulation mode, thereby obtaining a voltage multiplier of the first output voltage.

[0007] The buck-boost conversion circuit is configured to convert the input voltage of the adjustable ratio voltage converter into the first output voltage based on a voltage multiplier of the first output voltage when the adjustable ratio voltage converter is operating in voltage regulation mode. The first output voltage is related to both the charging time of the switched capacitor conversion circuit and the magnetization time of the buck-boost conversion circuit.

[0008] In some embodiments of this disclosure, the switched capacitor conversion circuit includes a flying capacitor, and the switched capacitor conversion circuit is further configured to control the flying capacitor to charge and discharge when the adjustable ratio voltage converter is operating in the voltage regulation mode, so as to obtain twice the voltage of the first output voltage.

[0009] The buck-boost conversion circuit includes an inductor, and is further configured to, when the adjustable ratio voltage converter operates in the voltage regulation mode, receive twice the voltage of the first output voltage based on the inductor, and control the inductor to charge and demagnetize, so as to step down the input voltage to obtain the first output voltage.

[0010] In some embodiments of this disclosure, when the adjustable ratio voltage converter operates in the first voltage regulation mode, during the switching cycle of the adjustable ratio voltage converter, the adjustable ratio voltage converter sequentially switches between the first charging demagnetization state, the charging and magnetizing state, and the discharging and demagnetizing state.

[0011] In the first charging demagnetizing state, the flying capacitor is connected between the voltage output terminal and ground so that the switched capacitor conversion circuit operates in the charging phase, and both ends of the inductor are connected to ground so that the buck-boost conversion circuit operates in the first demagnetizing phase.

[0012] In the charging and magnetizing state, the inductor and the flying capacitor are connected in parallel between the voltage output terminal and ground, so that the switched capacitor conversion circuit operates in the charging phase and the buck-boost conversion circuit operates in the magnetizing phase.

[0013] In the discharge demagnetization state, the inductor and the flying capacitor are connected in series between the voltage input terminal and the voltage output terminal, so that the switched capacitor conversion circuit operates in the discharge phase and the buck-boost conversion circuit operates in the second demagnetization phase.

[0014] In some embodiments of this disclosure, the first output voltage is equal to the input voltage and (1-D) / [2-(2-d)]. The product of D], where D is the proportion of the charging time in the switching cycle, and d is the proportion of the magnetization time in the charging time.

[0015] In some embodiments of this disclosure, when the adjustable ratio voltage converter operates in the second voltage regulation mode, during the switching cycle of the adjustable ratio voltage converter, the adjustable ratio voltage converter sequentially switches between a charging and magnetizing state, a discharging and magnetizing state, and a discharging and demagnetizing state.

[0016] In the charging and magnetizing state, the inductor and the flying capacitor are connected in parallel between the voltage output terminal and ground, so that the switched capacitor conversion circuit operates in the charging phase and the buck-boost conversion circuit operates in the magnetizing phase.

[0017] In the discharge and magnetization state, the inductor and the flying capacitor are connected in series between the voltage output terminal and ground, so that the switched capacitor conversion circuit operates in the discharge phase and the buck-boost conversion circuit operates in the magnetization phase.

[0018] In the discharge demagnetization state, the inductor and the flying capacitor are connected in series between the voltage input terminal and the voltage output terminal, so that the switched capacitor conversion circuit operates in the discharge phase and the buck-boost conversion circuit operates in the second demagnetization phase.

[0019] In some embodiments of this disclosure, the first output voltage is equal to the input voltage and [(1-D)]. The product of (1-d) / (2-D), where D is the proportion of the charging time in the switching cycle and d is the proportion of the magnetization time in the discharge time of the flying capacitor.

[0020] In some embodiments of this disclosure, when the adjustable ratio voltage converter operates in the third voltage regulation mode, during the switching cycle of the adjustable ratio voltage converter, the adjustable ratio voltage converter sequentially switches between the second charging demagnetization state, the charging and magnetizing state, and the discharging and demagnetizing state.

[0021] In the second charging demagnetizing state, the inductor is connected between the voltage input terminal and ground, and the flying capacitor is connected between the voltage output terminal and ground, so that the switched capacitor conversion circuit operates in the charging phase and the buck-boost conversion circuit operates in the third demagnetizing phase.

[0022] In the charging and magnetizing state, the inductor and the flying capacitor are connected in parallel between the voltage output terminal and ground, so that the switched capacitor conversion circuit operates in the charging phase and the buck-boost conversion circuit operates in the magnetizing phase.

[0023] In the discharge demagnetization state, the inductor and the flying capacitor are connected in series between the voltage input terminal and the voltage output terminal, so that the switched capacitor conversion circuit operates in the discharge phase and the buck-boost conversion circuit operates in the second demagnetization phase.

[0024] In some embodiments of this disclosure, the first output voltage is equal to the input voltage and (1-D) d) / [2-(2-d) The product of D], where D is the proportion of the charging time in the switching cycle, and d is the proportion of the magnetization time in the charging time.

[0025] In some embodiments of this disclosure, the switched capacitor conversion circuit further includes a first transistor, a second transistor, a third transistor, and a fourth transistor. The first transistor, the second transistor, the third transistor, and the fourth transistor are connected in series between the voltage input terminal and ground. The upper plate of the flying capacitor is connected to the connection point of the first transistor and the second transistor, the lower plate of the flying capacitor is connected to the connection point of the third transistor and the fourth transistor, and the voltage output terminal is connected to the connection point of the second transistor and the third transistor.

[0026] During the charging phase, the second transistor and the fourth transistor are turned on, while the first transistor and the third transistor are turned off; during the discharging phase, the third transistor is turned on, while the first transistor, the second transistor, and the fourth transistor are turned off.

[0027] In some embodiments of this disclosure, the buck-boost conversion circuit further includes a fifth transistor, a sixth transistor, a seventh transistor, and an eighth transistor. The first end of the inductor is connected to the voltage input terminal through the fifth transistor, and the first end of the inductor is also grounded through the sixth transistor. The second end of the inductor is connected to the upper plate of the flying capacitor through the seventh transistor, and the second end of the inductor is also connected to the lower plate of the flying capacitor through the eighth transistor.

[0028] Specifically, during the magnetization phase, the sixth and seventh transistors are turned on, while the fifth and eighth transistors are turned off; during the first demagnetization phase, the sixth and eighth transistors are turned on, while the fifth and seventh transistors are turned off; during the second demagnetization phase, the fifth and seventh transistors are turned on, while the sixth and eighth transistors are turned off; and during the third demagnetization phase, the fifth and eighth transistors are turned on while the sixth and seventh transistors are turned off.

[0029] In some embodiments of this disclosure, the buck-boost conversion circuit is further configured to convert the input voltage into a second output voltage of the adjustable ratio voltage converter when the adjustable ratio voltage converter is operating in buck-boost mode, wherein the second output voltage is related to the magnetization time of the inductor.

[0030] The switched capacitor conversion circuit is further configured to stabilize the second output voltage based on the flying capacitor when the adjustable ratio voltage converter operates in the buck-boost mode.

[0031] In some embodiments of this disclosure, the switched capacitor conversion circuit is further configured to reduce the input voltage to half of the input voltage when the adjustable ratio voltage converter is operating in a fixed voltage mode, so as to obtain a third output voltage of the adjustable ratio voltage converter.

[0032] In a second aspect, this disclosure provides a power supply chip, including a voltage input terminal, a voltage output terminal, and at least one adjustable ratio voltage converter provided in the first aspect.

[0033] In some embodiments of this disclosure, the power supply chip includes a first adjustable voltage converter and a second adjustable voltage converter, which are connected in parallel between the voltage input terminal and the voltage output terminal. The first and second adjustable voltage converters operate in the same mode, and the on / off states of the transistors at the same location in the first and second adjustable voltage converters are the same or opposite.

[0034] Thirdly, this disclosure provides an electronic device including the power chip provided in the second aspect.

[0035] The present disclosure provides an adjustable ratio voltage converter, including a switched capacitor conversion circuit and a buck-boost conversion circuit. When the adjustable ratio voltage converter operates in voltage regulation mode, the first output voltage of the adjustable ratio voltage converter is boosted by the switched capacitor conversion circuit to obtain a doubled first output voltage. Based on the doubled first output voltage, the buck-boost conversion circuit converts the input voltage of the adjustable ratio voltage converter into a first output voltage that is related to both the charging time of the switched capacitor conversion circuit and the magnetization time of the buck-boost conversion circuit, so as to realize the large ratio voltage regulation of the adjustable ratio voltage converter.

[0036] Furthermore, since the switched capacitor conversion circuit contributes to the turns ratio of the adjustable turns ratio voltage converter, it can reduce the turns ratio of the buck-boost conversion circuit, that is, reduce the charging current of the buck-boost conversion circuit, thereby improving the efficiency of the adjustable turns ratio voltage converter. Therefore, it is possible to achieve high-efficiency large turns ratio voltage regulation. Attached Figure Description

[0037] To more clearly illustrate the technical solutions of the embodiments of this application, the accompanying drawings used in the description of the embodiments will be briefly introduced below. It should be understood that the drawings described below only relate to some embodiments of this disclosure and are not intended to limit this disclosure, wherein: Figure 1 A circuit diagram of a buck-boost converter provided for the prior art.

[0038] Figure 2 A circuit diagram of a switched capacitor converter provided in the prior art.

[0039] Figure 3 This is a schematic diagram of an adjustable ratio voltage converter provided in an embodiment of the present disclosure.

[0040] Figure 4 This is a circuit diagram of an adjustable ratio voltage converter provided in an embodiment of the present disclosure.

[0041] Figure 5 for Figure 4 The diagram shows the equivalent circuit of the adjustable ratio voltage converter in the first charging demagnetization state.

[0042] Figure 6 for Figure 4 The diagram shows the equivalent circuit of the adjustable ratio voltage converter in the charging and magnetizing state.

[0043] Figure 7 for Figure 4 The diagram shows the equivalent circuit of the adjustable ratio voltage converter in the discharge demagnetization state.

[0044] Figure 8 for Figure 4 The diagram shows the equivalent circuit of the adjustable ratio voltage converter in the discharge and magnetization state.

[0045] Figure 9 for Figure 4 The diagram shows the equivalent circuit of the adjustable ratio voltage converter in the second charging demagnetization state.

[0046] Figures 10(a) and 10(b) are Figure 4 The diagram shows the equivalent circuit of the adjustable ratio voltage converter in buck-boost mode.

[0047] Figures 11(a) and 11(b) are Figure 4 The diagram shows the equivalent circuit of the adjustable ratio voltage converter in fixed voltage mode.

[0048] Figure 12 This is a schematic diagram of the structure of a power chip provided in an embodiment of this disclosure. Detailed Implementation

[0049] To make the objectives, technical solutions, and advantages of the embodiments of this disclosure clearer, the technical solutions of the embodiments of this disclosure will be clearly and completely described below with reference to the accompanying drawings. Obviously, the described embodiments are only some, not all, of the embodiments of this disclosure. All other embodiments obtained by those skilled in the art based on the described embodiments of this disclosure without creative effort are also within the scope of protection of this disclosure.

[0050] In this disclosure, the reference to "embodiment" means that a particular feature, structure, or characteristic described in connection with an embodiment may be included in at least one embodiment of this application. The appearance of the phrase "embodiment" in various places throughout the specification does not necessarily refer to the same embodiment, nor is it a mutually exclusive, independent, or alternative embodiment. It will be explicitly and implicitly understood by those skilled in the art that the embodiments described in this disclosure can be combined with other embodiments.

[0051] Furthermore, the terms "first," "second," etc., in the specification, claims, or the accompanying drawings are used to distinguish different objects rather than to describe a specific order, and may explicitly or implicitly include one or more of the features.

[0052] In the description of this disclosure, unless otherwise stated, "multiple" and "at least two" mean two or more (including two), and similarly, "multiple groups" and "at least two groups" mean two or more (including two groups).

[0053] To enable those skilled in the art to better understand the present application, the technical solutions in the embodiments of the present application will be clearly and completely described below with reference to the accompanying drawings.

[0054] Figure 1 A circuit diagram of a buck-boost converter provided for the prior art, such as... Figure 1 As shown, the buck-boost converter is a two-level buck-boost converter, specifically including a first switch Q1, a second switch Q2, an inductor L, an input capacitor CIN, and an output capacitor COUT. The connection point of the first switch Q1, the second switch Q2, and the inductor L is the switching node SW. The first switch Q1 is connected between the voltage input terminal IN and the switching node SW, the second switch Q2 is connected between the switching node SW and ground, the inductor L is connected between the switching node SW and the voltage output terminal OUT, the input capacitor CIN is connected between the voltage input terminal IN and ground, and the output capacitor COUT is connected between the voltage output terminal OUT and ground.

[0055] By controlling the switching on and off of the first switch Q1 and the second switch Q2, the inductor L is magnetized and demagnetized, thereby utilizing the energy stored in the inductor L to achieve voltage boosting and bucking. The turns ratio of the buck-boost converter is related to the magnetization time of the inductor L, so the voltage can be adjusted by regulating the magnetization time of the inductor L. However, when the buck-boost converter performs large turns ratio regulation, the charging current of the inductor L is large, resulting in greater losses in the buck-boost converter and thus affecting efficiency.

[0056] Figure 2 A circuit diagram of a switched-capacitor converter provided in the prior art, such as... Figure 2 As shown, the switched capacitor converter includes a third switch Q3, a fourth switch Q4, a fifth switch Q5, a sixth switch Q6, a flying capacitor Cfly, an input capacitor CIN, and an output capacitor COUT.

[0057] In this configuration, the third switch Q3, the fourth switch Q4, the fifth switch Q5, and the sixth switch Q6 are connected in series between the voltage input terminal IN and ground. The upper plate of the flying capacitor Cfly is connected to the connection point of the third switch Q3 and the fourth switch Q4, and the lower plate of the flying capacitor Cfly is connected to the connection point of the fifth switch Q5 and the sixth switch Q6. The voltage output terminal OUT is connected to the connection point of the fourth switch Q4 and the fifth switch Q5. The input capacitor CIN is connected between the voltage input terminal IN and ground, and the output capacitor COUT is connected between the voltage output terminal OUT and ground.

[0058] In the first phase, the third switch Q3 and the fifth switch Q5 are turned on, while the fourth switch Q4 and the sixth switch Q6 are turned off. The flying capacitor Cfly is connected between the voltage input terminal IN and the voltage output terminal OUT. The input voltage VIN provided by the voltage input terminal IN charges the voltage output terminal OUT through the flying capacitor Cfly. At this time, the voltage difference VCfly across the flying capacitor Cfly is equal to VIN - VOUT, where VOUT is the output voltage provided by the voltage output terminal OUT.

[0059] In the second phase, the fourth switch Q4 and the sixth switch Q6 are turned on, while the third switch Q3 and the fifth switch Q5 are turned off. The flying capacitor Cfly is connected between the voltage output terminal OUT and ground, and discharges to the voltage output terminal OUT. At this time, VCfly = VOUT. Since VCfly cannot change abruptly, VOUT = VIN - VOUT, therefore VIN = 2VOUT. Thus, the switched capacitor converter can achieve a 2:1 turns ratio.

[0060] Because switched-capacitor converters do not contain an inductor L, they have lower losses, resulting in higher efficiency. However, switched-capacitor converters can only achieve a fixed turns ratio and cannot achieve voltage regulation. Therefore, as the above analysis shows, existing voltage converters cannot simultaneously achieve both large turns ratio regulation and high efficiency.

[0061] In view of this, the present disclosure provides an adjustable ratio voltage converter, including a buck-boost conversion circuit and a switched capacitor conversion circuit. When the adjustable ratio voltage converter operates in voltage regulation mode, the first output voltage of the adjustable ratio voltage converter is boosted by the switched capacitor conversion circuit to obtain a doubled voltage of the first output voltage. Based on the doubled first output voltage, the buck-boost conversion circuit converts the input voltage of the adjustable ratio voltage converter into a first output voltage that is related to both the charging time of the switched capacitor conversion circuit and the magnetization time of the buck-boost conversion circuit, so as to realize the large ratio voltage regulation of the adjustable ratio voltage converter.

[0062] Furthermore, since the switched capacitor conversion circuit contributes to the turns ratio of the adjustable ratio voltage converter, it can reduce the turns ratio of the buck-boost conversion circuit, that is, reduce the charging current of the buck-boost conversion circuit, thereby improving the efficiency of the adjustable ratio voltage converter. Therefore, the adjustable ratio voltage converter can achieve high-efficiency large-ratio voltage regulation.

[0063] The disclosed technical solutions are described in detail below with several specific embodiments.

[0064] Figure 3 This is a schematic diagram of an adjustable ratio voltage converter provided in an embodiment of the present disclosure, as shown below. Figure 3 As shown, the adjustable ratio voltage converter 100 includes a switched capacitor conversion circuit 110 and a buck-boost conversion circuit 120. The input terminals of the switched capacitor conversion circuit 110 and the buck-boost conversion circuit 120 are connected to the voltage input terminal IN. The first input-output terminal of the switched capacitor conversion circuit 110 is connected to the first input-output terminal of the buck-boost conversion circuit 120. The second input-output terminal of the switched capacitor conversion circuit 110 is connected to the second input-output terminal of the buck-boost conversion circuit 120. The output terminal of the switched capacitor conversion circuit 110 is connected to the voltage output terminal OUT. The ground terminal of the buck-boost conversion circuit 120 and the ground terminal of the switched capacitor conversion circuit 110 are both grounded.

[0065] The switched capacitor conversion circuit 110 is configured to boost the first output voltage VOUT1 of the adjustable ratio voltage converter 100 when the adjustable ratio voltage converter 100 is operating in voltage regulation mode, so as to obtain a double voltage of the first output voltage VOUT1.

[0066] The buck-boost conversion circuit 120 is configured to convert the input voltage VIN of the adjustable ratio voltage converter 100 into the first output voltage VOUT1 based on the voltage multiplier of the first output voltage VOUT1 when the adjustable ratio voltage converter 100 is operating in voltage regulation mode. The first output voltage VOUT1 is related to the charging time of the switched capacitor conversion circuit 110 and the magnetization time of the buck-boost conversion circuit 120.

[0067] For example, Figure 4 This is a circuit diagram of an adjustable ratio voltage converter provided in an embodiment of the present disclosure, as shown below. Figure 4 As shown, the switched capacitor conversion circuit 110 includes a flying capacitor Cfly, and the buck-boost conversion circuit 120 includes an inductor L. The first terminal of inductor L is connected to the voltage input terminal IN through the input terminal of the buck-boost conversion circuit 120, and is also grounded through the ground terminal of the buck-boost conversion circuit 120. The second terminal of inductor L is connected to the upper plate of the flying capacitor Cfly through the first input / output terminal of the buck-boost conversion circuit 120, and is also connected to the lower plate of the flying capacitor Cfly through the second input / output terminal of the buck-boost conversion circuit 120.

[0068] See also Figure 4 The adjustable ratio voltage converter 100 also includes an input capacitor CIN and an output capacitor COUT. The input capacitor CIN is connected between the voltage input terminal IN and ground, and the output capacitor COUT is connected between the voltage output terminal OUT and ground.

[0069] The adjustable ratio voltage converter 100 operates in at least one voltage regulation mode. When the adjustable ratio voltage converter 100 operates in the first voltage regulation mode, during the switching cycle Tsw of the adjustable ratio voltage converter 100, the adjustable ratio voltage converter 100 sequentially... Figure 5 The first charging demagnetization state shown, Figure 6 The charging and magnetization states shown are Figure 7 Switching between the discharge demagnetization states shown, Figure 5 for Figure 4 The diagram shown is the equivalent circuit diagram of the adjustable ratio voltage converter in the first charging demagnetization state. Figure 6 for Figure 4 The diagram shows the equivalent circuit of the adjustable ratio voltage converter in the charging and magnetizing state. Figure 7 for Figure 4 The diagram shows the equivalent circuit of the adjustable ratio voltage converter in the discharge demagnetization state.

[0070] In the first charging and demagnetizing state, such as Figure 5 As shown, the flying capacitor Cfly is connected between the voltage output terminal OUT and ground, so the voltage difference VCfly across the flying capacitor Cfly is equal to VOUT1. Simultaneously, both ends of the inductor L are connected to ground, so the voltage difference VL across the inductor L is zero. At this time, the switched capacitor conversion circuit 110 operates in the charging phase, and the buck-boost conversion circuit 120 operates in the first demagnetizing phase, i.e., the flying capacitor Cfly is charging, and the inductor L is demagnetizing.

[0071] In the charging and magnetizing state, such as Figure 6 As shown, the inductor L and the flying capacitor Cfly are connected in parallel between the voltage output terminal OUT and ground, so VCfly = VL = VOUT1. At this time, the switched capacitor conversion circuit 110 operates in the charging phase, and the buck-boost conversion circuit 120 operates in the magnetizing phase, that is, the flying capacitor Cfly is charged, and the inductor L is magnetized.

[0072] In the state of discharge demagnetization, such as Figure 7 As shown, inductor L and flying capacitor Cfly are connected in series between the voltage input terminal IN and the voltage output terminal OUT. Therefore, -VL + VCfly = VIN - VOUT1. Since VCfly cannot undergo a sudden change, -VL + VOUT1 = VIN - VOUT1, and thus VL = 2VOUT1 - VIN. At this time, the switched capacitor conversion circuit 110 operates in the discharge phase, and the buck-boost conversion circuit 120 operates in the second demagnetization phase, i.e., the flying capacitor Cfly discharges, and the inductor L demagnetizes.

[0073] In the switching cycle Tsw, the duration of the first charging-demagnetizing state is T1, the duration of the charging-magnetizing state is T2, and the duration of the discharging-demagnetizing state is T3, and T1 + T2 + T3 = Tsw. From the inductor volt-second product balance, we know that 0 T1+VOUT1 T2+(2VOUT1-VIN) T3=0. Since the charging time of the switched capacitor conversion circuit 110 is T1+T2, and the magnetization time of the buck-boost conversion circuit 120 is T2, (T1+T2) / Tsw=D, T2 / (T1+T2)=d, therefore 0 D (1-d)+VOUT1 D d+(2VOUT1-VIN) (1-D)=0.

[0074] Therefore, VOUT1 = VIN (1-D) / [2-(2-d) [D], then the adjustable ratio voltage converter 100 can achieve a ratio of [2-(2-d)] through the energy storage of inductor L and flying capacitor Cfly. The voltage regulation is calculated as D] / (1-D). When D=0.5, the charging time T1+T2 of the flying capacitor Cfly within the switching cycle Tsw is equal to the discharging time T3 of the flying capacitor Cfly, resulting in higher efficiency. Therefore, VIN / VOUT1=2+d to achieve a transformation ratio of 2~3.

[0075] Thus, when the adjustable ratio voltage converter 100 operates in voltage regulation mode, the switched capacitor conversion circuit 110 can control the flying capacitor Cfly to charge and discharge, so as to obtain a double voltage 2VOUT1 of the first output voltage. The buck-boost conversion circuit 120 can receive the double voltage 2VOUT1 of the first output voltage based on the inductor L, and control the inductor L to charge and demagnetize, so as to step down the input voltage VIN and obtain the first output voltage VOUT1, thereby realizing a large ratio voltage regulation.

[0076] Furthermore, since the turns ratio of the adjustable ratio voltage converter 100 includes the turns ratio of the switched capacitor conversion circuit 110 and the turns ratio of the buck-boost conversion circuit 120, the turns ratio of the buck-boost conversion circuit 120 can be reduced to decrease the charging current of the inductor L during large-ratio voltage regulation, thereby improving the efficiency during large-ratio voltage regulation.

[0077] In this embodiment of the disclosure, when the adjustable ratio voltage converter 100 operates in voltage regulation mode, the first output voltage VOUT1 of the adjustable ratio voltage converter 100 can be boosted by the switched capacitor conversion circuit 110 to obtain a doubled voltage of the first output voltage VOUT1. Based on the doubled voltage of the first output voltage VOUT1, the buck-boost conversion circuit 120 can convert the input voltage VIN of the adjustable ratio voltage converter 100 into a first output voltage VOUT1 that is related to both the charging time of the switched capacitor conversion circuit 110 and the magnetization time of the buck-boost conversion circuit 120, so that the adjustable ratio voltage converter 100 can achieve large ratio voltage regulation.

[0078] Furthermore, since the switched capacitor conversion circuit 110 contributes to the turns ratio of the adjustable turns ratio voltage converter 100, it can reduce the turns ratio of the buck-boost conversion circuit 120, that is, reduce the charging current of the buck-boost conversion circuit 120, thereby improving the efficiency of the adjustable turns ratio voltage converter 100. Therefore, the adjustable turns ratio voltage converter 100 can achieve high-efficiency large turns ratio voltage regulation.

[0079] In some embodiments, Figure 8 for Figure 4 The diagram shows the equivalent circuit of the adjustable ratio voltage converter in the discharge and magnetization state. When the adjustable ratio voltage converter 100 operates in the second voltage regulation mode, during the switching cycle Tsw of the adjustable ratio voltage converter 100, the adjustable ratio voltage converter 100 sequentially... Figure 6 The charging and magnetization status shown Figure 8 The discharge and magnetization states shown are Figure 7 Switching between the discharge and demagnetization states shown.

[0080] Among them, in the charging and magnetizing state, such as Figure 6 As shown, the inductor L and the flying capacitor Cfly are connected in parallel between the voltage output terminal OUT and ground, so VCfly = VL = VOUT1. At this time, the switched capacitor conversion circuit 110 operates in the charging phase, and the buck-boost conversion circuit 120 operates in the magnetizing phase, that is, the flying capacitor Cfly is charged, and the inductor L is magnetized.

[0081] In the state of discharge and magnetization, such as Figure 8 As shown, inductor L and flying capacitor Cfly are connected in series between the voltage output terminal OUT and ground. -VCfly + VL = VOUT1. Since VCfly cannot undergo a sudden change, -VOUT1 + VL = VOUT1, therefore VL = 2VOUT1. At this time, the switched capacitor conversion circuit 110 operates in the discharge phase, and the buck-boost conversion circuit 120 operates in the magnetization phase. Flying capacitor Cfly discharges, and inductor L is magnetized.

[0082] In the state of discharge demagnetization, such as Figure 7 As shown, inductor L and flying capacitor Cfly are connected in series between the voltage input terminal IN and the voltage output terminal OUT. Therefore, -VL + VCfly = VIN - VOUT1. Since VCfly cannot undergo a sudden change, -VL + VOUT1 = VIN - VOUT1, and thus VL = 2VOUT1 - VIN. At this time, the switched capacitor conversion circuit 110 operates in the discharge phase, and the buck-boost conversion circuit 120 operates in the second demagnetization phase, i.e., the flying capacitor Cfly discharges, and the inductor L demagnetizes.

[0083] In the switching cycle Tsw, the duration of the charging and magnetizing state is T2, the duration of the discharging and magnetizing state is T4, and the duration of the discharging and demagnetizing state is T3, and T4 + T2 + T3 = Tsw. From the inductor volt-second product balance, we know that VOUT1... T2+2VOUT1 T4+(2VOUT1-VIN) T3=0. Since the discharge time of the switched capacitor conversion circuit 110 is T3+T4, the charging time of the switched capacitor conversion circuit 110 is T2, and the magnetization time of inductor L in the discharge time T3+T4 is T4, T2 / Tsw=D, T4 / (T4+T3)=d, therefore VOUT1 D+2VOUT1 (1-D) d+(2VOUT1-VIN) (1-D) (1-d)=0.

[0084] Therefore, VOUT1 = VIN [(1-D) (1-d)] / (2-D), then the adjustable ratio voltage converter 100 can achieve a transformation ratio of (2-D) / [(1-D) through the energy storage of the inductor L and the flying capacitor Cfly. The voltage regulation is (1-d). When D=0.5, the charging time T2 of the flying capacitor Cfly within the switching cycle Tsw is equal to the discharging time T3+T4 of the flying capacitor Cfly, which has a higher efficiency. Therefore, VIN / VOUT1=3 / (1-d) to achieve a transformation ratio of 3~+∞.

[0085] In some embodiments, Figure 9 for Figure 4 The diagram shows the equivalent circuit of the adjustable ratio voltage converter in the second charging and demagnetizing state. When the adjustable ratio voltage converter 100 operates in the third voltage regulation mode, during the switching cycle Tsw of the adjustable ratio voltage converter 100, the adjustable ratio voltage converter 100 sequentially... Figure 9 The second charging demagnetization state shown Figure 6 The charging and magnetization states shown are Figure 7 Switching between the discharge and demagnetization states shown.

[0086] In the second charging demagnetization state, such as Figure 9As shown, when inductor L is connected between the voltage input terminal IN and ground, VL = -VIN. When flying capacitor Cfly is connected between the voltage output terminal OUT and ground, VCfly = VOUT1. At this time, the switched capacitor conversion circuit 110 operates in the charging phase, and the buck-boost conversion circuit 120 operates in the third demagnetizing phase, that is, the flying capacitor Cfly is charging, and the inductor L is demagnetizing.

[0087] In the charging and magnetizing state, such as Figure 6 As shown, the inductor L and the flying capacitor Cfly are connected in parallel between the voltage output terminal OUT and ground, so VCfly = VL = VOUT1. At this time, the switched capacitor conversion circuit 110 operates in the charging phase, and the buck-boost conversion circuit 120 operates in the magnetizing phase, that is, the flying capacitor Cfly is charged, and the inductor L is magnetized.

[0088] In the state of discharge demagnetization, such as Figure 7 As shown, inductor L and flying capacitor Cfly are connected in series between the voltage input terminal IN and the voltage output terminal OUT. Therefore, -VL + VCfly = VIN - VOUT1. Since VCfly cannot undergo a sudden change, -VL + VOUT1 = VIN - VOUT1, and thus VL = 2VOUT1 - VIN. At this time, the switched capacitor conversion circuit 110 operates in the discharge phase, and the buck-boost conversion circuit 120 operates in the second demagnetization phase, i.e., the flying capacitor Cfly discharges, and the inductor L demagnetizes.

[0089] In the switching cycle Tsw, the duration of the second charging-demagnetizing state is T5, the duration of the charging-magnetizing state is T2, and the duration of the discharging-demagnetizing state is T3, and T5 + T2 + T3 = Tsw. From the inductor volt-second product balance, we know that VIN... T5+2VOUT1 T2+(2VOUT1-VIN) T3=0. Since the charging time of the switched capacitor conversion circuit 110 is T5+T2, and the magnetization time of the buck-boost conversion circuit 120 is T2, (T5+T2) / Tsw=D, T2 / (T5+T2)=d, therefore VIN D (1-d)+2VOUT1 D d + (2VOUT1 - VIN) (1-D)=0.

[0090] Therefore, VOUT1 = VIN (1-D d) / [2-(2-d) If [D], then the adjustable ratio voltage converter 100 can achieve a transformation ratio of [2-(2-d)] through the energy storage of the inductor L and the flying capacitor Cfly. D] / (1-D d) Voltage regulation. When D=0.5, the charging time T5+T2 of the flying capacitor Cfly within the switching cycle Tsw is equal to the discharging time T3 of the flying capacitor Cfly, resulting in higher efficiency. Therefore, VIN / VOUT1=4 / (2-d)-1 to achieve a transformation ratio of 1~3.

[0091] In some embodiments, the operating mode of the adjustable ratio voltage converter 100 includes a voltage regulation mode, which can be any one of the first voltage regulation mode, the second voltage regulation mode, and the third voltage regulation mode.

[0092] In some embodiments, the operating modes of the adjustable ratio voltage converter 100 include multiple voltage regulation modes, wherein the multiple voltage regulation modes can be any two or all of the first voltage regulation mode, the second voltage regulation mode and the third voltage regulation mode.

[0093] For example, the adjustable voltage converter 100 has two voltage regulation modes, such as a first voltage regulation mode and a second voltage regulation mode, or a first voltage regulation mode and a third voltage regulation mode, or a second voltage regulation mode and a third voltage regulation mode.

[0094] In other embodiments, the adjustable ratio voltage converter 100 has three voltage regulation modes, namely the first voltage regulation mode, the second voltage regulation mode, and the third voltage regulation mode.

[0095] In some embodiments, see continue to see Figure 4 The switched capacitor conversion circuit 110 also includes a first transistor M1, a second transistor M2, a third transistor M3, and a fourth transistor M4. The first transistor M1, the second transistor M2, the third transistor M3, and the fourth transistor M4 are connected in series between the voltage input terminal IN and ground. The upper plate of the flying capacitor Cfly is connected to the connection point of the first transistor M1 and the second transistor M2, and the lower plate of the flying capacitor Cfly is connected to the connection point of the third transistor M3 and the fourth transistor M4. The voltage output terminal OUT is connected to the connection point of the second transistor M2 and the third transistor M3.

[0096] Among them, under the charging phase, such as Figure 5 , Figure 6 and Figure 9 As shown, the second transistor M2 and the fourth transistor M4 are turned on, while the first transistor M1 and the third transistor M3 are turned off, so that the flying capacitor Cfly is connected between the voltage output terminal OUT and ground.

[0097] Under the discharge phase, such as Figure 7 and Figure 8 As shown, the third transistor M3 is turned on, and the first transistor M1, the second transistor M2, the third transistor M3, and the fourth transistor M4 are turned off, so that the upper plate of the flying capacitor Cfly is connected to the second terminal of the inductor L, and the lower plate of the flying capacitor Cfly is connected to the voltage output terminal OUT.

[0098] In some embodiments, see continue to see Figure 4 The buck-boost converter circuit 120 also includes a fifth transistor M5, a sixth transistor M6, a seventh transistor M7, and an eighth transistor M8. The first end of the inductor L is connected to the voltage input terminal IN through the fifth transistor M5. The first end of the inductor L is also grounded through the sixth transistor M6. The second end of the inductor L is connected to the upper plate of the flying capacitor Cfly through the seventh transistor M7. The second end of the inductor L is also connected to the lower plate of the flying capacitor Cfly through the eighth transistor M8.

[0099] In the magnetized phase, such as Figure 6 and Figure 8 As shown, the sixth transistor M6 and the seventh transistor M7 are turned on, while the fifth transistor M5 and the eighth transistor M8 are turned off, so that the inductor L is connected between the upper plate of the flying capacitor Cfly and ground. In the first demagnetization phase, as... Figure 5 As shown, the sixth transistor M6 and the eighth transistor M8 are turned on, while the fifth transistor M5 and the seventh transistor M7 are turned off, so that both ends of the inductor L are connected to ground.

[0100] In the second demagnetization phase, such as Figure 7 As shown, transistors M5 and M7 are turned on, while transistors M6 and M8 are turned off, connecting inductor L between the voltage input terminal IN and the voltage output terminal OUT. In the third demagnetizing phase, as... Figure 9 As shown, the fifth transistor M5 and the eighth transistor M8 are turned on, while the sixth transistor M6 and the seventh transistor M7 are turned off, so that the inductor L is connected between the voltage input terminal IN and ground.

[0101] In some embodiments, the operating mode of the adjustable ratio voltage converter 100 also includes a buck-boost mode. The buck-boost conversion circuit 120 is further configured to convert the input voltage VIN into a second output voltage VOUT2 of the adjustable ratio voltage converter 100 when the adjustable ratio voltage converter 100 is operating in buck-boost mode. The second output voltage VOUT2 is related to the magnetization time of the inductor L.

[0102] The switched capacitor conversion circuit 110 is also configured to stabilize the second output voltage VOUT2 based on the flying capacitor Cfly when the adjustable ratio voltage converter 100 is operating in buck-boost mode.

[0103] For example, Figures 10(a) and 10(b) are Figure 4 The equivalent circuit diagram of the adjustable ratio voltage converter in buck-boost mode is shown. When the adjustable ratio voltage converter 100 operates in buck-boost mode, during the switching cycle Tsw of the adjustable ratio voltage converter 100, the adjustable ratio voltage converter 100 switches between the target magnetization state shown in Figure 10(a) and the target demagnetization state shown in Figure 10(b).

[0104] In the target magnetized state, the second transistor M2, the fourth transistor M4, the sixth transistor M6, and the seventh transistor M7 are turned on, while the first transistor M1, the third transistor M3, the fifth transistor M5, and the eighth transistor M8 are turned off, so that the inductor L and the flying capacitor Cfly are connected in parallel between the voltage output terminal OUT and ground, as shown in Figure 10(a). At this time, the buck-boost converter circuit 120 operates in the magnetized phase, so the inductor L is magnetized, and VL = VOUT2.

[0105] In the target demagnetization state, the second transistor M2, the fourth transistor M4, the fifth transistor M5, and the seventh transistor M7 are turned on, while the first transistor M1, the third transistor M3, the sixth transistor M6, and the eighth transistor M8 are turned off. This connects the inductor L between the voltage input terminal IN and the voltage output terminal OUT, and the flying capacitor Cfly is connected between the voltage output terminal OUT and ground, as shown in Figure 10(b). At this time, the buck-boost converter circuit 120 operates in the demagnetization phase, so the inductor L is demagnetized, and VL = VOUT2 - VIN.

[0106] Since the flying capacitor Cfly remains connected between the voltage output terminal OUT and ground during both the target magnetization and demagnetization states, it does not charge or discharge in buck-boost mode. Therefore, the switched capacitor conversion circuit 110 stops operating in buck-boost mode. At this time, the flying capacitor Cfly acts as a voltage regulator, stabilizing the second output voltage VOUT2.

[0107] Within the switching cycle Tsw, the duration of the target demagnetization state (the magnetization time of inductor L) is T6, and the duration of the target demagnetization state (the demagnetization time of inductor L) is T7, and T6 + T7 = Tsw. From the inductor volt-second product balance, we know that VOUT2... T6+(VOUT2-VIN) T7=0. Since T6 / Tsw=d, therefore VOUT2 d+(VOUT2-VIN) (1-d)=0, therefore VOUT2=VIN (1-d), then the adjustable ratio voltage converter 100 can achieve a voltage regulation ratio of 1 / (1-d) through the energy storage of the inductor L, so as to achieve a ratio of 1 to +∞.

[0108] In some embodiments, the operating mode of the adjustable ratio voltage converter 100 also includes a fixed voltage mode, and the switched capacitor conversion circuit 110 is further configured to reduce the input voltage VIN to half of the input voltage VIN when the adjustable ratio voltage converter 100 is operating in the fixed voltage mode, so as to obtain the third output voltage VOUT3 of the adjustable ratio voltage converter 100, i.e., VOUT3=VIN / 2.

[0109] For example, Figures 11(a) and 11(b) are Figure 4 The equivalent circuit diagram of the adjustable ratio voltage converter in fixed voltage mode is shown. When the adjustable ratio voltage converter 100 operates in fixed voltage mode, during the switching cycle Tsw of the adjustable ratio voltage converter 100, the adjustable ratio voltage converter 100 switches between the target charging state shown in FIG11(a) and the target discharging state shown in FIG11(b).

[0110] In the target charging state, the first transistor M1 and the third transistor M3 are turned on, while the second transistor M2, the fourth transistor M4, the fifth transistor M5, the sixth transistor M6, the seventh transistor M7, and the eighth transistor M8 are turned off. The flying capacitor Cfly is connected between the voltage input terminal IN and the voltage output terminal OUT, and the inductor L is left floating, as shown in Figure 11(a). At this time, the switched capacitor conversion circuit 110 operates in the charging phase, and the flying capacitor Cfly is charged, VCfly = VIN - VOUT3.

[0111] In the target discharge state, the second transistor M2 and the fourth transistor M4 are turned on, the first transistor M1 and the third transistor M3 are turned off, the flying capacitor Cfly is connected between the voltage output terminal OUT and ground, and the inductor L is left floating, as shown in Figure 11(b). At this time, the switched capacitor conversion circuit 110 is operating in the discharge phase, so the flying capacitor Cfly discharges, and VCfly = VOUT3.

[0112] Since the inductor L remains floating during the target charging and discharging states, the buck-boost converter circuit 120 stops operating in fixed voltage mode. Because VCfly cannot undergo abrupt changes, VOUT3 = VIN - VOUT3, therefore VIN = 2VOUT3. Thus, the adjustable ratio voltage converter 100 can achieve a fixed 2:1 ratio through the energy stored in the flying capacitor Cfly, achieving a highly efficient 2:1 ratio to further improve efficiency at the 2:1 ratio.

[0113] This disclosure also provides a power supply chip, including at least one adjustable ratio voltage converter 100 provided in any of the above embodiments.

[0114] Figure 12 This is a schematic diagram of the structure of a power chip provided in an embodiment of this disclosure, such as... Figure 12 As shown, the power chip 200 includes a voltage input terminal IN, a voltage output terminal OUT, and at least one adjustable ratio voltage converter 100.

[0115] For example, such as Figure 12 As shown, the power chip 200 includes a first adjustable ratio voltage converter 100a and a second adjustable ratio voltage converter 100b, which are connected in parallel between the voltage input terminal IN and the voltage output terminal OUT.

[0116] In this configuration, the first adjustable voltage converter 100a and the second adjustable voltage converter 100b operate in the same mode. The transistors at the same location in the first adjustable voltage converter 100a and the second adjustable voltage converter 100b have the same or opposite on / off states. The first adjustable voltage converter 100a and the second adjustable voltage converter 100b each share half of the current.

[0117] For example, the transistors at the same location in the first adjustable voltage converter 100a and the second adjustable voltage converter 100b have the same on / off state to simplify the control of the power supply chip 200, or conversely, to reduce the ripple of the output voltage.

[0118] It should be noted that, Figure 12 The power chip 200 is shown as an example only, including two adjustable ratio voltage converters 100. In practical applications, the number of adjustable ratio voltage converters 100 can be one, three or more, and this disclosure does not impose any specific limitations on this.

[0119] The power chip 200 provided in this embodiment includes at least one adjustable ratio voltage converter 100 provided in any of the above embodiments, and has the functional modules and beneficial effects of the adjustable ratio voltage converter 100, which will not be described in detail here.

[0120] This disclosure also provides an electronic device, including the power chip 200 described above, that is, including the adjustable ratio voltage converter 100 provided in any of the above embodiments, which has the functional modules and beneficial effects of the adjustable ratio voltage converter 100, which will not be described in detail here.

[0121] Electronic devices include, but are not limited to, smartphones, tablets, smart home devices, vehicles, and wearable devices.

[0122] Unless otherwise expressly indicated by the context, the singular form of words used herein and in the appended claims includes the plural form, and vice versa. Thus, when referring to the singular, the plural form of the corresponding term is generally included. Similarly, the terms “comprising” and “including” are to be interpreted as including rather than exclusively. Likewise, the terms “including” and “or” should be interpreted as including unless such interpretation is expressly prohibited herein. Where the term “example” is used herein, the “example” is merely exemplary and illustrative, and should not be considered exclusive or extensive.

[0123] Several embodiments of this disclosure have been described in detail above. However, it is obvious that those skilled in the art can make various modifications and variations to the embodiments of this disclosure without departing from the spirit and scope of this disclosure. The scope of protection of this disclosure is defined by the appended claims.

Claims

1. An adjustable ratio voltage converter, characterized in that, Includes buck-boost conversion circuit and switched capacitor conversion circuit; The input terminal of the switched capacitor conversion circuit and the input terminal of the buck-boost conversion circuit are connected to the voltage input terminal. The input and output terminals of the switched capacitor conversion circuit are connected to the input and output terminals of the buck-boost conversion circuit. The output terminal of the switched capacitor conversion circuit 110 is connected to the voltage output terminal. The switched capacitor conversion circuit is configured to boost the first output voltage of the adjustable ratio voltage converter when the adjustable ratio voltage converter is operating in voltage regulation mode, so as to obtain a multiplier of the first output voltage. The buck-boost conversion circuit is configured to convert the input voltage of the adjustable ratio voltage converter into the first output voltage based on a voltage multiplier of the first output voltage when the adjustable ratio voltage converter is operating in voltage regulation mode. The first output voltage is related to both the charging time of the switched capacitor conversion circuit and the magnetization time of the buck-boost conversion circuit.

2. The adjustable ratio voltage converter according to claim 1, characterized in that, The switched capacitor conversion circuit includes a flying capacitor, and the buck-boost conversion circuit includes an inductor; The switched capacitor conversion circuit is further configured to control the flying capacitor to charge and discharge when the adjustable ratio voltage converter is operating in the voltage regulation mode, so as to obtain twice the voltage of the first output voltage. The buck-boost conversion circuit is further configured such that, when the adjustable ratio voltage converter operates in the voltage regulation mode, it receives twice the voltage of the first output voltage through the inductor and controls the inductor to charge and demagnetize, thereby stepping down the input voltage to obtain the first output voltage.

3. The adjustable ratio voltage converter according to claim 2, characterized in that, When the adjustable ratio voltage converter operates in the first voltage regulation mode, during the switching cycle of the adjustable ratio voltage converter, the adjustable ratio voltage converter switches sequentially between the first charging demagnetization state, the charging and magnetizing state, and the discharging and demagnetizing state. In the first charging demagnetizing state, the flying capacitor is connected between the voltage output terminal and ground so that the switched capacitor conversion circuit operates in the charging phase, and both ends of the inductor are connected to ground so that the buck-boost conversion circuit operates in the first demagnetizing phase. In the charging and magnetizing state, the inductor and the flying capacitor are connected in parallel between the voltage output terminal and ground, so that the switched capacitor conversion circuit operates in the charging phase and the buck-boost conversion circuit operates in the magnetizing phase. In the discharge demagnetization state, the inductor and the flying capacitor are connected in series between the voltage input terminal and the voltage output terminal, so that the switched capacitor conversion circuit operates in the discharge phase and the buck-boost conversion circuit operates in the second demagnetization phase.

4. The adjustable ratio voltage converter according to claim 3, characterized in that, The first output voltage is equal to the input voltage and (1-D) / [2-(2-d)]. The product of D], where D is the proportion of the charging time in the switching cycle, and d is the proportion of the magnetization time in the charging time.

5. The adjustable ratio voltage converter according to claim 2, characterized in that, When the adjustable ratio voltage converter operates in the second voltage regulation mode, during the switching cycle of the adjustable ratio voltage converter, the adjustable ratio voltage converter switches sequentially between the charging and magnetizing state, the discharging and magnetizing state, and the discharging and demagnetizing state. In the charging and magnetizing state, the inductor and the flying capacitor are connected in parallel between the voltage output terminal and ground, so that the switched capacitor conversion circuit operates in the charging phase and the buck-boost conversion circuit operates in the magnetizing phase. In the discharge and magnetization state, the inductor and the flying capacitor are connected in series between the voltage output terminal and ground, so that the switched capacitor conversion circuit operates in the discharge phase and the buck-boost conversion circuit operates in the magnetization phase. In the discharge demagnetization state, the inductor and the flying capacitor are connected in series between the voltage input terminal and the voltage output terminal, so that the switched capacitor conversion circuit operates in the discharge phase and the buck-boost conversion circuit operates in the second demagnetization phase.

6. The adjustable ratio voltage converter according to claim 5, characterized in that, The first output voltage is equal to the input voltage and [(1-D)] The product of (1-d) / (2-D), where D is the proportion of the charging time in the switching cycle and d is the proportion of the magnetization time in the discharge time of the flying capacitor.

7. The adjustable ratio voltage converter according to claim 2, characterized in that, When the adjustable ratio voltage converter operates in the third voltage regulation mode, during the switching cycle of the adjustable ratio voltage converter, the adjustable ratio voltage converter switches sequentially between the second charging demagnetization state, the charging and magnetizing state, and the discharging and demagnetizing state. In the second charging demagnetizing state, the inductor is connected between the voltage input terminal and ground, and the flying capacitor is connected between the voltage output terminal and ground, so that the switched capacitor conversion circuit operates in the charging phase and the buck-boost conversion circuit operates in the third demagnetizing phase. In the charging and magnetizing state, the inductor and the flying capacitor are connected in parallel between the voltage output terminal and ground, so that the switched capacitor conversion circuit operates in the charging phase and the buck-boost conversion circuit operates in the magnetizing phase. In the discharge demagnetization state, the inductor and the flying capacitor are connected in series between the voltage input terminal and the voltage output terminal, so that the switched capacitor conversion circuit operates in the discharge phase and the buck-boost conversion circuit operates in the second demagnetization phase.

8. The adjustable ratio voltage converter according to claim 7, characterized in that, The first output voltage is equal to the input voltage and (1-D) d) / [2-(2-d) The product of D], where D is the proportion of the charging time in the switching cycle, and d is the proportion of the magnetization time in the charging time.

9. The adjustable ratio voltage converter according to claim 3, 5 or 7, characterized in that, The switched capacitor conversion circuit further includes a first transistor, a second transistor, a third transistor, and a fourth transistor; The first transistor, the second transistor, the third transistor, and the fourth transistor are connected in series between the voltage input terminal and ground. The upper plate of the flying capacitor is connected to the connection point of the first transistor and the second transistor, the lower plate of the flying capacitor is connected to the connection point of the third transistor and the fourth transistor, and the voltage output terminal is connected to the connection point of the second transistor and the third transistor. During the charging phase, the second transistor and the fourth transistor are turned on, while the first transistor and the third transistor are turned off; during the discharging phase, the third transistor is turned on, while the first transistor, the second transistor, and the fourth transistor are turned off.

10. The adjustable ratio voltage converter according to claim 3, 5 or 7, characterized in that, The buck-boost conversion circuit also includes a fifth transistor, a sixth transistor, a seventh transistor, and an eighth transistor; The first end of the inductor is connected to the voltage input terminal through the fifth transistor, and the first end of the inductor is also grounded through the sixth transistor. The second end of the inductor is connected to the upper plate of the flying capacitor through the seventh transistor, and the second end of the inductor is also connected to the lower plate of the flying capacitor through the eighth transistor. Specifically, during the magnetization phase, the sixth and seventh transistors are turned on, while the fifth and eighth transistors are turned off; during the first demagnetization phase, the sixth and eighth transistors are turned on, while the fifth and seventh transistors are turned off; during the second demagnetization phase, the fifth and seventh transistors are turned on, while the sixth and eighth transistors are turned off; and during the third demagnetization phase, the fifth and eighth transistors are turned on while the sixth and seventh transistors are turned off.

11. The adjustable ratio voltage converter according to any one of claims 2-8, characterized in that, The buck-boost conversion circuit is further configured to convert the input voltage into a second output voltage of the adjustable ratio voltage converter when the adjustable ratio voltage converter is operating in buck-boost mode, wherein the second output voltage is related to the magnetization time of the inductor; The switched capacitor conversion circuit is further configured to stabilize the second output voltage based on the flying capacitor when the adjustable ratio voltage converter operates in the buck-boost mode.

12. The adjustable ratio voltage converter according to any one of claims 2-8, characterized in that, The switched capacitor conversion circuit is further configured to reduce the input voltage to half of the input voltage when the adjustable ratio voltage converter is operating in a fixed voltage mode, so as to obtain a third output voltage of the adjustable ratio voltage converter.

13. A power supply chip, characterized in that, It includes a voltage input terminal, a voltage output terminal, and at least one adjustable ratio voltage converter as described in any one of claims 1-12.

14. The power chip according to claim 13, characterized in that, Includes a first adjustable ratio voltage converter and a second adjustable ratio voltage converter; The first adjustable voltage converter and the second adjustable voltage converter are connected in parallel between the voltage input terminal and the voltage output terminal. The first adjustable voltage converter and the second adjustable voltage converter operate in the same mode. The on / off states of the transistors at the same location in the first adjustable voltage converter and the second adjustable voltage converter are the same or opposite.

15. An electronic device, characterized in that, Includes the power chip as described in claim 13.

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