Amplification circuit and electronic equipment

Abstract

The embodiment of the utility model discloses an amplifying circuit and an electronic device, which comprises an input matching unit used for matching impedance between an input end of a gain unit and a signal source, and the input matching unit is provided with a signal receiving end and a first output end. The correction unit is used for generating a compensation signal, and the compensation signal comprises a non-linear component. The gain unit receives the impedance-matched first signal output by the input matching unit and performs transconductance amplification on the first signal to generate a second signal; the compensation signal is received, the compensation signal and the second signal are superposed and then are further amplified to generate and output a third signal, and the compensation signal and the second signal are opposite in electrical property. And the output matching unit is used for matching impedance between the output end of the gain unit and the load so as to perform impedance matching processing on the received third signal and output the third signal subjected to the impedance matching processing.

Description

TECHNICAL FIELD

[0001] The utility model relates to the technical field of amplifier especially relates to an amplifier circuit and electronic equipment. BACKGROUND

[0002] With the mobile wireless communication technology gradually evolving from 2G to 5G and even future 6G, the performance of radio frequency front-end devices is required to be higher in communication systems. In wireless communication, after long-distance transmission, the signal is often extremely weak when it reaches the receiving end and is mixed with a large amount of noise. As the first active module of the receiver front-end, the low-noise amplifier is mainly responsible for amplifying the received weak signal, and its performance directly determines the overall quality of the communication system. Therefore, it is necessary to design a broadband, high-linearity, low-noise amplifier to ensure that the signal is not distorted during reception and amplification, thereby meeting the demand for high-speed and large-capacity communication.

[0003] Further, with the increasing shortage of modern wireless communication spectrum resources, complex modulation techniques such as orthogonal frequency division multiplexing (OFDM) are widely used to improve spectrum utilization. Such modulation methods have very high requirements for signal linearity, otherwise signal distortion and interference will occur, and in severe cases, the performance of the communication system will be affected. In order to improve the bandwidth and linearity of the low-noise amplifier, the prior art usually needs to sacrifice other performance parameters (such as noise figure or gain) as a trade-off. If the gain of the amplification circuit is reduced and the noise is improved on the basis of improving the bandwidth and linearity, the sensitivity of the receiver will be reduced, affecting the receiver's reception of weak signals. SUMMARY

[0004] Embodiments of the utility model provide an amplification circuit and electronic equipment, aiming to improve the bandwidth and linearity of the amplification circuit without compromising other performance indicators (such as noise figure and gain) of the amplification circuit.

[0005] To solve the above technical problems, embodiments of the utility model disclose the following technical solutions:

[0006] On the one hand, an amplification circuit is provided, comprising: an input matching unit, a gain unit, a correction unit, and an output matching unit;

[0007] The input matching unit is used to match the impedance between the input end of the gain unit and the signal source, and the input matching unit has a signal receiving end and a first output end, the signal receiving end is used to receive a first signal, and the first output end is used to output the first signal after impedance matching;

[0008] The correction unit receives the first signal through the gain unit and generates a compensation signal by performing negative transconductance compensation on the first signal, wherein the compensation signal contains a nonlinear component;

[0009] The gain unit receives the first signal that has been impedance matched by the input matching unit and generates a second signal by performing transconductance amplification on the first signal; receives the compensation signal, and further amplifies the superposition of the compensation signal and the second signal to generate and output a third signal, wherein the compensation signal and the second signal are electrically opposite;

[0010] The output matching unit is configured to match the impedance between the output end of the gain unit and the load, to perform impedance matching processing on the received third signal, and to output the third signal that has been subjected to impedance matching processing.

[0011] The first signal is a voltage-form weak signal to be amplified, and the second signal, the compensation signal, and the third signal are all in the form of current.

[0012] In addition to or instead of the one or more features disclosed above, the gain unit comprises a first N-type switch tube M1 and a second N-type switch tube M2, and both the first N-type switch tube M1 and the second N-type switch tube M2 are in the saturation region.

[0013] The gate end of the first N-type switch tube M1 is connected to the first output end, the source end of the first N-type switch tube M1 is grounded, the drain end of the first N-type switch tube M1 is connected to the source end of the second N-type switch tube M2, and the drain end of the second N-type switch tube M2 is connected to the input end of the output matching unit.

[0014] In addition to or instead of the one or more features disclosed above, the source end of the first N-type switch tube M1 is connected to the ground through a negative feedback inductor LS.

[0015] In addition to or instead of the one or more features disclosed above, the correction unit comprises a third N-type switch tube M3 and a fourth N-type switch tube M4, and both the third N-type switch tube M3 and the fourth N-type switch tube M4 are in the weak inversion region.

[0016] The gate end of the third N-type switch tube M3 is connected between the source end of the first N-type switch tube M1 and the negative feedback inductor LS, the source end of the third N-type switch tube M3 is grounded, the drain end of the third N-type switch tube M3 is connected to the source end of the fourth N-type switch tube M4, and the drain end of the fourth N-type switch tube M4 is connected between the drain end of the first N-type switch tube M1 and the source end of the second N-type switch tube M2.

[0017] In addition to one or more of the features described above, or as an alternative, the bias unit includes a first transmission end, a second transmission end, a third transmission end, and a fourth transmission end.

[0018] The first transmission end is connected to the gate end of the first N-type switch tube M1, for controlling the voltage of the gate end of the first N-type switch tube M1.

[0019] The second transmission end is connected to the gate end of the second N-type switch tube M2, for controlling the voltage of the gate end of the second N-type switch tube M2.

[0020] The third transmission end is connected to the gate end of the third N-type switch tube M3, for controlling the voltage of the gate end of the third N-type switch tube M3.

[0021] The fourth transmission end is connected to the gate end of the fourth N-type switch tube M4, for controlling the voltage of the gate end of the fourth N-type switch tube M4.

[0022] In addition to one or more of the features described above, or as an alternative, the gain unit further includes a first capacitor C1 and a second capacitor C2, the first capacitor C1 being connected between the first output end and the gate end of the first N-type switch tube M1, and the second capacitor C2 having one end connected between the connection path of the first transmission end and the gate end of the second N-type switch tube M2, and the other end grounded.

[0023] In addition to one or more of the features described above, or as an alternative, the correction unit further includes a third capacitor C3 and a fourth capacitor C4, the third capacitor C3 being connected between the source end of the first N-type switch tube M1 and the gate end of the third N-type switch tube M3, and the fourth capacitor C4 having one end connected between the connection path of the fourth transmission end and the gate end of the fourth N-type switch tube M4, and the other end grounded.

[0024] In addition to one or more of the features described above, or as an alternative, the input matching unit includes a first matching inductor Lin and a first matching capacitor Cin, one end of the first matching inductor Lin being connected to the signal receiving end, and the other end being connected to the first output end, and one end of the first matching capacitor Cin being connected between the first matching inductor Lin and the first output end, and the other end being grounded.

[0025] In addition to one or more of the above disclosed features, or as an alternative, the output matching unit includes a second matching inductor L7, a third matching inductor Ld, a second matching capacitor C6, and a third matching capacitor C5, the second matching capacitor C6 and the second matching inductor L7 are connected in series between the drain terminal of the second N-type switching tube M2 and the output terminal of the amplification circuit, one end of the third matching inductor Ld is grounded, and the other end is connected between the drain terminal of the second N-type switching tube M2 and the second matching capacitor C6, one end of the third matching capacitor C5 is grounded, and the other end is connected between the drain terminal of the second N-type switching tube M2 and the second matching capacitor C6.

[0026] In another aspect, an electronic device is provided, including any of the above disclosed amplification circuits.

[0027] One of the above technical solutions has the following advantages or beneficial effects: after the gain unit transconductance amplifies the first signal to generate the second signal, the second signal contains a linear component and a nonlinear component, the linear component is a component proportional to the first signal, and the nonlinear component is a distortion signal introduced during transconductance amplification. In order to improve the linearity of the amplification circuit, reduce the distortion of the signal, and improve the communication quality, the present application introduces a correction unit, which generates a compensation signal by negatively transconductance compensating the first signal. The compensation signal contains a nonlinear component, and the electrical properties of the compensation signal and the second signal are opposite. After the compensation signal is input to the gain unit, it is superimposed with the second signal, the distortion part in the second signal is eliminated, and a third signal is further amplified, so that the third signal has higher linearity on the basis of maintaining high gain. Such design can avoid the situation that the signal transmission bandwidth is limited due to excessively high gain. Further, the input matching unit optimizes the energy transfer efficiency between the signal source and the gain unit, and the output matching unit optimizes the energy transfer between the gain unit and the load, so that the amplification circuit can maintain good impedance matching on a wide frequency band, reduce signal loss, and improve signal transmission efficiency.

[0028] In summary, the technical solution disclosed in the present application can significantly improve the bandwidth and linearity of the amplification circuit without compromising other performance indicators of the amplification circuit. BRIEF DESCRIPTION OF DRAWINGS

[0029] The technical solution and other beneficial effects of the present application will be apparent from the following detailed description of the specific embodiments of the present application, combined with the accompanying drawings.

[0030] Figure 1 is a structure diagram of an amplification circuit provided by an embodiment of the present application Figure 1 ;

[0031] Figure 2is a structure diagram of an amplification circuit provided by an embodiment of the present application Figure 2 ;

[0032] Figure 3 is an equivalent circuit diagram of an amplification circuit provided by an embodiment of the present application

[0033] Figure 4 is a gain performance diagram of an amplification circuit simulation provided by an embodiment of the present application

[0034] Figure 5 is an input impedance matching performance diagram of an amplification circuit simulation provided by an embodiment of the present application

[0035] Figure 6 is a noise performance diagram of an amplification circuit simulation provided by an embodiment of the present application

[0036] Figure 7 is a linear optimization performance diagram of an amplification circuit simulation provided by an embodiment of the present application

[0037] Legend of reference signs:

[0038] 100, input matching unit

[0039] 200, gain unit

[0040] 300, correction unit

[0041] 400, output matching unit

[0042] 500, bias unit DETAILED DESCRIPTION

[0043] In order to make the purpose, technical scheme and beneficial effects of the present application clearer, the present application is further described in detail below in combination with the drawings and specific embodiments. It should be understood that the specific embodiments described in the present specification are only for the purpose of explaining the present application, and are not intended to limit the present application.

[0044] In the description of the utility model, it is necessary to understand that the orientation or positional relation indicated by the terms "center", "longitudinal", "lateral", "length", "width", "thickness", "upper", "lower", "front", "rear", "left", "right", "vertical", "horizontal", "top", "bottom", "inner", "outer", "clockwise", "counterclockwise" and the like is the orientation or positional relation based on the orientation or positional relation shown in the drawings, and is only for the convenience of describing the utility model and simplifying the description, and therefore cannot be understood as indicating or implying that the device or element indicated must have a particular orientation, be constructed and operated in a particular orientation, and therefore cannot be understood as limiting the utility model. In addition, the terms "first" and "second" are only for the purpose of description, and cannot be understood as indicating or implying relative importance or implicitly indicating the number of the indicated technical features. Therefore, the features limited by "first" and "second" can explicitly or implicitly include one or more of the features. In the description of the utility model, the meaning of "multiple" is two or more than two, unless otherwise explicitly specified and limited.

[0045] In the description of the utility model, it should be explained that, unless otherwise explicitly specified and limited, the terms "mounting", "connection", "connection" should be understood broadly, for example, it can be fixedly connected, or it can be detachably connected, or integrally connected, it can be mechanically connected, it can be directly connected, or indirectly connected through an intermediate medium, it can be the communication between two elements or the interaction relationship between two elements. For ordinary skilled in the art, the specific meaning of the above terms in the utility model can be understood according to the specific circumstances.

[0046] In the utility model, unless otherwise explicitly specified and limited, the "upper" or "lower" of the first feature in the second feature can include that the first and second features are in direct contact, or the first and second features are not in direct contact but are in contact through another feature between them. Moreover, the "upper", "upper" and "upper" of the first feature in the second feature include that the first feature is directly above and obliquely above the second feature, or only indicates that the horizontal height of the first feature is higher than that of the second feature. The "below", "below" and "below" of the first feature in the second feature include that the first feature is directly above and obliquely above the second feature, or only indicates that the horizontal height of the first feature is less than that of the second feature.

[0047] The utility model embodiment discloses an amplification circuit, refer to Figure 1The amplification circuit comprises an input matching unit 100, a gain unit 200, a correction unit 300, and an output matching unit 400. The input matching unit 100 is configured to match the impedance between the input end of the gain unit 200 and a signal source, so as to perform impedance matching processing on the received first signal. The correction unit 300 receives the first signal passing through the gain unit 200 through the gain unit 200, and performs negative transconductance compensation on the first signal to generate a compensation signal. The gain unit 200 is configured to receive the first signal passing through the impedance matching output by the input matching unit 100, and perform transconductance amplification on the first signal to generate a second signal; the gain unit 200 also receives the compensation signal, superimposes the compensation signal and the second signal to generate an output third signal, and the electrical properties of the compensation signal and the second signal are opposite. The output matching unit 400 is configured to match the impedance between the output end of the gain unit 200 and a load, so as to perform impedance matching processing on the received third signal, and output the third signal after the impedance matching processing.

[0048] After the gain unit 200 performs transconductance amplification on the first signal to generate a second signal, the second signal contains a linear component and a nonlinear component. The linear component is a component proportional to the first signal, and the nonlinear component is a distortion signal introduced during transconductance amplification. In order to improve the linearity of the amplification circuit, reduce the distortion of the signal, and improve the communication quality, the correction unit 300 is introduced. The correction unit 300 generates a compensation signal after performing negative transconductance compensation on the first signal. The compensation signal contains a nonlinear component, and the electrical properties of the compensation signal and the second signal are opposite. After the compensation signal is input to the gain unit 200 and superimposed with the second signal, the distortion part in the second signal is eliminated, and a third signal is further amplified, so that the third signal has higher linearity on the basis of maintaining high gain. In this way, the situation that the signal transmission bandwidth is limited due to excessively high gain can be avoided. Further, the input matching unit 100 optimizes the energy transmission efficiency between the signal source and the gain unit 200, and the output matching unit 400 optimizes the energy transmission between the gain unit 200 and the load, so that the amplification circuit can maintain good impedance matching on a wide frequency band, reduce signal loss, and improve signal transmission efficiency.

[0049] Specifically, referring to Figure 2The input matching unit 100 has a signal receiving end and a first input end. The signal receiving end is connected with the input end of the amplification circuit, and is used to receive a first signal, i.e., a weak signal in the form of voltage to be amplified. The first output end is used to output the first signal after impedance matching. In some embodiments, the input matching unit 100 includes a first matching inductor Lin and a first matching capacitor Cin. One end of the first matching inductor Lin is connected with the signal receiving end, and the other end is connected with the first output end. One end of the first matching capacitor Cin is connected between the first matching inductor Lin and the first output end, and the other end is grounded. The first matching inductor Lin and the first matching capacitor Cin form an LC matching network. In actual applications, the overall impedance characteristics of the input matching unit 100 can be adjusted by adjusting the parameters of the first matching inductor Lin and the first matching capacitor Cin, so as to adapt the output impedance of the signal source to the input impedance of the subsequent gain unit 200. At the same time, the first matching inductor Lin and the first matching capacitor Cin can also perform band-pass filtering on the first signal, select the target frequency band signal transmission, suppress the unnecessary interference signals, and reduce the influence of noise and unnecessary frequency components on the performance of the subsequent gain unit 200 and the correction unit 300.

[0050] Further, the gain unit 200 amplifies the first signal through the first N-type switch tube M1 and the second N-type switch tube M2. Specifically, the first N-type switch tube M1 and the second N-type switch tube M2 are both in the saturation region. The gate end of the first N-type switch tube M1 is connected with the first output end to receive the first signal. The source end of the first N-type switch tube M1 is grounded. The drain end of the first N-type switch tube M1 is connected with the source end of the second N-type switch tube M2. The drain end of the second N-type switch tube M2 is connected with the input end of the output matching unit 400. The gate end of the first N-type switch tube M1 receives a first bias voltage to ensure that the first N-type switch tube M1 is in the saturation region. The gate end of the second N-type switch tube M2 receives a second bias voltage to ensure that the second N-type switch tube M2 is in the saturation region. The correction unit 300 includes a third N-type switch tube M3 and a fourth N-type switch tube M4, both of which are in the weak inversion region. The gate end of the third N-type switch tube M3 is connected between the source end of the first N-type switch tube M1 and the negative feedback inductor LS to receive the first signal after the first N-type switch tube M1. The source end of the third N-type switch tube M3 is grounded. The drain end of the third N-type switch tube M3 is connected with the source end of the fourth N-type switch tube M4. The drain end of the fourth N-type switch tube M4 is connected between the drain end of the first N-type switch tube M1 and the source end of the second N-type switch tube M2.

[0051] The first N-type switch tube M1 and the second N-type switch tube M2 jointly constitute a first common-source common-gate structure, wherein the first N-type switch tube M1 is a common-source structure, and the second N-type switch tube M2 is a common-gate structure. The first N-type switch tube M1 and the second N-type switch tube M2 are both in a saturation region, the first signal is input in the form of a voltage from the gate terminal of the first N-type switch tube M1 to the gain unit 200, the first N-type switch tube M1 converts the input first signal in the form of a voltage into a second signal in the form of a current, so that the transconductance amplification is completed in the first N-type switch tube M1. The second signal formed after the transconductance amplification of the first N-type switch tube M1 is output from the drain terminal of the first N-type switch tube M1, and contains both a linear component and a nonlinear component, the nonlinear component is a high harmonic component, which will affect the linearity of the output of the amplification circuit. In order to be able to offset the nonlinear component generated by the first N-type switch tube M1, the third N-type switch tube M3 and the fourth N-type switch tube M4 are connected in parallel between the source terminal and the drain terminal of the first N-type switch tube M1, and the third N-type switch tube M3 and the fourth N-type switch tube M4 jointly constitute a second common-source common-gate structure, wherein the third N-type switch tube M3 is a common-source structure, and the fourth N-type switch tube M4 is a common-gate structure. The third N-type switch tube M3 and the fourth N-type switch tube M4 are both in a weak inverse type region, the gate terminal of the third N-type switch tube M3 is very sensitive to the signal after receiving the first signal of the first N-type switch tube M1, under the transconductance of the third N-type switch tube M3, the drain terminal of the third N-type switch tube M3 can output a high harmonic component, i.e. a nonlinear component, the nonlinear component is input in the form of a compensation signal (the compensation signal is also a current signal) to the source terminal of the second N-type switch tube M2 through the drain terminal of the fourth N-type switch tube M4. At the source terminal of the second N-type switch tube M2, the second signal and the compensation signal are superimposed, the electrical property of the compensation signal is opposite to that of the second signal, the nonlinear component in the second signal is offset, and the nonlinear component in the second signal is offset and then enters the second N-type switch tube M2, and is further amplified by the second N-type switch tube M2 and then output in the form of a third signal.

[0052] It is worth mentioning that the gain unit 200 and the correction unit 300 disclosed above also have high reverse isolation. The input end of the gain unit 200 (i.e. the gate end of the first N-type switch tube M1) and the output end of the gain unit 200 (i.e. the drain end of the second N-type switch tube M2) are close to no signal coupling and interference, so that the input signal and the output signal do not interfere with each other, and the correction unit 300 is the same. With such a design, the stability and isolation of the amplification circuit can be enhanced, oscillation and interference can be prevented, and the integrity of the transmission signal can be improved. In addition, the third N-type switch tube M3 and the fourth N-type switch tube M4 have low conductivity in the weak reverse type region, and the current flowing through them is very small, so that when the compensation signal is generated, excessive interference and noise will not be generated, and the gain unit 200 will not be affected. Therefore, the linearity of the amplifier can be significantly improved without compromising the noise coefficient of the amplification circuit.

[0053] It should be noted that when analyzing the linear performance of the amplification circuit disclosed in the present application, the amplification circuit disclosed in the present application can be simplified as an equivalent circuit as shown in Figure 3 . Specifically, the equivalent transconductance of the first common source and gate structure composed of the first N-type switch tube M1 and the second N-type switch tube M2 in the saturation region is approximately equal to the transconductance of the first N-type switch tube M1, and the nonlinear component is introduced by the first N-type switch tube M1. The equivalent transconductance of the second common source and gate structure composed of the third N-type switch tube M3 and the fourth N-type switch tube M4 in the weak reverse type region is approximately equal to the transconductance of the third N-type switch tube M3, and the fourth N-type switch tube M4 is close to an open circuit state and has no effect on the load of the gain unit 200. For linear performance analysis, the gain unit 200 in the simplified circuit can be equivalent to the gate-source parasitic capacitance Cgs1 of the first N-type switch tube M1, and the correction unit 300 can be equivalent to the gate-source parasitic capacitance Cgs3 of the third N-type switch tube M3. The total current Itotal output by the simplified circuit is equal to the sum of the current output by the gain unit 200 and the current output by the correction unit 300.

[0054] In some embodiments, the source end of the first N-type switch tube M1 is connected to the ground through a negative feedback inductor LS. The negative feedback inductor LS can provide a virtual resistance component for the gate end of the first N-type switch tube M1 without adding additional noise, so as to reduce the noise caused by the fluctuation of the source current, effectively filter out the high-frequency noise signals that are not desired, and reduce the noise of the amplification circuit.

[0055] In order to control the first N-type switch tube M1 and the second N-type switch tube M2 to work in the saturation region, and the third N-type switch tube M3 and the fourth N-type switch tube M4 to work in the weak reverse type region, the amplification circuit further comprises a bias unit 500, which has a first transmission end, a second transmission end, a third transmission end and a fourth transmission end. The first transmission end is connected with the gate end of the first N-type switch tube M1, and is used for controlling the voltage of the gate end of the first N-type switch tube M1. The second transmission end is connected with the gate end of the second N-type switch tube M2, and is used for controlling the voltage of the gate end of the second N-type switch tube M2. The third transmission end is connected with the gate end of the third N-type switch tube M3, and is used for controlling the voltage of the gate end of the third N-type switch tube M3. The fourth transmission end is connected with the gate end of the fourth N-type switch tube M4, and is used for controlling the voltage of the gate end of the fourth N-type switch tube M4.

[0056] Further, the gain unit 200 further comprises a first capacitor C1 and a second capacitor C2. The first capacitor C1 is connected between the first output end and the gate end of the first N-type switch tube M1. The second capacitor C2 is connected between the first transmission end and the connection path of the gate end of the second N-type switch tube M2 at one end, and is grounded at the other end. The first capacitor C1 can avoid the direct influence of the direct current bias in the signal output by the input impedance matching unit on the bias voltage of the first N-type switch tube M1. The second capacitor C2 can lead the high-frequency component in the alternating current signal received by the gate end of the second N-type switch tube M2 to the ground, so as to prevent the high-frequency noise or interference signal from being superimposed on the bias voltage of the second N-type switch tube M2, thereby stabilizing the gate voltage of the second N-type switch tube M2 and reducing the influence of noise interference on the circuit performance.

[0057] Similarly, the correction unit 300 further comprises a third capacitor C3 and a fourth capacitor C4. The third capacitor C3 is connected between the source end of the first N-type switch tube M1 and the gate end of the third N-type switch tube M3. The fourth capacitor C4 is connected between the fourth transmission end and the connection path of the gate end of the fourth N-type switch tube M4 at one end, and is grounded at the other end. The third capacitor C3 can avoid the direct influence of the direct current bias at the source end of the first N-type switch tube M1 on the bias voltage at the gate end of the third N-type switch tube M3. The fourth capacitor C4 can lead the high-frequency component in the alternating current signal received by the gate end of the fourth N-type switch tube M4 to the ground, so as to prevent the high-frequency noise or interference signal from being superimposed on the bias voltage of the fourth N-type switch tube M4, thereby stabilizing the gate voltage of the fourth N-type switch tube M4 and reducing the influence of noise interference on the circuit performance.

[0058] The output matching unit 400 includes a second matching inductor L7, a third matching inductor Ld, a second matching capacitor C6, and a third matching capacitor C5. The second matching capacitor C6 and the second matching inductor L7 are connected in series between the drain terminal of the second N-type transistor M2 and the output terminal of the amplification circuit. One end of the third matching inductor Ld is grounded, and the other end is connected between the drain terminal of the second N-type transistor M2 and the second matching capacitor C6. One end of the third matching capacitor C5 is grounded, and the other end is connected between the drain terminal of the second N-type transistor M2 and the second matching capacitor C6. The second matching inductor L7 and the second matching capacitor C6 form a series resonance network, which adjusts the impedance characteristics of the output terminal of the amplification circuit, ensures that the third signal output can be efficiently transmitted to the subsequent circuit (or load), and improves the power transmission efficiency of the output signal in the target frequency range. In the target operating frequency range (for example, 3.3 GHz to 4.2 GHz), the second matching inductor L7 and the second matching capacitor C6 can resonate to selectively enhance the frequency components within the signal bandwidth and suppress interference of other frequencies. The third matching inductor Ld can improve the output efficiency and power gain of the amplification circuit by adjusting the load impedance of the drain terminal of the second N-type transistor M2. The third matching capacitor C5 can realize the decoupling function of high-frequency signals, and by providing a low-impedance path, high-frequency noise components are introduced into the ground, thereby eliminating high-frequency interference in the output signal.

[0059] Further, the index for measuring the linearity of the amplification circuit is IIP3 (third-order intermodulation intercept point). The Volterra series can be used to derive IIP3 in the technical solution disclosed in the present application,

[0060]

[0061] wherein the larger IIP3 is, the higher the linearity is, and g m is the transconductance of the gain unit 200, which is an important parameter of the linear amplification capability in the circuit. ∈: nonlinear coefficient, representing the nonlinear distortion characteristics of the circuit. Z1(s): input impedance of the circuit. A1(s): gain factor of the third-order harmonic component. 6: correction factor, derived from the normalization processing of high-order harmonic components in the Volterra series derivation. As can be seen from the formula of IIP3, the size of IIP3 is determined by the relationship between g m , ∈, Z1(s), and A4(s). High g m improves the linear gain capability, and low ∈ and small A4(s) can reduce the nonlinear distortion of the transconductance amplification circuit and improve the linearity. The present application improves the transconductance of the gain unit 200 by the first N-type transistor M1 and the second N-type transistor M2, and improves the linear gain capability of the amplification circuit.

[0062] Further, ∈ = g 3m -g 2m2 / 3g 1m +g 3a n(s)|n(s)2,g 1m ,g 2m ,g 3m represent the linear, first-order and third-order transconductance characteristics of the gain unit 200, g 3a : the third-order transconductance component of the correction unit 300, which plays a role in compensating for nonlinearity (affected by the bias voltage of the gate terminal of the third N-type switch tube M3), n(s): a characteristic function calculated by the input signal and the circuit parameters, reflecting the influence of impedance, gain, and parasitic capacitance on the nonlinearity of the system. n(s) = sLs(g 1m +sC gs1 ) / 1+s 2 C gs3 L s . Therefore, the g 1m ,g 2m ,g 3m of the gain unit 200 determines the linear and nonlinear relationship of the transconductance amplification circuit, and the correction unit 300 can efficiently compensate for the nonlinear type through g3a. That is, the distortion part of the gain unit 200 in the amplification process can be corrected by the correction unit 300. Figures 4-7 , the simulation results of the gain performance of the amplification circuit disclosed in the present application when transmitting signals in the n77 frequency band (3.3GHz-4.2GHz) are shown in the following figure, Figure 4 , the gain performance of the amplification circuit disclosed in the present application is relatively stable, and has good gain performance in the range of 20-21.5dB, which can stabilize the amplification of the input signal. Figure 4 , the input impedance matching performance of the amplification circuit disclosed in the present application is shown in the following figure. In the wideband range, especially at the sideband frequency points of 3.4GHz and 4.1GHz, the impedance matching performance is good (S11 is less than -6dB), which indicates that the input end reflection loss of the amplification circuit disclosed in the present application is small. And the voltage standing wave ratio (VSWR) is less than 1.65, which indicates that the matching effect of the amplification circuit disclosed in the present application is good, which can reduce signal reflection and improve energy transmission efficiency. Figure 5 , the noise figure of the amplification circuit disclosed in the present application is less than 1.15dB. Figure 6 , the noise performance of the amplification circuit disclosed in the present application is shown in the following figure. The noise figure is less than 1.15dB, which indicates that the amplification circuit disclosed in the present application has low noise characteristics in the entire bandwidth, which helps to improve the signal-to-noise ratio (SNR) after signal amplification, and is suitable for high-performance communication systems. Figure 6 , the noise performance of the amplification circuit disclosed in the present application is less than 1.15dB. Figure 7A linear optimization performance graph of the amplifier circuit disclosed in the present application shows the change of the third-order intermodulation intercept point (IIP3) and the bias voltage Vb3 of the third N-type switch tube M3. The larger the IIP3, the better the linearity of the amplifier. When Vb3 is close to the threshold voltage (about 0.3V) of the third N-type switch tube M3, IIP3 reaches the optimal value. It is shown that the working voltage of the third N-type switch tube M3 is set in the weak inversion region in the present application, which can generate a compensation signal opposite to the nonlinear component of the gain unit 200, thereby minimizing the linear distortion.

[0063] At least one embodiment of the present application also provides an electronic device comprising any of the above disclosed amplifier circuits.

[0064] The technical features of the above embodiments can be combined in any manner. To make the description concise, all possible combinations of the technical features in the above embodiments are not described, but as long as the combinations of the technical features do not exist contradictions, they should be considered as the scope of the present application.

[0065] The above embodiments only express several implementation manners of the present application, and the description is specific and detailed, but it should not be understood as a limitation on the patent scope of the present application. It should be pointed out that for those skilled in the art, without departing from the concept of the present application, a number of modifications and improvements can be made, which are all within the protection scope of the present application. Therefore, the protection scope of the patent of the present application should be subject to the appended claims.

Claims

1. An amplification circuit, characterized by, The application relates to a gain unit and a gain control method thereof. The input matching unit is used for matching the impedance between the input end of the gain unit and a signal source, and has a signal receiving end for receiving a first signal and a first output end for outputting the first signal after impedance matching. The correction unit is used for receiving the first signal through the gain unit and performing negative cross-gain compensation on the first signal to generate a compensation signal containing a nonlinear component. The gain unit is used for receiving the first signal after impedance matching output by the input matching unit, performing cross-gain amplification on the first signal to generate a second signal, receiving the compensation signal, superimposing the compensation signal and the second signal and further amplifying the superimposed signal to generate and output a third signal, and the compensation signal and the second signal are electrically opposite. The output matching unit is used for matching the impedance between the output end of the gain unit and a load, performing impedance matching processing on the received third signal, and outputting the third signal after impedance matching processing. The first signal is a voltage form weak signal to be amplified, and the second signal, the compensation signal and the third signal are all in the form of current. The gain unit comprises a first N-type switch tube M1 and a second N-type switch tube M2, and the first N-type switch tube M1 and the second N-type switch tube M2 are both in the saturation region.

2. The amplification circuit according to claim 1, characterized by The gate end of the first N-type switch tube M1 is connected with the first output end, the source end of the first N-type switch tube M1 is grounded, the drain end of the first N-type switch tube M1 is connected with the source end of the second N-type switch tube M2, and the drain end of the second N-type switch tube M2 is connected with the input end of the output matching unit. The source end of the first N-type switch tube M1 is connected to the ground through a negative feedback inductor LS.

3. The amplification circuit of claim 2, wherein The correction unit comprises a third N-type switch tube M3 and a fourth N-type switch tube M4, and the third N-type switch tube M3 and the fourth N-type switch tube M4 are both in the weak reverse type region.

4. The amplification circuit of claim 3, wherein The gate end of the third N-type switch tube M3 is connected between the source end of the first N-type switch tube M1 and the negative feedback inductor LS, the source end of the third N-type switch tube M3 is grounded, the drain end of the third N-type switch tube M3 is connected with the source end of the fourth N-type switch tube M4, and the drain end of the fourth N-type switch tube M4 is connected between the drain end of the first N-type switch tube M1 and the source end of the second N-type switch tube M2. The bias unit has a first transmission end, a second transmission end, a third transmission end and a fourth transmission end.

5. The amplification circuit of claim 4, wherein, The first transmission end is connected with the gate end of the first N-type switch tube M1 and is used for controlling the voltage of the gate end of the first N-type switch tube M1. The second transmission end is connected with the gate end of the second N-type switch tube M2 and is used for controlling the voltage of the gate end of the second N-type switch tube M2. The third transmission end is connected with the source end of the third N-type switch tube M3 and is used for controlling the voltage of the source end of the third N-type switch tube M3. The fourth transmission end is connected with the source end of the fourth N-type switch tube M4 and is used for controlling the voltage of the source end of the fourth N-type switch tube M4. The third transmission end is connected with the gate end of the third N-type switch tube M3, for controlling the voltage of the gate end of the third N-type switch tube M3. The fourth transmission end is connected with the gate end of the fourth N-type switch tube M4, for controlling the voltage of the gate end of the fourth N-type switch tube M4.

6. The amplification circuit of claim 5, wherein, The gain unit further comprises a first capacitor C1 and a second capacitor C2, the first capacitor C1 is connected between the first output end and the gate end of the first N-type switch tube M1, and the second capacitor C2 is connected between the first transmission end and the gate end of the second N-type switch tube M2.

7. The amplification circuit of claim 5, wherein The correction unit further comprises a third capacitor C3 and a fourth capacitor C4, the third capacitor C3 is connected between the source end of the first N-type switch tube M1 and the gate end of the third N-type switch tube M3, and the fourth capacitor C4 is connected between the fourth transmission end and the gate end of the fourth N-type switch tube M4.

8. The amplification circuit of claim 1, wherein, The input matching unit comprises a first matching inductor Lin and a first matching capacitor Cin, one end of the first matching inductor Lin is connected with the signal receiving end, and the other end is connected with the first output end, and one end of the first matching capacitor Cin is connected between the first matching inductor Lin and the first output end, and the other end is grounded.

9. The amplification circuit of claim 2, wherein, The output matching unit comprises a second matching inductor L7, a third matching inductor Ld, a second matching capacitor C6 and a third matching capacitor C5, the second matching capacitor C6 and the second matching inductor L7 are connected in series between the drain end of the second N-type switch tube M2 and the output end of the amplification circuit, one end of the third matching inductor Ld is grounded, and the other end is connected between the drain end of the second N-type switch tube M2 and the second matching capacitor C6, one end of the third matching capacitor C5 is grounded, and the other end is connected between the drain end of the second N-type switch tube M2 and the second matching capacitor C6.

10. An electronic device, comprising: The amplification circuit comprises the amplification circuit according to any one of claims 1-9. The amplification circuit comprises the amplification circuit according to any one of claims 1-9.

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