Electronic device comprising converter circuit and control method therefor

Abstract

The present disclosure relates to an electronic device comprising a converter circuit for current balancing, and a control method therefor. The electronic device may comprise a plurality of half-bridge converters connected in parallel to share a resonance capacitor. The electronic device can control a first half bridge unit included in a first converter circuit and a second half bridge circuit included in a second converter unit such that the first converter circuit and the second converter unit can be sequentially started at a first time interval (td).

Description

Electronic device and control method including converter circuit

[0001] The present disclosure relates to an electronic device including a converter circuit for current balancing and a method of controlling the same.

[0002] With the recent advancement of electronic technology, various types of electronic devices are being developed and distributed.

[0003] As an example of a converter circuit applied to such electronic devices, a half bridge LLC resonant converter is widely used as a structure that enables zero voltage switching (ZVS) and high power efficiency.

[0004] For electronic devices requiring high power, at least two half-bridge LLC resonant converters can be connected in parallel. In this case, current balancing, i.e., the need for even current distribution among multiple LLC resonant converters, is required. While a load-sharing circuit can be used for current balancing, the increased volume and production cost associated with adding a load-sharing circuit often leads to the use of passive current balancing methods.

[0005] One embodiment of the present disclosure can provide a converter circuit that allows a plurality of resonant converters to be sequentially started at time intervals in an electronic device.

[0006] An electronic device according to one embodiment of the present disclosure may include a first converter circuit having a resonant capacitor, a first leakage inductor, and a first transformer, a second converter circuit connected in parallel with the first converter circuit to share the resonant capacitor, the second converter circuit including a second leakage inductor and a second transformer, and a control unit configured to control the start-up of the first converter circuit and the second converter circuit.

[0007] According to one embodiment, the control unit causes the first converter circuit and the second converter to operate at a first time interval (t d ) can be configured to control the first half-bridge section included in the first converter circuit and the second half-bridge section included in the second converter section so that they can be sequentially operated.

[0008] According to one embodiment of the present disclosure, by sequentially starting a plurality of resonant converters included in an electronic device, the inrush voltage applied to a leakage inductor can be reduced.

[0009] The technical problems to be achieved in the present disclosure are not limited to the technical problems mentioned above, and other technical problems not mentioned above can be derived from the exemplary embodiments of the present disclosure by a person having ordinary knowledge in the relevant technical field.

[0010] FIG. 1 illustrates the structure of a converter circuit according to one embodiment of the present disclosure.

[0011] FIG. 2 illustrates an equivalent circuit of the converter circuit illustrated in FIG. 1 according to one embodiment of the present disclosure.

[0012] FIG. 3a illustrates the structure of a converter circuit according to one embodiment of the present disclosure.

[0013] FIG. 3b illustrates the structure of a converter circuit according to one embodiment of the present disclosure.

[0014] FIGS. 4A and 4B illustrate equivalent circuits of the converter circuit illustrated in FIGS. 3A and 3B according to one embodiment of the present disclosure.

[0015] FIG. 5a and FIG. 5b are graphs illustrating an inrush current occurring in a leakage inductor according to one embodiment of the present disclosure.

[0016] FIG. 6 illustrates the structure of a soft starter for controlling a converter circuit according to one embodiment of the present disclosure.

[0017] FIG. 7 is a graph showing voltage at a point over time according to one embodiment of the present disclosure.

[0018] FIG. 8 illustrates the structure of a converter circuit according to one embodiment of the present disclosure.

[0019] In connection with the description of the drawings, the same or similar reference numerals may be used for identical or similar components.

[0020] Hereinafter, embodiments of the present disclosure will be described in detail with reference to the drawings so that those with ordinary skill in the art (hereinafter referred to as "skilled in the art") can easily implement the present disclosure. However, the present disclosure may be implemented in various different forms and is not limited to the embodiments described herein. In connection with the description of the drawings, the same or similar reference numerals may be used for the same or similar components. In addition, in the drawings and related descriptions, descriptions of well-known functions and configurations may be omitted for clarity and conciseness.

[0021] In various embodiments of this document, when a part is referred to as "including" a component, this does not mean that it excludes other components, but rather that it may include other components, unless otherwise specified. Furthermore, when this document refers to "connected," this means that it is electrically or physically connected, unless otherwise specified.

[0022] The converter circuit described below (e.g., converter circuit (10) of FIG. 1) is an example of a half-bridge LLC resonant converter circuit (hereinafter referred to as a converter for convenience of explanation) applied to implement a power supply included in an electronic device. When the electronic device requires high power, the resonant converters can be connected in parallel to implement the power supply. The current value output to the output terminals of the parallel-connected converters needs to be evenly distributed, i.e., current balancing needs to be satisfied. To this end, the current output to the output terminal can be detected.

[0023] For the current balancing described above, a method of implementing a converter circuit by connecting a load share circuit to each output terminal of a converter connected in parallel, or a method of implementing the converter circuit with a differential mode coupled resonant inductor structure may be proposed, but this may increase the production cost of the converter circuit or increase the volume of the converter circuit.

[0024] Therefore, to achieve current balancing without increasing production costs or volume, a converter structure that shares resonant capacitors can be proposed. The converter circuit (10) described below in this document illustrates an example of a half-bridge LLC converter structure that shares resonant capacitors.

[0025] Fig. 1 illustrates the structure of a converter circuit (10) according to one embodiment.

[0026] Referring to Fig. 1, the illustrated converter circuit (10) can be applied to various electronic devices. The electronic devices may include portable terminals, computers, tablet PCs, home appliances such as TVs, or automobiles. However, the present invention is not limited thereto and may include any type of electronic device having a power supply.

[0027] According to one embodiment, the converter circuit (10) may be included in a power supply. The power supply may include, for example, a switching mode power supply (SMPS).

[0028] According to one embodiment, the converter circuit (10) may be composed of a plurality of LLC resonant circuits connected in parallel. For example, the converter circuit (10) may include a first converter circuit (100) and a second converter circuit (100-2). The first converter circuit (100) and the second converter circuit (100-2) may be connected in parallel. Both the first converter circuit (100) and the second converter circuit (100-2) may be implemented as LLC resonant circuits.

[0029] According to one embodiment, the first converter circuit (100) and the second converter circuit (100-2) include a resonant capacitor (C r )(130) can be shared. For example, the input terminal A node (N) of the resonant capacitor (130) provided in the first converter circuit (100) A ) and output terminal B node (N B ) can be connected to the second converter circuit (100-2). This converter circuit (10) can be referred to as an “LLC converter circuit sharing a resonant capacitor,” but in this document, for the convenience of explanation, it is referred to as a converter circuit (10).

[0030] According to one embodiment, the first converter circuit (100) includes a first half-bridge section (half-bridge section #1) (110), a first leakage inductor (L lkg1 )(120), resonant capacitor (C r )(130), a first transformer (T1)(140) and a first rectifier (rectifier #1)(150). The inductance value of the first leakage inductor (120) is L lkg1 can be defined as. The capacitance value of the resonant capacitor (130) is C r can be defined as

[0031] According to one embodiment, the second converter circuit (100-2) includes a second half-bridge section (half-bridge section #2) (110-2), a second leakage inductor (L lkg2 )(120-2), a second transformer (T2)(140-2) and a second rectifier (150-2). The inductance value of the second leakage inductor (120-2) is L lkg2 can be defined as

[0032] According to one embodiment, the first and second half-bridge units (110, 110-2) may be implemented as a half-bridge circuit. The first and second half-bridge units (110, 110-2) may include two switching elements. Here, the switching elements may be implemented as transistors, and preferably, may be implemented as metal oxide semiconductor field effect transistors (MOSFETs). The two switching elements included in the first and second half-bridge units (110, 110-2) may be shorted (switch-on or connection) or opened (switch-off or disconnection). For example, one of the two switching elements may be shorted and the other may be open. For example, both of the two switching elements may be open. For example, both of the two switching elements may be shorted. The first and second half-bridge units (110, 110-2) can supply an output voltage in response to the turn-on or turn-off operation of two switching elements included therein. For example, the first and second half-bridge units (110, 110-2) can control a signal output from a power source at a predetermined duty ratio.

[0033] According to one embodiment, in order to control the operation of the switching elements included in the first and second half-bridge units (110, 110-2), the converter circuit (10) may include a control unit (e.g., the control unit (20) of FIG. 3A or 3B). The control unit (20) may output a signal for controlling the switching elements included in the first and second half-bridge units (110, 110-2) to be short-circuited or opened. The control unit (20) may sequentially operate the switching elements, thereby reducing the size of the inrush current generated in the converter circuit (10). In this regard, a description will be given below in FIG. 3A.

[0034] According to one embodiment, a first leakage inductor (120) may be present between one side of the first half-bridge unit (110) and a first transformer (140). An input terminal of the first leakage inductor (120) may be connected to one output terminal of the first half-bridge unit (110). A second leakage inductor (120-2) may be present between one side of the second half-bridge unit (110-2) and a second transformer (140-2). An input terminal of the second leakage inductor (120-2) may be connected to one output terminal of the second half-bridge unit (110-2). The first leakage inductor (120) may be generated due to the first transformer (140). The second leakage inductor (120-2) may be generated due to the second transformer unit (140-2). That is, the first and second leakage inductors (120, 120-2) may be generated due to the leakage flux of the first and second transformer sections (140, 140-2). A power signal may flow through the first and second leakage inductors (120, 120-2) and an inrush current may be generated. In relation to this, a description will be given below with reference to FIG. 2.

[0035] According to one embodiment, a resonant capacitor (130) may be connected between one side of the first half-bridge unit (110) and the first transformer (140). The resonant capacitor (130) may be connected between one side of the second half-bridge unit (110-2) and the second transformer (140-2). The input terminal (N) of the resonant capacitor (130) A ) can be connected to one output terminal of the first half bridge unit (110). The input terminal (N) of the resonant capacitor (130) A ) can be connected to one output terminal of the second half bridge section (110-2).

[0036] According to one embodiment, a first leakage inductor (120) and a resonant capacitor (130) may be connected to the input terminal of the first transformer (140). The first transformer (140) may step up or step down a signal transmitted from the first half-bridge unit (110) at a predetermined voltage ratio.

[0037] According to one embodiment, the first transformer (140) may include a first magnetizing inductor (141) and a first coil portion (143). The first coil portion (143) may include a primary coil and a secondary coil. The number of turns (p) of the primary coil included in the first coil portion (143) and the number of turns (q) of the secondary coil may have a predetermined turn ratio (p:q). The winding direction of the primary coil included in the first coil portion (143) and the winding direction of the secondary coil may be the same. The turn ratio n1 of the first transformer (140) may be derived as n1 = q / p. For example, the first transformer (140) may be assumed to be an ideal transformer.

[0038] According to one embodiment, a second leakage inductor (120-2) and a resonant capacitor (130) may be connected to the input terminal of the second transformer unit (140-2). The second transformer unit (140-2) may boost or lower the signal transmitted from the second half-bridge unit (110-2) at a predetermined voltage ratio.

[0039] According to one embodiment, the second transformer (140-2) may include a second magnetizing inductor (141-2) and a second coil portion (143-2). The second coil portion (143-2) may include a primary coil and a secondary coil. The number of turns (r) of the primary coil included in the second coil portion (143-2) and the number of turns (s) of the secondary coil may have a predetermined turns ratio (r:s). The winding direction of the primary coil included in the first coil portion (143) and the winding direction of the secondary coil may be the same. The turn ratio n2 of the first transformer (140) may be derived as n2 = s / r. For example, the second transformer (140-2) may be assumed to be an ideal transformer.

[0040] According to one embodiment, the turn ratio n1 of the first transformer (140) and the turn ratio n2 of the second transformer (140-2) may have the same value. However, the present invention is not limited thereto, and may have different values ​​depending on the design of the converter circuit (10). Hereinafter, in the present disclosure, it will be assumed that the turn ratio n1 of the first transformer (140) and the turn ratio n2 of the second transformer (140-2) have the same value. The first transformer (140) may have the same winding direction as the second transformer (140-2).

[0041] According to one embodiment, the first rectifier (150) may be connected to the secondary side of the first transformer (140). The second rectifier (150-2) may be connected to the secondary side of the second transformer (140-2). The first rectifier (150) may rectify the AC signal transformed from the first transformer (140) into a DC signal. The second rectifier (150-2) may rectify the AC signal transformed from the second transformer (140-2) into a DC signal.

[0042] According to one embodiment, the converter circuit (10) may include an electrolytic capacitor (160). The electrolytic capacitor (160) may be connected in parallel to a secondary output terminal of a first transformer (140) and a secondary output terminal of a second transformer (140-2). For example, one end (N5) of the electrolytic capacitor (160) may be connected to one end of a first rectifier (150) and one end of a second rectifier (150-2). For example, the other end (N6) of the electrolytic capacitor (160) may be connected to the other end of the first rectifier (150) and the other end of the second rectifier (150-2).

[0043] FIG. 2 illustrates an equivalent circuit of the converter circuit illustrated in FIG. 1 (e.g., the converter circuit (10) of FIG. 1), according to one embodiment.

[0044] Referring to Fig. 2, it can be understood that the equivalent circuit of some circuits included in part A shown in Fig. 1 is shown when the converter circuit (10) is initially driven. The converter circuit (10) is supplied with an input power supply (V in )(201) may be included.

[0045] According to one embodiment, the half-bridge section (210) included in the converter circuit (10) (e.g., the first and second half-bridge sections (110, 110-2) of FIG. 1) may include a predetermined switch circuit. The switch circuit may include at least two switching elements.

[0046] According to one embodiment, the half-bridge section (210) may include a first switching element (211) and a second switching element (213). The first switching element (211) and / or the second switching element (213) may be implemented as a MOSFET. The first and second switching elements (211, 213) may be connected in response to a gate signal having a voltage higher than a threshold level.

[0047] According to one embodiment, a voltage signal output from the input power source (201) in response to the connection of the first switching element (211) and a voltage signal output from the input power source (201) in response to the connection of the second switching element (213) may have a phase difference of 180°.

[0048] According to one embodiment, the first switching element (211) or the second switching element (213) may be input as a gate signal a control signal output from a control unit (e.g., the control unit (20) of FIG. 3), and may be opened or shorted in response to the gate signal.

[0049] According to one embodiment, the leakage inductor (220) is a first leakage inductor (221) (e.g., the first leakage inductor (L) of FIG. 1). lkg1 )(120)) and a second leakage inductor (223) (e.g., the second leakage inductor (L) of FIG. 1 lkg2 )(120-2)). The first leakage inductor (221) may correspond to the first leakage inductor (120) of Fig. 1, and the second leakage inductor (223) may correspond to the second leakage inductor (120-2) of Fig. 1.

[0050] According to one embodiment, the leakage inductor (220) in which the first leakage inductor (221) and the second leakage inductor (223) are connected in parallel on the equivalent circuit can be derived as a composite value of the first leakage inductor (221) and the second leakage inductor (223). Therefore, the inductance value L of the leakage inductor (220) is L = (L lkg1)*(L lkg2 ) / ((L lkg1 )+(L lkg2 )) can be derived. The above inductance value L is the inductance value L of the first leakage inductor (221). lkg1 Smaller, the inductance value L of the second leakage inductor (223) lkg2 It's smaller than.

[0051] According to one embodiment, the resonant capacitor (230) may correspond to the resonant capacitor (130) of FIG. 1.

[0052] According to one embodiment, the transformer (240) may correspond to the first transformer (140) or the second transformer (140-2) of FIG. 1. The transformer (240) may include a magnetizing inductor (241) (e.g., the first magnetizing inductor (141) or the second magnetizing inductor (141-2) of FIG. 1) and a transformer (243) (e.g., the first transformer (140) or the second transformer (140-2) of FIG. 1).

[0053] According to one embodiment, in the converter circuit (10) at the time of initial operation, the voltage value applied to the magnetizing inductor (241) and the resonant capacitor (230) may correspond to 0 V. Therefore, according to Kirchoff's voltage law (KVL), the voltage value applied to the leakage inductor (220) may be equal to the voltage of the input power source (201). At this time, the current value flowing through the leakage inductor (220), i.e., the inrush current, may have a larger value than when only one of the first leakage inductor (221) or the second leakage inductor (223) exists. This may have a negative effect on electrical components included in an electronic device or electrical components included in a power supply. Therefore, in the present disclosure, a control method for controlling an inrush current that occurs in an excessive size may be proposed.

[0054] FIGS. 3A and 3B illustrate the structure of a converter circuit (10) (e.g., the converter circuit (10) of FIG. 1) according to one embodiment. FIGS. 3A and 3B can be understood as a structure proposed to reduce the size of the inrush current occurring in FIGS. 1 and 2.

[0055] Referring to FIGS. 3a and 3b, the control unit (20) starts the resonant operation for a first time interval (t d ) can be controlled to start only the first converter circuit (100) included in the converter circuit (10) until the first time interval (t) elapses (see Fig. 3a). In this case, the first time interval (t d ) may not be started until the second converter circuit (100-2) included in the converter circuit (10) has elapsed. The control unit (20) may not start the first time interval (t) after starting the resonance operation. d ) can be controlled to start the second converter circuit (100-2) (see Fig. 3b). For example, the converter circuit (10) starts resonant operation and starts a first time interval (t d ) after the above-described first converter circuit (100) and the second converter circuit (100-2) can both be started. Hereinafter, the structure of the converter circuit (10) illustrated in FIGS. 3a and 3b may correspond to the converter circuit (100) illustrated in FIG. 1, and therefore, a duplicate description will be omitted. The first converter circuit (100) and the second converter circuit (100-2) may be connected in parallel to share a resonant capacitor (130).

[0056] According to one embodiment, the control unit (20) can output a control signal (gate signal A, gate signal B, gate signal A', and gate signal B') for controlling the operation of the converter circuit (10). In response to the control signal, the first converter circuit (100) and / or the second converter circuit (100-2) included in the converter circuit (10) can perform a resonance operation. For example, the control unit (20) can output a first time interval (t) after the resonance operation by the first converter circuit (100) is initiated. d ) can output a control signal so that the resonance operation by the second converter circuit (100-2) is initiated. For example, the control unit (20) can output a control signal so that the first converter circuit (100) and the second converter circuit (100-2) are operated at a first time interval (t d ) can be configured to sequentially operate the first half bridge unit (110) included in the first converter circuit (100) and the second half bridge unit (110-2) included in the second converter circuit (100-2).

[0057] The above control unit (20) can output a first control signal (e.g., gate signal A and gate signal B) for controlling the start-up of the first converter circuit (100) included in the converter circuit (10) when the resonance operation starts (see FIG. 3a). The first control signal (gate signal A and gate signal B) can control the switching operation of the first half-bridge unit (110) included in the first converter circuit (100).

[0058] The above control unit (20) starts the resonance operation of the first converter circuit (100) after a first time interval (t d) has elapsed, a second control signal (gate signal A' and gate signal B') for controlling the start-up of the second converter circuit (100-2) included in the converter circuit (10) can be output (see FIG. 3b). The second control signal (gate signal A' and gate signal B') can control the switching operation of the second half-bridge unit (110-2) included in the second converter circuit (100-2).

[0059] According to one embodiment, the first control signal (e.g., gate signal A and gate signal B) output by the control unit (20) may be supplied as a switching control signal for turning on or off the switching elements (e.g., first switching element (111) and second switching element (113)) included in the first half-bridge unit (110). For example, the first control signal may include gate signal A and gate signal B. The gate signal A may be supplied as a switching control signal for turning on or off the first switching element (111) included in the first half-bridge unit (110). The gate signal A may be supplied, for example, to a gate terminal (Q1) of a first switching element (111) so that the first switching element (111) may be turned on (connected or shorted) or turned off (opened or opened). The gate signal B (Gate B) may be supplied as a switching control signal for turning on or off a second switching element (113) included in the first half-bridge unit (110). The gate signal B may be supplied, for example, to a gate terminal (Q2) of a second switching element (113) so that the second switching element (113) may be turned on (connected or shorted) or turned off (opened or opened). The switching control signal for turning on or off the first or second switching element (111, 113) may also be referred to as a first gate signal.

[0060] According to one embodiment, the second control signal (e.g., gate signal A' and gate signal B') output by the control unit (20) may be supplied as a switching control signal for turning on or off the switching elements (e.g., the third switching element (111-2), the fourth switching element (113-2)) included in the second half-bridge unit (110-2). For example, the second control signal may include the third gate signal, gate signal A', and the fourth gate signal, gate signal B'. The gate signal A' may be supplied as a switching control signal for turning on or off the third switching element (111-2) included in the second half-bridge unit (110-2). The above gate signal A' is supplied, for example, to the gate terminal (Q3) of the third switching element (111-2) so that the third switching element (111-2) can be turned on (connected or shorted) or turned off (opened or opened). The above gate signal B' (Gate B') can be supplied as a switching control signal for turning on or off the fourth switching element (113-2) included in the second half-bridge unit (110-2). The above gate signal B' is supplied, for example, to the gate terminal (Q4) of the fourth switching element (113-2) so that the fourth switching element (113-2) can be turned on (connected or shorted) or turned off (opened or opened). The switching control signal for turning on or off the third or fourth switching element (111-2, 113-2) may also be referred to as a second gate signal.

[0061] According to one embodiment, the control unit (20) outputs a first gate signal (gate signal A and gate signal B) for connecting the first switching element (111) and the second switching element (113), and outputs a first gate signal (gate signal A and gate signal B) for a predetermined time interval (e.g., a first time interval (t d)) Afterwards, the second gate signal (gate signal A' and gate signal B') for connecting the third switching element (111-2) and the fourth switching element (113-2) can be output. The first gate signal and the second gate signal can be output at a predetermined time interval, which is a delay time (t d ) is output to reduce the inrush current generated in the leakage inductor (120, 120-2) in response to the start-up of the half-bridge section (110, 110-2). The delay time (t d ) can correspond to several milliseconds. However, it is not limited to this and can have various values ​​depending on the settings.

[0062] According to one embodiment, the control unit (20) may include a soft starter (e.g., the soft starter (300) of FIG. 6). The soft starter (300) may be configured to start a first time interval (t) after a first gate signal (gate signal A and gate signal B) for switching operation of the first half-bridge unit (110) is input. d ) can be configured to output a second gate signal (gate signal A' and gate signal B') for the switching operation of the second half bridge unit (110-2) in response to the passage of time. In this regard, it will be described in detail with reference to FIG. 6.

[0063] FIGS. 4a and 4b illustrate equivalent circuits when the converter circuit (10) illustrated in FIGS. 3a and 3b is started, according to one embodiment.

[0064] Referring to FIGS. 4a and 4b, FIG. 4a illustrates an equivalent circuit when the converter circuit (10) illustrated in FIG. 3a is initially started, and FIG. 4b illustrates an equivalent circuit when the converter circuit (10) illustrated in FIG. 3b is initially started. The equivalent circuits illustrated in FIGS. 4a and 4b may correspond in part or in whole to the equivalent circuit illustrated in FIG. 2, and therefore, overlapping descriptions will be omitted, and descriptions will be focused on differences.

[0065] According to one embodiment, FIG. 4A illustrates an equivalent circuit when the first switching element (211) operates in a first state during initial startup. The first state may correspond to, for example, an operating state in which the first switching element (111) and the second switching element (113) of FIG. 3A are turned on, and the third switching element (111-2) and the fourth switching element (113-2) are turned off. When the first switching element (211) operates in the first state, it can be understood that only the first leakage inductor (120) of FIG. 3A exists as the leakage inductor (221), and only the first magnetizing inductor (141) of FIG. 3A exists as the magnetizing inductor (241).

[0066] According to one embodiment, the voltage across the resonant capacitor (230) and the transformer (240) in FIG. 4a may be 0 V. By Kirchhoff's voltage law, the voltage across the first leakage inductor (221) is V in It can be derived as follows. The inductance value L of the first leakage inductor (221) lkg1 is the value of inductance L in Fig. 2 lkg2 Since it is larger, it can be deduced that the size of the inrush current occurring in the first leakage inductor (221) is reduced compared to that in Fig. 2.

[0067] According to one embodiment, FIG. 4b illustrates an equivalent circuit in a case where the first switching element (211) operates in a second state after a predetermined time has elapsed after the initial startup. The second state may correspond, for example, to an operating state in which the first switching element (111) and the second switching element (113) of FIG. 3a are turned on, and the third switching element (111-2) and the fourth switching element (113-2) are also turned on. When the first switching element (211) operates in the second state, the leakage inductor (221, 223) can be understood as the first leakage inductor (120) and the second leakage inductor (120-2) of FIG. 3b connected in parallel, and the magnetizing inductor (241, 241-2) can be understood as the first magnetizing inductor (141) and the second magnetizing inductor (141-2) of FIG. 3b connected in parallel.

[0068] In one embodiment, after initial startup, a delay time (t d ) corresponding to the passage of time, the voltage V(T) applied to the transformer (240) is equal to the output voltage (V o ) is multiplied by the turn ratio (n) (e.g. n1 or n2 in Fig. 1), V(T)=n*V o The voltage can be applied as much as the delay time (t d ) in response to the passage of time, the voltage V(C) applied to the resonant capacitor (230) r ) is practically V(C r )=(1 / 2)*(V in )±α voltage can be applied. This can be understood as the duty ratio of the half bridge unit (210) is set to 0.5, so that half of the voltage Vin of the input power source (201) is output, and the AC signal of the input power source (201) increases or decreases by α. Here, α is (1 / 2)*(V in ) can correspond to a substantially very small value compared to the resonant capacitor (230). Therefore, the voltage V(C) applied to the resonant capacitor (230) r) is V(C r )=(1 / 2)*(V in ) can be expressed as.

[0069] According to one embodiment, by Kirchhoff's voltage law, the voltage V(L) applied to the first leakage inductor (221) and the second leakage inductor (223) connected in parallel lkg ) is V(L lkg )=(1 / 2)*Vin-(n*V o ) can be derived. The voltage V(L lkg ) is smaller than the voltage applied to the first leakage inductor (221) of (a), so that the size of the inrush current generated in the leakage inductor (221, 223) can be reduced as both the first converter circuit (e.g., the first converter circuit (100) of FIG. 1) and the second converter circuit (e.g., the second converter circuit (100-2) of FIG. 1) are started.

[0070] FIGS. 5A and 5B are graphs illustrating an inrush current occurring in a leakage inductor (e.g., the leakage inductor (220) of FIG. 2 or the first and second leakage inductors (221, 223) of FIG. 4) according to one embodiment. FIG. 5A is a graph illustrating an inrush current occurring in a leakage inductor (e.g., the leakage inductor (220) of FIG. 2) in the equivalent circuit of FIG. 2, and FIG. 5B may be understood as a graph illustrating an inrush current occurring in a leakage inductor (e.g., the first leakage inductor (221) or the second leakage inductor (223) of FIG. 4) in the equivalent circuit of FIGS. 4A and 4B.

[0071] Referring to FIGS. 5a and 5b, the numerical values ​​of the current shown represent an experimental example for explaining the reduction of the inrush current according to one embodiment, and the numerical values ​​may vary depending on the configuration of the circuit.

[0072] According to one embodiment, in the graph of FIG. 5a, at time point t onPreviously, neither the first converter (e.g., the first converter circuit (100) of Fig. 1) nor the second converter (e.g., the second converter circuit (100-2) of Fig. 1) was started, but at time t on In , both the first converter circuit (100) and the second converter circuit (100-2) can be started.

[0073] According to one embodiment, at time t on In , the first converter circuit (100) and the second converter circuit (100-2) can be started. The first converter circuit (100) and the second converter circuit (100-2) can be started by a control unit (e.g., the control unit (20) of FIG. 3).

[0074] According to one embodiment, at time t on In response to the activation of the first converter circuit (100) and the second converter circuit (100-2), an inrush current may be generated in the first leakage inductor (120) and the second leakage inductor (120-2). The maximum value (I) of the inrush current generated in the first leakage inductor (120) Lr1, max ) is 8.62A, and the maximum value (I) of the inrush current generated in the second leakage inductor (120-2) Lr2, max ) can be 8.77 A. The maximum value of this inrush current is the voltage applied to the first leakage inductor (120) and the second leakage inductor (120-2) in Fig. 2, which is the voltage value V output by the input power source (e.g., the input power source (201) in Fig. 2). in can be derived accordingly.

[0075] According to one embodiment, in the graph of FIG. 5b, before time t1, neither the first converter (e.g., the first converter circuit (100) of FIG. 1) nor the second converter (e.g., the second converter circuit (100-2) of FIG. 1) is started, and at time t1, the first converter circuit (100) is started, the second converter circuit (100-2) is not started, and at time t2, both the first converter circuit (100) and the second converter circuit (100-2) may be started. The time interval between time t1 and time t2 may be referred to as a delay time (t d- )(e.g. delay time (t) of Figs. 3a and 3b d )) can be said.

[0076] According to one embodiment, at time t1, in response to the first converter circuit (100) being started, an inrush current may be generated in the first leakage inductor (120). The maximum value (I) of the inrush current generated in the first leakage inductor (120) Lr1, max ) can be 5.59A. This can be understood as a decrease in inrush current compared to Fig. 5a.

[0077] According to one embodiment, at time t2, in response to the second converter circuit (100-2) being started, an inrush current may be generated in the first leakage inductor (120) and the second leakage inductor (120-2). The maximum value (I) of the inrush current generated in the second leakage inductor (120-2) Lr2, max ) can be 5.22A. This can be understood as a decrease in inrush current compared to Fig. 5a.

[0078] According to one embodiment, the inrush current can be reduced by sequentially starting the first converter circuit (100) and the second converter circuit (100-2).

[0079] FIG. 6 illustrates the structure of a soft starter (300) configured to control the start-up of a converter circuit (e.g., converter circuit (10) of 3a of FIG. 1) according to one embodiment. The soft starter (300) starts a first converter circuit (e.g., first converter circuit (100) of FIG. 3a) and starts a predetermined time (e.g., first time interval (t d ) or delay time (t d )) can be defined as a circuit for starting the second converter circuit (e.g., the second converter circuit (100-2) of FIG. 3a) after the passage of time.

[0080] Referring to FIG. 6, the soft starter (300) may be configured by combining at least some passive components (e.g., resistors, capacitors) and switching components (e.g., diodes, transistors). The soft starter (300) is not limited to that illustrated, and some electrical components may be changed to perform the same function.

[0081] According to one embodiment, the soft starter (300) may include a driving unit (310), a first element unit (320), a second element unit (330), or a switch unit. The first element unit (320) may be configured to initiate a first time interval (t) in response to charging / discharging by a supply voltage. d ) can be configured to perform a switching operation. The supply voltage may be a voltage supplied by the driving unit (310). The second element unit (330) may be switched on at a first time interval (t d) may be configured to generate a first switching signal in response to the operation of the first element unit (320) being turned on. The switch unit may be configured to input a first control signal (gate signal A and gate signal B) from a control unit (e.g., control unit (20) of FIG. 3A or 3B) and output a second control signal (gate signal A' and gate signal B') in response to the first switching signal. For example, the switch unit may include two switch elements (e.g., switching element A (341) and switching element B (343)). The first switching element (Q1) corresponding to the switching element A (341) may be configured to be turned on or off by a first gate signal (gate signal A), which is one of the first control signals. The second switching element (Q2) corresponding to the above switching element A (341) can be configured to be turned on or off by a second gate signal (gate signal B), which is one of the first control signals.

[0082] According to one embodiment, the soft starter (300) may include a third element (350) positioned between the output terminal of the switching element A (341) and the ground terminal. The third element (350) may be a circuit positioned between the output terminal of the switching element A (341) and the ground terminal, and may be a circuit in which one resistor (R5) (351) and one capacitor (C1) (353) are connected in parallel. The soft starter (300) may include a fourth element (360) positioned between the output terminal of the switching element B (343) and the ground terminal. The fourth element (360) may be a circuit in which one resistor (R6) (361) and one capacitor (C2) (363) are connected in parallel.

[0083] According to one embodiment, the driving unit (310) may be connected to the first element unit (320). The first element unit (320) may be connected to the second element unit (330). The second element unit (330) may be connected to the gate terminal of the switching element A (341). The second element unit (330) may be connected to the gate terminal of the switching element B (343). The drain terminal of the switching element A (341) may be connected to the third element unit (350). The drain terminal of the switching element B (343) may be connected to the fourth element unit (360).

[0084] According to one embodiment, the driving unit (310) can supply an operating voltage for driving the soft starter (300). The driving unit (310) can be connected to a control unit (e.g., the control unit (20) of FIG. 3A). The driving unit (310) can output an operating voltage, which is a signal having a predetermined level, to the soft starter (300).

[0085] According to one embodiment, a control signal that connects the first and second switching elements (111, 113) may be output to the gate terminal (Q1) of the first switching element (e.g., the first switching element (111) of FIG. 3A) and the gate terminal (Q2) of the second switching element (e.g., the second switching element (113) of FIG. 3A) included in the first converter circuit (100) in response to the voltage intensity of the signal output by the driving unit (310). As a result, a gate signal A may be output to the gate terminal (Q1) of the first switching element (111), and a gate signal B may be output to the gate terminal (Q2) of the second switching element (113). The gate signal A and the gate signal B may have a phase difference of 180°.

[0086] For example, the threshold voltage of the gate signal output by the driving unit (310) to connect the first and second switching elements (111, 113) can be defined as the first threshold driving voltage.

[0087] According to one embodiment, a control signal can be output to connect the third and fourth switching elements (111-2, 113-2) to the gate terminal (Q3) of the third switching element (e.g., the third switching element (111-2) of FIG. 3A) and the gate terminal (Q4) of the fourth switching element (e.g., the fourth switching element (113-2) of FIG. 3A) included in the first converter circuit (100) in response to the voltage intensity of the signal output by the driving unit (310).

[0088] For example, the threshold voltage of the gate signal output by the driving unit (310) to connect the third and fourth switching elements (111-2, 113-2) can be defined as the second threshold driving voltage.

[0089] Hereinafter, the signal processing operation of the circuit for connecting the first and second switching elements (111, 113) and, after a predetermined time has elapsed, connecting the third and fourth switching elements (111-2, 113-2) will be described.

[0090] According to one embodiment, the first element (320) may be connected to the output terminal of the driving unit (310). The first element (320) may be connected to a capacitor (C ss )(321) and a diode (323). The diode (323) may be implemented as a zener diode (or a constant voltage diode), but is not limited thereto. The capacitor (C ss )(321) may be provided to connect between the driving unit (310) to which the supply voltage is input and the ground. The capacitor (C ss )(321) can charge or discharge a predetermined voltage by the operating voltage supplied from the driving unit (310). The diode (323) is connected to the capacitor (C ss )(321) can perform a switching operation in response to the charging / discharging. For example, the diode (323) can be operated by the operating voltage supplied by the driving unit (310) or the capacitor (Css )(321) can be turned on by the voltage discharged to form a ground path of the second element (330).

[0091] According to one embodiment, the second element (330) is a collector voltage (V cc )(331), a first resistor (R1)(332), a second resistor (R2)(334), a transistor (333), a third resistor (R3)(335), and a fourth resistor (R4)(336). The transistor (333) may be implemented as a PNP transistor. The transistor (333) may perform the function of a switching element. The transistor (333) may have a source terminal connected to a collector voltage (collector voltage, V cc )(331), the gate terminal may be connected to the first element (320) through the second resistor (334), and the drain terminal may be connected to the gate terminals of the switching element A (341) and the switching element B (343) through the third resistor (335). The first resistor (332) may be connected between the gate terminal and the source terminal of the transistor (333). The fourth storage (336) may be connected between the output terminal to be connected to the gate terminals of the switching element A (341) and the switching element B (343) among the terminals on both sides of the third resistor (335) and the ground.

[0092] According to one embodiment, the switching element A (341) can output one of the first control signals, the gate signal A, as one of the second control signals, the gate signal A', in response to a switching signal output from the second element unit (330).

[0093] According to one embodiment, the switching element B (343) can output one of the first control signals, the gate signal B, as one of the second control signals, the gate signal B', in response to a switching signal output from the second element unit (330).

[0094] According to one embodiment, the driving unit (310) can output a signal having a certain level of voltage. The driving unit (310) can be implemented as an integral part of the control unit (e.g., the control unit (20) of FIG. 3A) or can be implemented as a separate configuration. When the driving unit (310) is implemented as a separate configuration from the control unit (20), the output terminal of the control unit (20) and the input terminal of the driving unit (310) can be connected. The signal output from the driving unit (310) can be transmitted to the switching element A (341) and the switching element B (343) via the first element unit (320) and the second element unit (330).

[0095] According to one embodiment, when a signal having a voltage higher than a threshold level is output from the driving unit (310), the signal may be output to the second element unit (330).

[0096] According to one embodiment, the second element unit (330) may output a voltage by a collector power supply (331) to the switching element A (341) and the switching element B (343) in response to a signal having a voltage higher than a threshold level being input from the first element unit (320). The switching element A (341) and the switching element B (343) may be connected based on the collector signal. In response to the connection of the switching element A (341) and the switching element B (343), a gate signal A' may be input to the gate terminal (Q3) of the third switching element (111-2), and a gate signal B' may be input to the gate terminal (Q4) of the fourth switching element (113-2). The gate signal A' and the gate signal B' may have a phase difference of 180°.

[0097] According to one embodiment, the gate signal A' is delayed by a delay time (t) compared to the gate signal A d ) can be delayed by the gate signal B' compared to the gate signal B by the delay time (t d) may be delayed. Due to this, after the first converter circuit (100) is started, the delay time (t d ) can be elapsed and the second converter circuit (100-2) can be started, and the inrush current generated in the leakage inductor (e.g., the leakage inductor (221, 223) of FIG. 4) can be reduced.

[0098] Fig. 7 is a graph showing the voltage at a point of a soft starter (e.g., the soft starter (300) of Fig. 6) over time according to one embodiment. Fig. 7 shows a capacitor (321) (e.g., the capacitor (C) of Fig. 6) constituting the first element (320) of Fig. 6 (e.g., the first element (320) of Fig. 6) ss )(321)) voltage (V) applied to ss ) can be understood as a graph showing the

[0099] Referring to FIG. 7, a driving unit (e.g., driving unit (310) of FIG. 6) can output an operating voltage, which is a signal having a predetermined voltage, to the first element unit (320). As time passes, a voltage value applied to the capacitor (321) can increase. When the voltage value applied to the capacitor (321) exceeds a threshold value, a gate signal for connecting a third switching element (e.g., the third switching element (111-2) of FIG. 3b) and a fourth switching element (e.g., the fourth switching element (113-2) of FIG. 3b) can be output.

[0100] According to one embodiment, at time t1, a voltage of V1 may be applied to the capacitor (321). At time t1, the driving unit (310) may output a gate signal A and a gate signal B for connecting a first switching element (e.g., the first switching element (111) of FIG. 3A) and a second switching element (e.g., the second switching element (113) of FIG. 3A). When the gate terminal (Q1) of the first switching element (111) and the gate terminal (Q2) of the second switching element (113) receive the gate signal A and the gate signal B, the first switching element (111) and the second switching element (113) may be connected. In response to the connection of the first switching element (111) and the second switching element (113), the first converter circuit (e.g., the first converter circuit (100) of FIG. 1) may be started. The threshold voltage V1 at which the above first converter circuit (100) is started can be referred to as the first threshold driving voltage.

[0101] According to one embodiment, at a time point t2 after a delay time (td) has elapsed from a time point t1, a voltage of V2 may be applied to the capacitor (321). At the time point t2, the diode (323) of the first element unit (320) may be turned on so that the second element unit (330) may form a ground path. The voltage of the signal input to the second element unit (330) and the signal output from the collector power supply (331) may be input to the gate terminal of the switching element A (341) and the gate terminal of the switching element B (343). The voltage intensity of the signal may be a gate signal that controls to connect the switching element A (341) and the switching element B (343). The gate signal A' that controls to connect the switching element A (341) to connect the third switching element (e.g., the third switching element (111-2) of FIG. 3A) may be compared with the gate signal A by t dA delay of that amount may occur. The gate signal B' that controls the switching element B (343) to be connected to connect the fourth switching element (e.g., the fourth switching element (113-2) of FIG. 3a) is compared with the gate signal B d A delay of that amount may occur. The second converter circuit (100-2) can be started by the gate signal A' and the gate signal B'. The threshold voltage V2 at which the second converter circuit (100-2) is started can be referred to as a second threshold driving voltage.

[0102] According to one embodiment, the voltage intensity of the signal stored in the capacitor (321) in the driving unit (310) increases over time and may be saturated at a predetermined point in time. The intensity of the voltage saturated at the predetermined point in time is referred to as the saturated driving voltage (V sat ) can be said to be. For example, at time t3, V is applied to the capacitor (321). sat As much voltage can be applied. The above V1, V2, V sat The value of V1 <V2<V sat can have a relationship of . The intensity of the saturated voltage V sat is not limited to a specific voltage and may have various values ​​depending on the capacitance of the capacitor (321).

[0103] According to one embodiment, the first threshold driving voltage V1 and the second threshold driving voltage V2 are determined by a delay time t d can be set by considering the delay time t d In response to this lengthening or shortening, the first threshold driving voltage V1 and the second threshold driving voltage V2 can be set. The saturation driving voltage V sat The time point t3 at which the second critical driving voltage V2 is reached can be set to have a value after the time point t2 at which the second critical driving voltage V2 is reached.

[0104] Fig. 8 illustrates the structure of a converter circuit (10) according to one embodiment. Fig. 8 may be understood as illustrating an additional embodiment in which the converter circuit (10) is composed of n split converter circuits (100, 100-2, ……100-n).

[0105] Referring to FIG. 8, the converter circuit (10) may be configured to include at least three converter circuits. For example, in addition to the first converter circuit (100) and the second converter circuit (100-2), the converter circuit (10) may further include at least one converter circuit (e.g., at least one of the third converter circuit (100-3) to the n-th converter circuit (100-n)). That is, the converter circuit (10) may be configured with n split converter circuits. Here, n may be understood as a natural number greater than or equal to 3. Hereinafter, duplicate descriptions in FIGS. 1 to 7 will be omitted, and differences will be mainly described.

[0106] As an example, the third converter circuit may be connected in parallel with the first converter circuit (100) and / or the second converter circuit (100-2). In this case, the control unit (20) controls the second converter circuit (100-2) and the third converter circuit to be connected at a second time interval (t d ') can be configured to control the second half-bridge unit (110-2) included in the second converter circuit (100-2) and the third half-bridge unit included in the third converter circuit (100-n) so that they can be sequentially started. For example, the soft starter (soft starter (300) of FIG. 6) can control the second half-bridge unit (110-2) included in the second converter circuit (100-2) after the second control signal (gate signal A' and gate signal B') for the switching operation of the second half-bridge unit (110-2) is input, at the second time interval (t d ') can be configured to output a third control signal (gate signal A'' and gate signal B'') for switching operation of the third half-bridge section in response to the passage of time.

[0107] According to one embodiment, the nth converter circuit (100-n) may include a half-bridge section (110-n), a leakage inductor (120-n), a transformer (140-n), and a rectifier section (150-n). The nth converter circuit (100-n) may be connected in parallel with the first converter circuit (100), the second converter circuit (100-2), the third converter circuit (100-3), … … the n-1th converter circuit (100-(n-1)) so as to share a resonant capacitor (130) with other converter circuits (110, 110-2).

[0108] According to one embodiment, the output terminal of the nth converter circuit (100-n) and the electrolytic capacitor (160) may be connected. That is, the output terminal of the nth rectifier (150-n) included in the nth converter circuit (100-n) and the electrolytic capacitor (160) may be connected.

[0109] According to one embodiment, the half-bridge section (110-n) included in the n-th converter circuit (100-n) may include two switching elements (111-n, 113-n). The switching elements (111-n, 113-n) may include a (2n-1)th switching element (111-n) and a (2n)th switching element (113-n).

[0110] According to one embodiment, the control unit (20) (e.g., the control unit (20) of FIG. 3a) can sequentially activate the first to nth converter circuits (100, 100-2, ……100-n).

[0111] According to one embodiment, a soft starter (e.g., a soft starter (300) of FIG. 6) may be provided to sequentially start the first to nth converter circuits (100, 100-2, ……100-n). An input terminal of the soft starter (300) and an output terminal of a driving unit (e.g., a driving unit (310) of FIG. 6) may be connected. The output terminal of the soft starter (300) may be connected to a gate terminal provided in a switching element included in a half-bridge unit (110, 110-2, ……110-n) of a split converter circuit included in the converter circuit (10). The switching element included in the half-bridge unit (110, 110-2, ……110-n) may be connected in response to a voltage value of a signal output by the soft starter (300). By this, the first to nth converter circuits (100, 100-2, ……100-n) can be sequentially started.

[0112] For example, the control unit (20) can start the first converter circuit (100), and after a predetermined time has elapsed, start the second converter circuit (100-2). The control unit (e.g., the control unit (20) of FIG. 3A) can start the second converter circuit (100-2), and after a predetermined time has elapsed, start the third converter circuit (100-3). The control unit (20) can start the (n-1)th converter circuit (100-(n-1)), and after a predetermined time has elapsed, start the nth converter circuit (100-n). Although not described, the first to nth converter circuits (100, 100-2, ……100-n) included in the converter circuit (10) can be started without any order restrictions, and after a predetermined time has elapsed, another split converter circuit can be started. However, for convenience of explanation, this document assumes that the first to nth converter circuits (100, 100-2, …… 100-n) are sequentially started in ascending order.

[0113] According to one embodiment, when one converter circuit (e.g., a first converter circuit (100)) is started and another converter circuit (e.g., a second converter circuit (100-2)) is started after a predetermined time has elapsed, the predetermined time is referred to as a first time interval or a first delay time (t d1 ) can be defined as. When one converter circuit (e.g., the second converter circuit (100-2)) is started and another converter circuit (e.g., the third converter circuit (100-3)) is started after a predetermined time has elapsed, the predetermined time is referred to as the second time interval or the second delay time (t d2 ) can be defined as follows. When one converter circuit (e.g., the (n-1)th converter circuit (100-(n-1)) is started and another converter circuit (e.g., the nth converter circuit (100-n)) is started after a predetermined time has elapsed, the predetermined time is called the n-1th time interval or the n-1th delay time (t d(n-1) ) can be defined as follows.

[0114] According to one embodiment, the first to n-1th delay times (t d1 , t d2 , … … t d(n-1) ) may be several milliseconds. The first to n-1th delay times (t d1 , t d2 , … … t d(n-1) ) may be the same or different from each other. That is, the first to n-1th delay times (t d1 , t d2 , … … t d(n-1) ) may have the same time interval or different time intervals. The first to n-1th delay times (t d1 , t d2 , … … t d(n-1) ) At least two delay times may have the same time interval.

[0115] According to one embodiment, the control unit (20) sets the first to n-1th delay times (t d1 , t d2 , … … t d(n-1) ) can be sequentially started up according to the split converter circuits, thereby reducing the inrush current. Since the first to nth converter circuits (100, 100-2, ……100-n) are sequentially started up, the size of the inrush current occurring in the leakage inductor (120, 120-2, ……120-n) existing in the first to nth converter circuits (100, 100-2, ……100-n) can be reduced compared to the case where the first to nth converter circuits (100, 100-2, ……100-n) are started up simultaneously.

[0116] An electronic device (10) according to one embodiment of the present disclosure comprises a resonant capacitor (C r )(130), a second converter circuit (100-2) connected in parallel with the first converter circuit (100) to share the resonant capacitor (130), and a control unit (20) configured to control the start-up of the first converter circuit (100) and the second converter circuit (100-2). The control unit (20) controls the first converter circuit (100) and the second converter circuit (100-2) to start at a first time interval (t d ) can be configured to sequentially operate the first half bridge unit (110) included in the first converter circuit (100) and the second half bridge unit (110-2) included in the second converter circuit (100-2).

[0117] In an electronic device (10) according to one embodiment of the present disclosure, the first converter circuit (100) may include a first leakage inductor (120) and a first transformer (140), and the second converter circuit (100-2) may include a second leakage inductor (120-2) and a second transformer (140-2).

[0118] An electronic device (10) according to one embodiment of the present disclosure may include an electrolytic capacitor (160) connected in parallel to a secondary output terminal of the first transformer (140) and a secondary output terminal of the second transformer (140-2).

[0119] In an electronic device (10) according to one embodiment of the present disclosure, the control unit (20) inputs a first control signal (gate signal A and gate signal B) for a switching operation of the first half-bridge unit (110) and then, at the first time interval (t d ) may include a soft starter (300) configured to output a second control signal (gate signal A' and gate signal B') for the switching operation of the second half bridge section (110-2) in response to the passage of time.

[0120] In an electronic device (10) according to one embodiment of the present disclosure, the soft starter (300) responds to charging / discharging by the supply voltage at the first time interval (t d ) configured to perform a switching operation, the first element (320), the first time interval (t d ) and a second element unit (330) configured to generate a first switching signal in response to the operation of the first element unit (320) that is turned on, and a switch unit (341, 343) configured to input the first control signal (gate signal A and gate signal B) and output the second control signal (gate signal A' and gate signal B') in response to the first switching signal.

[0121] In an electronic device (10) according to one embodiment of the present disclosure, a first half-bridge unit (110) may include a first switching element (Q1) configured to be turned on or off by a first gate signal (gate signal A) which is one of the first control signals, and a second switching element (Q2) configured to be turned on or off by a second gate signal (gate signal B) which is one of the first control signals.

[0122] In an electronic device (10) according to one embodiment of the present disclosure, the second half-bridge unit (110-2) may include a third switching element (Q3) configured to be turned on or off by a third gate signal (gate signal A') which is one of the second control signals, and a fourth switching element (Q4) configured to be turned on or off by a fourth gate signal (gate signal B') which is one of the second control signals.

[0123] An electronic device (10) according to one embodiment of the present disclosure may include a third converter circuit (100-n) connected in parallel with the first converter circuit (100) to share the resonant capacitor (130). The control unit (20) controls the second converter circuit (100-2) and the third converter circuit (100-n) to be connected at a second time interval (t d ') can be configured to control the second half bridge unit (110-2) included in the second converter circuit (100-2) and the third half bridge unit (110-n) included in the third converter circuit (100-n) so that they can be sequentially operated.

[0124] In an electronic device (10) according to one embodiment of the present disclosure, the control unit (20) controls the first time interval (t d ) and the second time interval (t d ') can be configured to control the same value.

[0125] In an electronic device (10) according to one embodiment of the present disclosure, the control unit (20) controls the first time interval (t d ) and the second time interval (t d ') can be configured to control different values.

[0126] In an electronic device (10) according to one embodiment of the present disclosure, the control unit (20) inputs a second control signal (gate signal A' and gate signal B') for the switching operation of the second half-bridge unit (110-2) and then, at the second time interval (t d ') may include a soft starter (300) configured to output a third control signal (gate signal A'' and gate signal B'') for the switching operation of the third half bridge section (110-n) in response to the passage of time.

[0127] In an electronic device (10) according to one embodiment of the present disclosure, the soft starter (300) responds to charging / discharging by the supply voltage at the second time interval (t d '), the third element (320) configured to perform a switching operation, the second time interval (t d ') and a fourth element unit (330) configured to generate a second switching signal in response to the operation of the first element unit (320) that is turned on, and a switch unit (341, 343) configured to input the second control signal (gate signal A' and gate signal B') and output the third control signal (gate signal A'' and gate signal B'') in response to the second switching signal.

[0128] In an electronic device (10) according to one embodiment of the present disclosure, the third half-bridge unit (110-n) includes a fifth switching element (Q) configured to be turned on or off by a fifth gate signal (gate signal A''), which is one of the third control signals. 2n-1 ) and a sixth switching element (Q) configured to be turned on or off by a sixth gate signal (gate signal B'') which is one of the third control signals. 2n ) may be included.

[0129] In an electronic device (10) according to one embodiment of the present disclosure, the first element (320) includes a first capacitor (C) provided between a terminal to which the supply voltage is input and ground. ss )(321) and the first capacitor (C ss )(321) may include a seventh switching element (323) configured to switch in response to charging / discharging.

[0130] In an electronic device (10) according to one embodiment of the present disclosure, the first element (320) includes a first capacitor (C) provided between a terminal to which the supply voltage is input and ground. ss )(321) and the first capacitor (C ss )(321) may include a seventh switching element (323) configured to switch in response to charging / discharging.

[0131] In an electronic device (10) according to one embodiment of the present disclosure, the second element unit (330) may include an eighth switching element (333) configured to output the first switching signal in response to the turn-on of the seventh switching element (323).

[0132] In an electronic device (10) according to one embodiment of the present disclosure, one resistor and one capacitor may be connected in parallel between the output terminal and the ground terminal of the switch unit (341, 343) from which the second control signal (gate signal A' and gate signal B') is output.

[0133] The various embodiments of this document and the terminology used therein are not intended to limit the technical features described in this document to specific embodiments, but should be understood to include various modifications, equivalents, or substitutes of the embodiments. In connection with the description of the drawings, similar reference numerals may be used for similar or related components. The singular form of a noun corresponding to an item may include one or more of the items, unless the context clearly indicates otherwise. In this document, each of the phrases “A or B,” “at least one of A and B,” “at least one of A or B,” “A, B, or C,” “at least one of A, B, and C,” and “at least one of A, B, or C” may include any one of the items listed together in the corresponding phrase among those phrases, or all possible combinations thereof. Terms such as “first,” “second,” or “first” or “second” may be used merely to distinguish one component from another, and do not limit the components in any other respect (e.g., importance or order). When a component (e.g., a first component) is referred to as “coupled” or “connected” to another component (e.g., a second component), with or without the terms “functionally” or “communicatively,” it means that the component can be connected to the other component directly (e.g., wired), wirelessly, or through a third component.

[0134] The term "module" used in various embodiments of this document may include a unit implemented in hardware, software, or firmware, and may be used interchangeably with terms such as logic, logic block, component, or circuit. A module may be an integral component, or a minimum unit or part of such a component that performs one or more functions. For example, according to one embodiment, a module may be implemented in the form of an application-specific integrated circuit (ASIC).

[0135] Various embodiments of this document may be implemented as software (e.g., a program) including one or more instructions stored in a storage medium (e.g., internal memory or external memory) that can be read by a machine. For example, a processor of the machine may call at least one instruction among the one or more instructions stored from the storage medium and execute it. This enables the machine to operate to perform at least one function according to the at least one instruction called. The one or more instructions may include code generated by a compiler or code that can be executed by an interpreter. The machine-readable storage medium may be provided in the form of a non-transitory storage medium. Here, 'non-transitory' only means that the storage medium is a tangible device and does not contain a signal (e.g., electromagnetic waves), and this term does not distinguish between cases where data is stored semi-permanently and cases where it is stored temporarily in the storage medium.

[0136] According to one embodiment, the method according to various embodiments disclosed in this document may be provided as included in a computer program product. The computer program product may be traded as a product between a seller and a buyer. The computer program product may be distributed in the form of a machine-readable storage medium (e.g., compact disc read-only memory (CD-ROM)), or may be distributed online (e.g., downloaded or uploaded) through an application store (e.g., Play Store™) or directly between two user devices (e.g., smart phones). In the case of online distribution, at least a portion of the computer program product may be temporarily stored or temporarily generated in a machine-readable storage medium, such as the memory of a manufacturer's server, an application store's server, or an intermediary server.

[0137] According to various embodiments, each component (e.g., a module or a program) of the above-described components may include one or more entities, and some of the entities may be separated and placed in other components. According to various embodiments, one or more components or operations of the aforementioned components may be omitted, or one or more other components or operations may be added. Alternatively or additionally, a plurality of components (e.g., a module or a program) may be integrated into a single component. In such a case, the integrated component may perform one or more functions of each of the plurality of components identically or similarly to those performed by the corresponding component among the plurality of components prior to the integration. According to various embodiments, the operations performed by a module, program, or other component may be executed sequentially, in parallel, iteratively, or heuristically, or one or more of the operations may be executed in a different order, omitted, or one or more other operations may be added.

Claims

1. In an electronic device (10), Resonant capacitor (C r )(130), a first converter circuit (100) including a first leakage inductor (12) and a first transformer (140); A second converter circuit (100-2) connected in parallel with the first converter circuit (100) to share the resonant capacitor (130) and including a second leakage inductor (120-2) and a second transformer (140-2); and It includes a control unit (20) configured to control the operation of the first converter circuit (100) and the second converter circuit (100-2), The above control unit (20) The first converter circuit (100) and the second converter circuit (100-2) are connected at a first time interval (t d ) and is configured to control the first half-bridge unit (110) included in the first converter circuit (100) and the second half-bridge unit (110-2) included in the second converter circuit (100-2) to sequentially operate.

2. In paragraph 1, An electronic device (10) including an electrolytic capacitor (160) connected in parallel to the secondary output terminal of the first transformer (140) and the secondary output terminal of the second transformer (140-2).

3. In paragraph 1, The above control unit (20) After the first control signal (gate signal A and gate signal B) for the switching operation of the first half bridge section (110) is input, the first time interval (t d ) is configured to output a second control signal (gate signal A' and gate signal B') for switching operation of the second half-bridge section (110-2) in response to the passage of time.

4. In paragraph 3, The above soft starter (300) is In response to the charge / discharge by the supply voltage, the first time interval (t d ) configured to perform a switching operation; The first time interval (t) above d ) configured to generate a first switching signal in response to the operation of the first element (320) being turned on; and An electronic device (10) including a switching unit (341, 343) configured to input the first control signal (gate signal A and gate signal B) and output the second control signal (gate signal A' and gate signal B') in response to the first switching signal.

5. In any one of paragraphs 1 to 3, The above first half bridge section (110) is A first switching element (Q) configured to be turned on or off by a first gate signal (gate signal A), which is one of the first control signals 1 ); and A second switching element (Q) configured to be turned on or off by a second gate signal (gate signal B), which is one of the first control signals 2 ) comprising an electronic device (10).

6. In any one of paragraphs 1 to 3, The above second half bridge section (110-2) is A third switching element (Q) configured to be turned on or off by a third gate signal (gate signal A'), which is one of the second control signals 3 ); and A fourth switching element (Q) configured to be turned on or off by a fourth gate signal (gate signal B'), which is one of the second control signals 4 ) comprising an electronic device (10).

7. In any one of paragraphs 1 to 6, A third converter circuit (100-n) is connected in parallel with the first converter circuit (100) to share the resonant capacitor (130). The above control unit (20) The second converter circuit (100-2) and the third converter circuit (100-n) are connected at a second time interval (t d An electronic device (10) configured to control the second half-bridge unit (110-2) included in the second converter circuit (100-2) and the third half-bridge unit (110-n) included in the third converter circuit (100-n) so as to sequentially operate the second half-bridge unit (110-2) included in the second converter circuit (100-2).

8. In paragraph 1 or paragraph 7, The above control unit (20) The first time interval (t) above d ) and the second time interval (t d An electronic device (10) configured to control two inputs (') to the same value.

9. In paragraph 1 or paragraph 7, The above control unit (20) The first time interval (t) above d ) and the second time interval (t d An electronic device (10) configured to control a voltage (') to different values.

10. In paragraph 7, The above control unit (20) After the second control signal (gate signal A' and gate signal B') for the switching operation of the second half bridge section (110-2) is input, the second time interval (t d An electronic device (10) including a soft starter (300) configured to output a third control signal (gate signal A'' and gate signal B'') for a switching operation of the third half-bridge section (110-n) in response to the passage of ').

11. In paragraph 10, The above soft starter (300) is In response to the charge / discharge by the supply voltage, the second time interval (t d A third element (320) configured to perform a switching operation with '); The second time interval (t) above d A fourth element (330) configured to generate a second switching signal in response to the operation of the first element (320) being turned on by '); and An electronic device (10) including a switching unit (341, 343) configured to input the second control signal (gate signal A' and gate signal B') and output the third control signal (gate signal A'' and gate signal B'') in response to the second switching signal.

12. In paragraph 10, The above third half bridge section (110-n) is A fifth switching element (Q) configured to be turned on or off by a fifth gate signal (gate signal A'') which is one of the third control signals 2n-1 ); and A sixth switching element (Q) configured to be turned on or off by a sixth gate signal (gate signal B'') which is one of the third control signals 2n ) comprising an electronic device (10).

13. In paragraph 4, The above first element (320) is, A first capacitor (C) provided between the terminal to which the above supply voltage is input and ground ss )(321); and The above first capacitor (C ss )(321) comprising a seventh switching element (323) configured to switch in response to charging / discharging.

14. In paragraph 13, The above second element (330) is An electronic device (10) comprising an eighth switching element (333) configured to output the first switching signal in response to turning on the seventh switching element (323).

15. In paragraph 4, An electronic device (10), in which one resistor and one capacitor are connected in parallel between the output terminal and the ground terminal of the switch unit (341, 343) from which the second control signal (gate signal A' and gate signal B') is output.

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