Calibration method, device and electronic equipment for zero intermediate frequency signal transceiver

Abstract

The present application belongs to the field of signal calibration, and in particular, relates to a calibration method, device and electronic device for a zero intermediate frequency signal transceiver, the method comprising: obtaining a modulated radio frequency signal sent by a signal transmitter using a loopback link; and demodulating the radio frequency signal to obtain a baseband signal; determining the baseband spectrum information of the signal receiver according to the baseband signal; determining the imbalance information of the amplitude or angle of the in-phase orthogonal signal of the signal receiver and the DC bias information based on the baseband spectrum information; determining a first optimal compensation value for the imbalance information, and determining a second optimal compensation value for the DC bias information; calibrating the imbalance information according to the first optimal compensation value, and calibrating the DC bias information according to the second optimal compensation value. That is, the embodiment of the present application can simultaneously calibrate the imbalance information of the amplitude or angle of the in-phase orthogonal signal of the signal receiver and the DC bias information, thereby improving the reliability of the signal receiver.

Description

Technical Field

[0001] The present application relates to the field of signal calibration, and in particular to a calibration method, device, and electronic equipment for a zero intermediate frequency signal transceiver. Background Art

[0002] One existing calibration method for wireless testers uses specialized, higher-precision equipment (such as a high-precision spectrum analyzer, signal source, power meter, or atomic clock frequency counter) as a companion tester. The basic calibration logic is as follows: Using the high-precision companion tester as a benchmark, the wireless tester to be calibrated is adjusted to a level as close to that of the high-precision companion tester as possible. This method is highly dependent on the companion tester and places high demands on its accuracy.

[0003] Another calibration solution for wireless testers is self-calibration, which can calibrate the device's power accuracy and signal quality without a companion tester. However, existing self-calibration solutions can only calibrate the local oscillator leakage and DC bias in the wireless tester, and cannot simultaneously calibrate multiple factors that affect the power accuracy and signal quality of the wireless tester. In other words, it cannot simultaneously reduce the impact of multiple factors on device reliability. Summary of the Invention

[0004] Embodiments of the present application provide a calibration method, device, and electronic device for a zero-IF signal transceiver, which can improve the reliability of a signal receiver.

[0005] In a first aspect, an embodiment of the present application provides a calibration method for a zero-IF signal transceiver, the calibration method comprising:

[0006] Acquire a modulated radio frequency signal sent by a signal transmitter using a loopback link, and demodulate the radio frequency signal to obtain a baseband signal, wherein the radio frequency signal is a single-tone signal;

[0007] determining baseband spectrum information of the signal receiver according to the baseband signal;

[0008] Determining imbalance information of amplitude or angle of in-phase and quadrature signals of the signal receiver and DC offset information based on the baseband spectrum information;

[0009] Determining a first optimal compensation value for the imbalance information based on the imbalance information and a preset first compensation value range for the imbalance information, and determining a second optimal compensation value for the DC bias information based on the DC bias information and a preset second compensation value range for the DC bias information;

[0010] The imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver is calibrated according to the first optimal compensation value, and the DC bias information of the signal receiver is calibrated according to the second optimal compensation value.

[0011] In a possible implementation of the first aspect, the center frequency of the single-tone signal is the same as the local oscillator frequency of the signal transmitter, the deviation between the local oscillator frequency of the signal receiver and the local oscillator frequency of the signal transmitter is less than 1 / 4 baseband bandwidth, and the demodulating the radio frequency signal to obtain the baseband signal includes:

[0012] Demodulate the radio frequency signal to obtain an in-phase signal in the baseband signal, where the in-phase signal is:

[0013]

[0014] Wherein, I′(t) represents the in-phase signal in the baseband signal of the signal receiver, C Q1 represents the amplitude of the local oscillator leakage of the orthogonal signal of the signal transmitter, A1 represents the amplitude of the in-phase orthogonal signal of the signal transmitter, ω1 represents the local oscillator frequency of the signal transmitter, ω2 represents the local oscillator frequency of the signal receiver, C I1 represents the amplitude of the local oscillator leakage of the in-phase signal of the signal transmitter, Represents the angle of the in-phase and quadrature signals of the signal transmitter, C I2 A magnitude representing a local oscillator leakage of an in-phase signal of the signal receiver;

[0015] Demodulate the radio frequency signal to obtain an orthogonal signal in the baseband signal, where the orthogonal signal is:

[0016]

[0017] Wherein, Q'(t) represents the quadrature signal in the baseband signal of the signal receiver, A2 represents the amplitude of the in-phase quadrature signal of the signal receiver, represents the angle of the in-phase and quadrature signals of the signal receiver, the C Q1 、C I1 , A1 and is the non-ideal characteristic of the signal transmitter, the C I2 , A2 and is a non-ideal characteristic of the signal receiver;

[0018] The baseband signal is obtained based on the in-phase signal in the baseband signal and the quadrature signal in the baseband signal, where the baseband signal is:

[0019]

[0020] in, represents the baseband signal, I′(t) represents the real part of the baseband signal, and jQ′(t) represents the imaginary part of the baseband signal.

[0021] Wherein, determining baseband spectrum information of the signal receiver according to the baseband signal includes:

[0022] Performing Fourier transform on the baseband signal to determine baseband spectrum information of the signal receiver, where the baseband spectrum information is:

[0023]

[0024] in, represents the baseband spectrum information of the signal receiver, C Q2 represents the amplitude of the local oscillator leakage of the orthogonal signal of the signal receiver, δ(ω+ω2-ω1) represents the center frequency of the single tone signal, δ(ω+ω1-ω2) represents the image frequency of the signal receiver, δ(ω) represents the local oscillator frequency of the signal receiver, and the C Q2 It is an irrational characteristic of the signal receiver.

[0025] The step of determining the imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver and the DC bias information based on the baseband spectrum information includes:

[0026] Based on the baseband spectrum information, the imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver is determined as follows:

[0027]

[0028] Based on the baseband spectrum information, the DC offset information of the in-phase and quadrature signals of the signal receiver is determined as follows:

[0029] [[2(C I2 +j+C Q2 )]]2πδ(ω);

[0030] The method of determining a first optimal compensation value for the imbalance information based on the imbalance information and a preset first compensation value range for the imbalance information, and determining a second optimal compensation value for the DC bias information based on the DC bias information and a preset second compensation value range for the DC bias information, includes:

[0031] Using the optimization algorithm, determine the first compensation value range of the imbalance information The first optimal compensation value of

[0032] And using the optimization algorithm, in the preset second compensation value range of the DC bias information, determine [[2(C I2 +j+C Q2 )]The second optimal compensation value of 2πδ(ω).

[0033] In a second aspect, an embodiment of the present application provides a calibration method for a zero-IF signal transceiver, the calibration method comprising:

[0034] Acquire a modulated radio frequency signal sent by a signal transmitter using a loopback link, and demodulate the radio frequency signal to obtain a baseband signal, wherein the radio frequency signal is a single-tone signal;

[0035] determining baseband spectrum information of the signal receiver according to the baseband signal;

[0036] Determining, based on the baseband spectrum information, amplitude or angle imbalance information of the in-phase and quadrature signals of the signal transmitter, and local oscillator leakage information;

[0037] determining a first optimal compensation value for the imbalance information based on the imbalance information and a preset first compensation value range for the imbalance information, and determining a third optimal compensation value for the local oscillator leakage information based on the local oscillator leakage information and a preset third compensation value range for the local oscillator leakage information;

[0038] The imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal transmitter is calibrated according to the first optimal compensation value, and the local oscillator leakage information of the signal transmitter is calibrated according to the third compensation value.

[0039] In a third aspect, an embodiment of the present application provides a calibration device for a zero-IF signal transceiver, the calibration device comprising:

[0040] An acquisition module is used to acquire a modulated radio frequency signal sent by a signal transmitter using a loopback link, and demodulate the radio frequency signal to obtain a baseband signal, wherein the radio frequency signal is a single-tone signal;

[0041] A first determining module, configured to determine baseband spectrum information of the signal receiver according to the baseband signal;

[0042] a second determining module, configured to determine, based on the baseband spectrum information, imbalance information of amplitudes or angles of in-phase and quadrature signals of the signal receiver, and DC offset information;

[0043] a third determining module, configured to determine a first optimal compensation value for the imbalance information based on the imbalance information and a preset first compensation value range for the imbalance information, and to determine a second optimal compensation value for the DC bias information based on the DC bias information and a preset second compensation value range for the DC bias information;

[0044] A calibration module is used to calibrate the amplitude or angle imbalance information of the in-phase and quadrature signals of the signal receiver according to the first optimal compensation value, and to calibrate the DC bias information of the in-phase and quadrature signals of the signal receiver according to the second optimal compensation value.

[0045] In a fourth aspect, an embodiment of the present application provides a calibration device for a zero-IF signal transceiver, the calibration device comprising:

[0046] An acquisition module is used to acquire a radio frequency signal sent by a signal transmitter and demodulate the radio frequency signal to obtain a baseband signal, wherein the radio frequency signal is a single-tone signal;

[0047] A first determining module, configured to determine baseband spectrum information of the signal receiver according to the baseband signal;

[0048] a second determining module, configured to determine, based on the baseband spectrum information, amplitude or angle imbalance information of the in-phase and quadrature signals of the signal transmitter, and local oscillator leakage information;

[0049] a third determining module, configured to determine a first optimal compensation value for the imbalance information based on the imbalance information and a preset first compensation value range for the imbalance information, and to determine a third optimal compensation value for the local oscillator leakage information based on the local oscillator leakage information and a preset third compensation value range for the local oscillator leakage information;

[0050] A calibration module is configured to calibrate the amplitude or angle imbalance information of the in-phase and quadrature signals of the signal transmitter according to the first optimal compensation value, and to calibrate the local oscillator leakage information of the signal transmitter according to the third compensation value.

[0051] In a fifth aspect, an embodiment of the present application provides an electronic device, comprising a memory, a processor, and a computer program stored in the memory and runnable on the processor. When the processor executes the computer program, the calibration method for the zero intermediate frequency signal transceiver as described in any one of the first aspect, or the calibration method for the zero intermediate frequency signal transceiver as described in the second aspect is implemented.

[0052] In a sixth aspect, an embodiment of the present application provides a computer-readable storage medium, wherein the computer-readable storage medium stores a computer program, and when the computer program is executed by a processor, the calibration method of the zero intermediate frequency signal transceiver as described in any one of the first aspect, or the calibration method of the zero intermediate frequency signal transceiver as described in the second aspect is implemented.

[0053] Compared with the prior art, the embodiments of the present application have the following advantages: in the embodiments of the present application, the radio frequency signal transmitted by the signal transmitter using the loopback link is obtained; the radio frequency signal is demodulated to obtain a baseband signal; baseband spectrum information of the signal receiver is determined based on the baseband signal; based on the baseband spectrum information, the amplitude or angle imbalance information and DC bias information of the in-phase and quadrature signals of the signal receiver are determined; a first optimal compensation value for the imbalance information is determined, and a second optimal compensation value for the DC bias information is determined; the imbalance information is calibrated according to the first optimal compensation value, and the DC bias information is calibrated according to the second optimal compensation value. That is, the embodiments of the present application can simultaneously calibrate the amplitude or angle imbalance information and DC bias information of the in-phase and quadrature signals of the signal receiver, thereby improving the reliability of the signal receiver. BRIEF DESCRIPTION OF THE DRAWINGS

[0054] In order to more clearly illustrate the technical solutions in the embodiments of the present application, the following briefly introduces the drawings required for use in the embodiments or descriptions of the prior art. Obviously, the drawings described below are only some embodiments of the present application. For ordinary technicians in this field, other drawings can be obtained based on these drawings without any creative work.

[0055] Figure 1 This is a schematic diagram of an application scenario of a calibration method for a zero-IF signal transceiver provided in an embodiment of the present application;

[0056] Figure 2 This is a schematic flow chart of a calibration method for a zero-IF signal transceiver provided in an embodiment of the present application;

[0057] Figure 3a is a schematic flow chart of a specific method for obtaining a baseband signal provided in an embodiment of the present application;

[0058] Figure 3b This is an example diagram of a power spectrum before and after loopback self-calibration of a signal receiver provided in an embodiment of the present application;

[0059] Figure 4 is a schematic flow chart of a calibration method for a zero-IF signal transceiver provided in an embodiment of the present application;

[0060] Figure 5is a schematic flow chart of a specific method for obtaining a baseband signal provided in an embodiment of the present application;

[0061] Figure 6 1 is a schematic structural diagram of a calibration method for a zero-IF signal transceiver provided in an embodiment of the present application;

[0062] Figure 7 1 is a schematic structural diagram of a calibration method for a zero-IF signal transceiver provided in an embodiment of the present application;

[0063] Figure 8 It is a structural diagram of an electronic device provided in one embodiment of the present application. DETAILED DESCRIPTION

[0064] In the following description, specific details such as specific system structures and technologies are provided for the purpose of illustration rather than limitation, so as to provide a thorough understanding of the embodiments of the present application. However, it should be clear to those skilled in the art that the present application can also be implemented in other embodiments without these specific details. In other cases, detailed descriptions of well-known systems, devices, circuits, and methods are omitted to avoid obstructing the description of the present application with unnecessary details. In other cases, the specific technical details of the various embodiments can be referenced to each other, and specific systems not described in one embodiment can be referenced to other embodiments.

[0065] It should be understood that when used in this application, the term "comprising" indicates the presence of described features, integers, steps, operations, elements and / or components, but does not preclude the presence or addition of one or more other features, integers, steps, operations, elements, components and / or groups thereof.

[0066] It will also be understood that the term “and / or” used in this application refers to and includes any and all possible combinations of one or more of the associated listed items.

[0067] References to "an embodiment of the present application" or "some embodiments" in the present specification mean that one or more embodiments of the present application include specific features, structures, or characteristics described in conjunction with the embodiment. Therefore, phrases such as "in other embodiments," "an embodiment of the present application," and "other embodiments of the present application" appearing in different places in this specification do not necessarily refer to the same embodiment, but rather mean "one or more but not all embodiments," unless otherwise specifically emphasized. The terms "including," "comprising," "having," and their variations all mean "including but not limited to," unless otherwise specifically emphasized.

[0068] In addition, in the description of the present application, the terms "first", "second", etc. are only used to distinguish the description and cannot be understood as indicating or implying relative importance.

[0069] Existing self-calibration solutions for wireless testers can calibrate device power accuracy and signal quality without a companion tester. However, these solutions can only calibrate the local oscillator leakage and DC bias in the wireless tester. They cannot simultaneously calibrate multiple factors that affect the power accuracy and signal quality of the wireless tester. This means they cannot simultaneously reduce the impact of multiple factors on device reliability.

[0070] In order to solve the above-mentioned defects, the invention of this application is as follows:

[0071] When the signal receiver in the embodiment of the present application performs loop self-calibration, a radio frequency signal may be transmitted by a signal transmitter with non-ideal characteristics. The radio frequency signal is received and demodulated by a signal receiver with non-ideal characteristics to obtain a baseband signal. The baseband signal is mixed with the local oscillator leakage information of the signal transmitter and the imbalance information of the in-phase orthogonal signal, i.e., the 1Q signal, as well as the DC bias information of the signal receiver and the imbalance information of the 1Q signal. These nonlinear signals mixed together will reduce the signal quality. The embodiment of the present application can separate and extract these mixed nonlinear signals by sending a single tone wave of a specific frequency, and then determine the first optimal compensation value of the imbalance information and the second optimal compensation value of the DC bias information; calibrating the imbalance information according to the first optimal compensation value and calibrating the DC bias information according to the second optimal compensation value can simultaneously reduce the impact of multiple factors on the reliability of the equipment.

[0072] In order to illustrate the technical solution of the present application, specific embodiments are provided below.

[0073] Please refer to Figure 1 , Figure 1 This is a schematic diagram of an application scenario of a calibration method for a zero-IF signal transceiver provided in an embodiment of the present application. For ease of explanation, only the portion relevant to the present application is shown. The application scenario includes: a signal transmitter 100, a signal receiver 200, and a loopback link 300.

[0074] The information transmitter 100 is a zero-IF architecture transmitter. The signal transmitter 100 is used to modulate a radio frequency signal and then transmit the radio frequency signal to the signal receiver 200 via a transmission path (loop link 300 ).

[0075] The signal receiver 200 is a receiver with a zero intermediate frequency architecture. After receiving the RF signal, the signal receiver selects the frequency band through a bandpass filter and amplifies it through a low-noise amplifier. The RF signal is then demodulated by a demodulator. The signal receiver performs spectrum analysis on the demodulated signal and, based on the spectrum analysis results, calibrates various factors that affect the signal quality of the signal receiver or signal transmitter.

[0076] Please refer to Figure 2 , Figure 2 This is a schematic flowchart of a calibration method for a zero intermediate frequency signal transceiver provided in an embodiment of the present application. Figure 2 The execution subject of the method in can be Figure 1 The signal receiver in . Figure 2 As shown, the method includes: S201 to S205.

[0077] S201: A signal receiver obtains a radio frequency signal sent by a signal transmitter using a loopback link, and demodulates the radio frequency signal to obtain a baseband signal.

[0078] Specifically, the radio frequency signal is a single-tone signal, which is a signal of a single frequency.

[0079] In the embodiment of the present application, the signal transmitter and the signal receiver share a clock source, and the relative frequency error is negligible.

[0080] In the embodiment of the present application, the radio frequency signal sent by the signal transmitter can be expressed by the following formula:

[0081]

[0082] Among them, -sin(ω1t) is the original ideal single-tone signal, The irrational characteristics of the signal transmitter itself The distortion caused to the original ideal single tone signal, C I1 、C Q1 、A1、 The specific meaning of can be referred to other embodiments and will not be repeated here.

[0083] After the signal transmitter transmits the above signal using the loopback link, it demodulates the RF signal. Please refer to Figure 3 for the obtained baseband signal.

[0084] FIG3 is a schematic flow chart of a specific method for obtaining a baseband signal provided by an embodiment of the present application. The execution subject of the method in FIG3 can be Figure 1 As shown in FIG3 , the method includes: S301 to S303 .

[0085] S301: The signal receiver demodulates the RF signal to obtain an in-phase signal from the baseband signal. Specifically, the center frequency of the single-tone signal is the same as the local oscillator frequency of the signal transmitter, and the deviation between the local oscillator frequency of the signal receiver and the local oscillator frequency of the signal transmitter is less than 1 / 4 of the baseband bandwidth.

[0086] In the embodiment of the present application, the signal receiver itself also has non-ideal characteristics CI2 、C Q2 、A2、 It will also cause distortion to the original ideal single tone signal, C I2 、C Q2 、A2、 The specific meaning of can be referred to other embodiments and will not be repeated here.

[0087] The signal receiver in the embodiment of the present application demodulates the radio frequency signal, and the demodulation process is as follows:

[0088]

[0089] as well as:

[0090]

[0091] In the embodiment of this application, After filtering out all the frequency multipliers through a low-pass filter (using product sum and difference to obtain the frequency multipliers and then discarding them), the in-phase signal in the baseband signal can be expressed by the following formula:

[0092]

[0093] Where I′(t) represents the in-phase signal in the baseband signal of the signal receiver, C Q1 represents the amplitude of the local oscillator leakage of the orthogonal signal of the signal transmitter, A1 represents the amplitude of the in-phase orthogonal signal of the signal transmitter, ω1 represents the local oscillator frequency of the signal transmitter, ω2 represents the local oscillator frequency of the signal receiver, and C I1 Represents the amplitude of the local oscillator leakage of the in-phase signal of the signal transmitter, Represents the angle of the in-phase and quadrature signals of the signal transmitter, C I2 Represents the amplitude of the local oscillator leakage of the in-phase signal at the signal receiver.

[0094] S302: The signal receiver demodulates the radio frequency signal to obtain an orthogonal signal in the baseband signal.

[0095] In the embodiment of this application, After filtering out all the frequency multiplication components through a low-pass filter (using product sum difference to obtain the frequency multiplication components and then discarding them), the orthogonal signal in the baseband signal can be expressed by the following formula:

[0096]

[0097] Where Q'(t) represents the quadrature signal in the baseband signal of the signal receiver, A2 represents the amplitude of the in-phase quadrature signal of the signal receiver, Represents the angle of the in-phase and quadrature signals at the receiver, C Q1 、CI1 , A1 and is the non-ideal characteristic of the signal transmitter, C I2 , A2 and is a non-ideal characteristic of the signal receiver.

[0098] In the embodiment of the present application, the non-ideal characteristics of the signal transmitter and the signal receiver are both first-order small quantities and the frequency that changes with time is much smaller than the local oscillator frequency.

[0099] S303 : The signal receiver obtains a baseband signal based on the in-phase signal and the quadrature signal in the baseband signal.

[0100] The obtained baseband signal can be expressed by the following formula:

[0101]

[0102] in, represents the baseband signal, I′(t) represents the real part of the baseband signal, and jQ′(t) represents the imaginary part of the baseband signal.

[0103] S202: The signal receiver determines baseband spectrum information of the signal receiver according to the baseband signal.

[0104] Perform Fourier transform on the baseband signal to determine the baseband spectrum information of the signal receiver. The baseband spectrum information is:

[0105]

[0106] in, Represents the baseband spectrum information of the signal receiver, C Q2 represents the amplitude of the local oscillator leakage of the orthogonal signal of the signal receiver, δ(ω+ω2-ω1) represents the center frequency of the single-tone signal, δ(ω+ω1-ω2) represents the image frequency of the signal receiver, δ(ω) represents the local oscillator frequency of the signal receiver, and C O2 It is an irrational characteristic of the signal receiver.

[0107] In an embodiment of the present application, in the spectrum information, the center frequency of the single-tone signal has the largest energy and the highest peak height, and is affected by the local oscillator leakage of the signal transmitter and the DC bias of the signal receiver, as well as the imbalance information of the IQ amplitude angle of the signal transmitter and the signal receiver.

[0108] In the embodiment of the present application, in the spectrum information, the image frequency of the signal receiver is only affected by the imbalance information of the IQ amplitude angle of the signal receiver.

[0109] In the embodiment of the present application, in the spectrum information, the local oscillator frequency of the signal receiver is only affected by the DC bias of the I path and the Q path of the signal receiver.

[0110] In the embodiment of the present application, the higher the spectrum resolution and the larger the baseband bandwidth, the better the effect of calibrating non-ideal characteristics.

[0111] S203: The signal receiver determines the imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver and the DC offset information based on the baseband spectrum information.

[0112] Based on the baseband spectrum information, the imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver is determined as follows:

[0113]

[0114] Based on the baseband spectrum information, the DC offset information of the in-phase and quadrature signals of the signal receiver is determined as:

[0115] [2(C I2 +j+C Q2 )]2πδ(ω).

[0116] Specifically, the signal receiver may calculate the power spectrum density based on the baseband spectrum information.

[0117] In the embodiment of the present application, the power spectrum density can be calculated by the following method:

[0118]

[0119] The following conclusions can be drawn from the calculated power spectrum density in the present embodiment:

[0120] 1In the power spectrum, the peak height of the image frequency at the signal receiver is proportional to This indicates that the IQ amplitude imbalance and IQ angle imbalance of the signal receiver are decoupled from the peak height of the image frequency. When the IQ amplitude imbalance and IQ angle imbalance of the signal receiver are minimized at the same time, the peak height of the image frequency is the lowest.

[0121] 2 In the power spectrum, the peak height of the local oscillator frequency of the signal receiver is proportional to C I2 2 +C Q2 2 , indicating that the I-channel DC bias and Q-channel DC bias of the signal receiver are decoupled from the peak height of the local oscillator frequency. When the I-channel DC bias and the Q-channel DC bias reach their minimum values ​​at the same time, the peak height of the local oscillator frequency is the minimum.

[0122] S204. The signal receiver determines a first optimal compensation value for the imbalance information based on the imbalance information and a preset first compensation value range for the imbalance information, and determines a second optimal compensation value for the DC bias information based on the DC bias information and a preset second compensation value range for the DC bias information.

[0123] Specifically, using the optimization algorithm, within the preset first compensation value range of the imbalance information, determine The first optimal compensation value.

[0124] Specifically, in the embodiments of this application, Characterizes the peak height of the image frequency of the signal receiver in the power spectrum.

[0125] In some embodiments, the preset first compensation value range of the imbalance information is: QDAC×IDAC∈[-1024, 1024]×[-1024, 1024], where QDAC and IDAC are registers on a decoding chip (DAC), and [-1024, 1024]×[-1024, 1024] is the voltage value of the compensation circuit inside the register.

[0126] In some embodiments, the preset first compensation value range of the imbalance information is:

[0127] The preset first compensation value range of the imbalance information is: QDAC×IDAC×DAC1×DAC2∈[−1024, 1024]×[−1024, 1024]×[−1024, 1024]×[−1024, 1024].

[0128] The optimization algorithms in the embodiments of the present application include but are not limited to: directional acceleration method (Powell optimization algorithm), conjugate gradient descent algorithm, etc., and the embodiments of the present application do not limit this.

[0129] In the embodiment of the present application, when the Powell optimization algorithm is used to optimize the peak height of the image frequency of the signal receiver, the optimization process has the following characteristics:

[0130] 1. The one-dimensional optimization process is iterated repeatedly, and the direction of each one-dimensional optimization is determined by the results of the previous N one-dimensional optimizations.

[0131] 2. The initial N one-dimensional optimization directions need to be given and must form a linearly independent group.

[0132] 3. When a function has multiple minimum points, it can only guarantee to find a certain minimum point, but cannot guarantee to find the global minimum point.

[0133] 4. When a function has multiple minimum points, the searched points are related to the initial search direction and the function gradient distribution.

[0134] And using the optimization algorithm, in the second compensation value range of the preset DC bias information, determine [2(C I2 +j+C Q2 )]]The second optimal compensation value of 2πδ(ω).

[0135] Specifically, in the embodiment of the present application [2(C I2 +j+C Q2 )]2πδ(ω) represents the peak height of the local oscillator frequency of the signal receiver in the power spectrum.

[0136] In some embodiments, the second compensation value range of the preset DC bias information is Among them, ΔA represents the amplitude compensation value range of IQ imbalance information, The range of angle compensation values ​​that characterizes IQ imbalance information.

[0137] In the prior art, it takes 17 hours to find the first optimal compensation point and the second optimal compensation point through traversal, but it can be completed in a few seconds using the optimization algorithm in this application.

[0138] For example, when using the Powell optimization algorithm, the optimization process only required 100 to 200 single-point measurements to find the optimal calibration point. Furthermore, due to the universality of the Powell optimization algorithm, it can be applied to the calibration process of this application without modification, reducing the development workload.

[0139] S205: The signal receiver calibrates the imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver according to the first optimal compensation value, and calibrates the DC bias information of the signal receiver according to the second optimal compensation value.

[0140] Specifically, using the calibration method in the embodiment of the present application, the calibration result of the DC bias is 5-10 dB lower than that of the existing calibration scheme, and the average value of the DC bias of the existing calibration scheme is about -75 dB.

[0141] By using the calibration method in the embodiment of the present application, the imbalance information of the IQ angle is less than 0.03°, and the imbalance information of the IQ amplitude is less than 0.01 dB.

[0142] The signal receiver in the embodiment of the present application calibrates the amplitude or angle imbalance information of the in-phase and quadrature signals of the signal receiver according to the first optimal compensation value, thereby reducing the impact of the amplitude or angle imbalance information of the in-phase and quadrature signals of the signal receiver on the reliability of the device. The DC bias information of the signal receiver is calibrated according to the second optimal compensation value, thereby simultaneously reducing the impact of the DC bias information of the signal receiver on the reliability of the device.

[0143] Please refer to Figure 3b , Figure 3b This is an example diagram of the power spectrum before and after loopback self-calibration of a signal receiver provided by an embodiment of the present application. Figure 3b In the figure, Figure a represents the power spectrum before calibration, and Figure b represents the power spectrum after calibration. Figure 3b The horizontal axis represents the frequency value, the unit of the horizontal axis is MHz, and the vertical axis represents the power spectrum density value, the unit of the vertical axis is dBm / 100KHz.

[0144] exist Figure 3b In Figure a, the M peak represents the peak height of the mirror frequency, and the N peak represents the peak height of the local oscillator frequency. The M peak and the N peak in Figure b after calibration basically disappear, that is, the calibration method in the embodiment of the present application reduces the impact of the imbalance information of the amplitude or angle of the in-phase orthogonal signal of the signal receiver on the reliability of the device, while reducing the impact of the DC bias information of the signal receiver on the reliability of the device.

[0145] In summary, the technical solution of the present application is to obtain the radio frequency signal sent by the signal transmitter using the loopback link; demodulate the radio frequency signal to obtain the baseband signal; determine the baseband spectrum information of the signal receiver based on the baseband signal; determine the amplitude or angle imbalance information and DC bias information of the in-phase and quadrature signals of the signal receiver based on the baseband spectrum information; determine the first optimal compensation value for the imbalance information, and determine the second optimal compensation value for the DC bias information; calibrate the imbalance information according to the first optimal compensation value, and calibrate the DC bias information according to the second optimal compensation value. That is, the embodiment of the present application can simultaneously calibrate the amplitude or angle imbalance information and DC bias information of the in-phase and quadrature signals of the signal receiver, thereby improving the reliability of the signal receiver.

[0146] Please refer to Figure 4 , Figure 4 This is a schematic flowchart of a calibration method for a zero intermediate frequency signal transceiver provided in an embodiment of the present application. Figure 4 The execution subject of the method in can be Figure 1 The signal receiver in . Figure 4 As shown, the method includes: S401 to S405.

[0147] S401: A signal receiver obtains a radio frequency signal sent by a signal transmitter using a loopback link, and demodulates the radio frequency signal to obtain a baseband signal.

[0148] Specifically, the radio frequency signal is a single-tone signal.

[0149] In the embodiment of the present application, the radio frequency signal sent by the signal transmitter can be expressed by the following formula:

[0150]

[0151] Among them, cos(ω2t) is the original ideal single-tone signal, The irrational characteristics of the signal transmitter itself The distortion caused to the original ideal single tone signal, C I1 、C Q1 、A1、 The specific meaning of can be referred to other embodiments and will not be repeated here.

[0152] After the signal transmitter transmits the above signal using the loopback link, it demodulates the RF signal and obtains the baseband signal. Figure 5 .

[0153] Figure 5 This is a schematic flowchart of a specific method for obtaining a baseband signal provided in an embodiment of the present application. Figure 5 The execution subject of the method in can be Figure 1 The signal receiver in . Figure 5 As shown, the method includes: S501 to S503.

[0154] S501: A signal receiver demodulates a radio frequency signal to obtain an in-phase signal in a baseband signal.

[0155] Specifically, the center frequency of the single tone signal is the same as the local oscillator frequency of the signal receiver, and the deviation between the local oscillator frequency of the signal transmitter and the local oscillator frequency of the signal receiver is less than 1 / 4 of the baseband bandwidth. In the embodiment of the present application, the signal receiver itself also has non-ideal characteristics. C I2 、C Q2 、A2、 It will also cause distortion to the original ideal single tone signal, C I2 、C Q2 、A2、 The specific meaning of can be referred to other embodiments and will not be repeated here.

[0156] The demodulation of the radio frequency signal by the signal receiver in the embodiment of the present application can be referred to other embodiments and will not be repeated here.

[0157] In the embodiment of this application, After filtering out all the frequency multiplication components through a low-pass filter (using product sum difference to obtain the frequency multiplication components and then discarding them), the in-phase signal in the baseband signal can be expressed by the following formula:

[0158]

[0159] Where I'(t) represents the in-phase signal in the baseband signal of the signal receiver, A1 represents the amplitude of the in-phase orthogonal signal of the signal transmitter, and C I1 represents the amplitude of the local oscillator leakage of the in-phase signal of the signal transmitter, w1 represents the local oscillator frequency of the signal transmitter, w2 represents the local oscillator frequency of the signal receiver, C Q1 Represents the amplitude of the local oscillator leakage of the orthogonal signal of the signal transmitter, Represents the angle of the in-phase and quadrature signals of the signal transmitter, C I2 Represents the amplitude of the local oscillator leakage of the in-phase signal at the signal receiver.

[0160] S502: The signal receiver demodulates the radio frequency signal to obtain an orthogonal signal in the baseband signal.

[0161] In the embodiment of this application, After filtering out all the frequency multiplication components through a low-pass filter (using product sum difference to obtain the frequency multiplication components and then discarding them), the orthogonal signal in the baseband signal can be expressed by the following formula:

[0162]

[0163] Where Q′(t) represents the quadrature signal in the baseband signal of the signal receiver, Represents the angle of the in-phase and quadrature signals at the signal receiver, Represents the angle of the in-phase and quadrature signals at the receiver, C Q2 is the irrational characteristic of the signal receiver, C Q1 、C I1 , A1 and is the non-ideal characteristic of the signal transmitter, C I2 、C Q2 and is a non-ideal characteristic of the signal receiver.

[0164] S503: The signal receiver obtains a baseband signal based on the in-phase signal and the quadrature signal in the baseband signal.

[0165] The obtained baseband signal can be expressed by the following formula:

[0166]

[0167] in, represents the baseband signal, I′(t) represents the real part of the baseband signal, and jQ′(t) represents the imaginary part of the baseband signal.

[0168] S402: The signal receiver determines baseband spectrum information of the signal receiver according to the baseband signal.

[0169] Perform Fourier transform on the baseband signal to determine the baseband spectrum information of the signal receiver. The baseband spectrum information is:

[0170]

[0171] in, represents the baseband spectrum information of the signal receiver, δ(ω) represents the center frequency of the single-tone signal, δ(ω-2(ω1-ω2)) represents the image frequency of the signal transmitter, and δ(ω-ω1+ω2) represents the local oscillator frequency of the signal transmitter.

[0172] In an embodiment of the present application, in the spectrum information, the center frequency of the single-tone signal has the largest energy and the highest peak height, and is affected by the local oscillator leakage of the signal transmitter and the DC bias of the signal receiver, as well as the imbalance information of the IQ amplitude angle of the signal transmitter and the signal receiver.

[0173] In the embodiment of the present application, in the spectrum information, the image frequency of the signal transmitter is only affected by the imbalance information of the IQ amplitude angle of the signal receiver.

[0174] In the embodiment of the present application, in the spectrum information, the local oscillator frequency of the signal transmitter is only affected by the local oscillator leakage of the I path and the Q path of the signal receiver.

[0175] S403: The signal receiver determines the imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal transmitter and the local oscillator leakage information based on the baseband spectrum information.

[0176] Based on the baseband spectrum information, the imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal transmitter is determined as follows:

[0177]

[0178] Based on the baseband spectrum information, the local oscillator leakage information of the in-phase and quadrature signals of the signal transmitter is determined as:

[0179] [(C I1 -jC Q1 )]2πδ(ω-ω1+ω2).

[0180] Specifically, the signal receiver may calculate the power spectrum density based on the baseband spectrum information.

[0181] In the embodiment of the present application, the power spectrum density can be calculated by the following method:

[0182]

[0183] The following conclusions can be drawn from the calculated power spectrum density in the present embodiment:

[0184] 1In the power spectrum, the peak height of the image frequency of the signal transmitter is proportional to This indicates that the IQ amplitude imbalance and IQ angle imbalance of the signal transmitter are decoupled from the peak height of the image frequency. When the IQ amplitude imbalance and IQ angle imbalance of the signal transmitter are minimized at the same time, the peak height of the image frequency is the lowest.

[0185] 2 In the power spectrum, the peak height of the local oscillator frequency of the signal transmitter is proportional to C I2 2 +C Q2 2 , indicating that the I-channel local oscillator leakage and Q-channel local oscillator leakage of the signal transmitter are decoupled from the peak height of the local oscillator frequency. When the I-channel local oscillator leakage and the Q-channel local oscillator leakage reach their minimums at the same time, the peak height of the local oscillator frequency is the minimum.

[0186] S404: The signal receiver determines a first optimal compensation value for the imbalance information based on the imbalance information and a preset first compensation value range for the imbalance information, and determines a third optimal compensation value for the local oscillator leakage information based on the local oscillator leakage information and a preset third compensation value range for the local oscillator leakage information.

[0187] Using the optimization algorithm, determine the first compensation value range of the preset imbalance information The first optimal compensation value.

[0188] And using the optimization algorithm, in the preset third compensation value range of the local oscillator leakage information, determine [(C I1 -jC Q1 )]2πδ(ω-ω1+ω2) is the third optimal compensation value.

[0189] Specifically, the specific method of S404 is the same as that of S204 and will not be repeated here.

[0190] S405: The signal receiver calibrates the imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal transmitter according to the first optimal compensation value, and calibrates the local oscillator leakage information of the signal transmitter according to the third compensation value.

[0191] Specifically, the signal receiver of the embodiment of the present application calibrates the amplitude or angle imbalance information of the in-phase orthogonal signal of the signal transmitter according to the first optimal compensation value, thereby reducing the impact of the amplitude or angle imbalance information of the in-phase orthogonal signal of the signal transmitter on the reliability of the device, and calibrates the local oscillator leakage information of the signal transmitter according to the third optimal compensation value, thereby simultaneously reducing the impact of the local oscillator leakage information of the signal transmitter on the reliability of the device.

[0192] In summary, the technical solution of the present application obtains the radio frequency signal sent by the signal transmitter using the loopback link; demodulates the radio frequency signal to obtain the baseband signal; determines the baseband spectrum information of the signal receiver based on the baseband signal; determines the amplitude or angle imbalance information and local oscillator leakage information of the in-phase and quadrature signals of the signal transmitter based on the baseband spectrum information; determines a first optimal compensation value for the imbalance information and a third optimal compensation value for the local oscillator leakage information; calibrates the imbalance information based on the first optimal compensation value and calibrates the local oscillator leakage information based on the third optimal compensation value. That is, the embodiments of the present application can simultaneously calibrate the amplitude or angle imbalance information and local oscillator leakage information of the in-phase and quadrature signals of the signal transmitter, thereby improving the reliability of the signal receiver.

[0193] Furthermore, the technical solution of the present application does not require additional accompanying test equipment or reliance on other special hardware equipment. It only requires connecting the signal transmitter and the signal receiver through a loopback link to achieve calibration of the signal transmitter and the signal receiver, further improving the calibration efficiency. The solution is low-cost and easy to promote.

[0194] Furthermore, the technical solution of the present application utilizes an optimization algorithm for calibration, which has high calibration accuracy and fast calibration speed.

[0195] It should be understood that the size of the serial numbers of the steps in the above embodiments does not mean the order of execution. The execution order of each process should be determined by its function and internal logic, and should not constitute any limitation on the implementation process of the embodiments of this application.

[0196] Please refer to Figure 6 , Figure 6 : is a structural diagram of a calibration method for a zero-IF signal transceiver provided in an embodiment of the present application, the device comprising:

[0197] The acquisition module 61 is configured to acquire a modulated radio frequency signal sent by a signal transmitter using a loopback link, and demodulate the radio frequency signal to obtain a baseband signal. The radio frequency signal is a single-tone signal.

[0198] The first determining module 62 is configured to determine baseband spectrum information of the signal receiver according to the baseband signal.

[0199] The second determination module 63 is configured to determine the imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver and the DC offset information based on the baseband spectrum information.

[0200] The third determination module 64 is configured to determine a first optimal compensation value for the imbalance information based on the imbalance information and a preset first compensation value range for the imbalance information, and to determine a second optimal compensation value for the DC bias information based on the DC bias information and a preset second compensation value range for the DC bias information.

[0201] The calibration module 65 is configured to calibrate the amplitude or angle imbalance information of the in-phase and quadrature signals of the signal receiver according to the first optimal compensation value, and to calibrate the DC bias information of the signal receiver according to the second optimal compensation value.

[0202] The center frequency of the single-tone signal is the same as the local oscillator frequency of the signal transmitter, and the deviation between the local oscillator frequency of the signal receiver and the local oscillator frequency of the signal transmitter is less than 1 / 4 of the baseband bandwidth. The acquisition module 61 is also used to demodulate the radio frequency signal to obtain the in-phase signal in the baseband signal. The in-phase signal is:

[0203]

[0204] Where I′(t) represents the in-phase signal in the baseband signal of the signal receiver, C Q1 represents the amplitude of the local oscillator leakage of the orthogonal signal of the signal transmitter, A1 represents the amplitude of the in-phase orthogonal signal of the signal transmitter, ω1 represents the local oscillator frequency of the signal transmitter, ω2 represents the local oscillator frequency of the signal receiver, and C I1 Represents the amplitude of the local oscillator leakage of the in-phase signal of the signal transmitter, Represents the angle of the in-phase and quadrature signals of the signal transmitter, C I2 The amplitude of the local oscillator leakage representing the in-phase signal at the signal receiver;

[0205] Demodulate the RF signal to obtain the orthogonal signal in the baseband signal. The orthogonal signal is:

[0206]

[0207]

[0208] Where Q'(t) represents the quadrature signal in the baseband signal of the signal receiver, A2 represents the amplitude of the in-phase quadrature signal of the signal receiver, Represents the angles of the in-phase and quadrature signals of the signal receiver, CQ1, CI1, A1 and is the non-ideal characteristic of the signal transmitter, CI2, A2 and is a non-ideal characteristic of the signal receiver;

[0209] Based on the in-phase signal in the baseband signal and the orthogonal signal in the baseband signal, the baseband signal is obtained, and the baseband signal is:

[0210]

[0211] in, represents the baseband signal, I′(t) represents the real part of the baseband signal, and jQ′(t) represents the imaginary part of the baseband signal.

[0212] The first determining module 62 is further configured to perform Fourier transform on the baseband signal to determine baseband spectrum information of the signal receiver. The baseband spectrum information is:

[0213]

[0214] in, Represents the baseband spectrum information of the signal receiver, C Q2 represents the amplitude of the local oscillator leakage of the orthogonal signal of the signal receiver, δ(ω+ω2-ω1) represents the center frequency of the single-tone signal, δ(ω+ω1-ω2) represents the image frequency of the signal receiver, δ(ω) represents the local oscillator frequency of the signal receiver, and C Q2 It is an irrational characteristic of the signal receiver.

[0215] The second determining module 63 is further configured to determine, based on the baseband spectrum information, the imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver:

[0216]

[0217] Based on the baseband spectrum information, the DC offset information of the in-phase and quadrature signals of the signal receiver is determined as:

[0218] [2(C I2 +j+C Q2 )]2πδ(ω);

[0219] The third determining module 64 is further configured to use an optimization algorithm to determine the first compensation value range of the preset imbalance information. The first optimal compensation value of

[0220] And using the optimization algorithm, in the second compensation value range of the preset DC bias information, determine [2(C I2 +j+C Q2 )]The second optimal compensation value of 2πδ(ω).

[0221] Please refer to Figure 7 , Figure 7 : is a structural diagram of a calibration method for a zero-IF signal transceiver provided in an embodiment of the present application, the device comprising:

[0222] The acquisition module 71 is configured to acquire a modulated radio frequency signal sent by a signal transmitter using a loopback link, and demodulate the radio frequency signal to obtain a baseband signal. The radio frequency signal is a single-tone signal.

[0223] The first determining module 72 is configured to determine baseband spectrum information of the signal receiver according to the baseband signal.

[0224] The second determination module 73 is configured to determine the imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal transmitter and the local oscillator leakage information based on the baseband spectrum information.

[0225] The third determination module 74 is configured to determine a first optimal compensation value for the imbalance information based on the imbalance information and a preset first compensation value range for the imbalance information, and to determine a third optimal compensation value for the local oscillator leakage information based on the local oscillator leakage information and a preset third compensation value range for the local oscillator leakage information.

[0226] The calibration module 75 is configured to calibrate the amplitude or angle imbalance information of the in-phase and quadrature signals of the signal transmitter according to the first optimal compensation value, and to calibrate the local oscillator leakage information of the signal transmitter according to the third compensation value.

[0227] The center frequency of the single-tone signal is the same as the local oscillator frequency of the signal receiver, and the local oscillator frequency of the signal transmitter and the local oscillator frequency of the signal receiver are less than 1 / 4 of the baseband bandwidth. The acquisition module 71 is also used to demodulate the radio frequency signal to obtain the in-phase signal in the baseband signal. The in-phase signal is:

[0228]

[0229] Where I'(t) represents the in-phase signal in the baseband signal of the signal receiver, A1 represents the amplitude of the in-phase orthogonal signal of the signal transmitter, and C I1 represents the amplitude of the local oscillator leakage of the in-phase signal of the signal transmitter, ω1 represents the local oscillator frequency of the signal transmitter, ω2 represents the local oscillator frequency of the signal receiver, and C Q1 Represents the amplitude of the local oscillator leakage of the orthogonal signal of the signal transmitter, Represents the angle of the in-phase and quadrature signals of the signal transmitter, C I2 The amplitude of the local oscillator leakage representing the in-phase signal at the signal receiver;

[0230] Demodulate the RF signal to obtain the orthogonal signal in the baseband signal. The orthogonal signal is:

[0231]

[0232] Where Q′(t) represents the quadrature signal in the baseband signal of the signal receiver, Represents the angle of the in-phase and quadrature signals at the signal receiver, Represents the angle of the in-phase and quadrature signals at the receiver, C Q2 is the irrational characteristic of the signal receiver, C Q1 、C I1 , A1 and is the non-ideal characteristic of the signal transmitter, C I2、C Q2 and is a non-ideal characteristic of the signal receiver;

[0233] Based on the in-phase signal in the baseband signal and the orthogonal signal in the baseband signal, the baseband signal is obtained, and the baseband signal is:

[0234]

[0235] in, represents the baseband signal, I′(t) represents the real part of the baseband signal, and jQ′(t) represents the imaginary part of the baseband signal.

[0236] The first determining module 72 is further configured to perform Fourier transform on the baseband signal to determine baseband spectrum information of the signal receiver. The baseband spectrum information is:

[0237]

[0238]

[0239] in, represents the baseband spectrum information of the signal receiver, δ(ω) represents the center frequency of the single-tone signal, δ(ω-2(ω1-ω2)) represents the image frequency of the signal transmitter, and δ(ω-ω1+ω2) represents the local oscillator frequency of the signal transmitter.

[0240] The second determining module 72 is further configured to determine, based on the baseband spectrum information, the imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal transmitter:

[0241]

[0242] Based on the baseband spectrum information, the local oscillator leakage information of the in-phase and quadrature signals of the signal transmitter is determined as:

[0243] [(C I1 -jC Q1 )]2πδ(ω-ω1+ω2).

[0244] The third determining module 73 is further configured to use an optimization algorithm to determine the first compensation value range of the preset imbalance information. The first optimal compensation value of

[0245] And using the optimization algorithm, in the preset third compensation value range of the local oscillator leakage information, determine [(C I1 -jC Q1 )]2πδ(ω-ω1+ω2).

[0246] Those skilled in the art can clearly understand that, for the convenience and brevity of description, only the division of the above-mentioned functional units and modules is used as an example for illustration. In actual applications, the above-mentioned functions can be distributed and completed by different functional units and modules as needed, that is, the internal structure of the device can be divided into different functional units or modules to complete all or part of the functions described above. The functional units and modules in the embodiment can be integrated into one processing unit, or each unit can exist physically alone, or two or more units can be integrated into one unit. The above-mentioned integrated unit can be implemented in the form of hardware or in the form of software functional units. In addition, the specific names of the functional units and modules are only for the convenience of distinguishing each other, and are not used to limit the scope of protection of this application. The specific working process of the units and modules in the above-mentioned system can refer to the corresponding process in the aforementioned method embodiment, and will not be repeated here.

[0247] like Figure 8 As shown, an embodiment of the present application further provides an electronic device 200, including a memory 21, a processor 22, and a computer program 23 stored in the memory 21 and executable on the processor 22. When the processor 22 executes the computer program 23, the calibration method of the zero intermediate frequency signal transceiver of the above embodiment is implemented, or the calibration method of the zero intermediate frequency signal transceiver of the above embodiment is implemented.

[0248] The processor 22 may be a central processing unit (CPU), or other general-purpose processors, digital signal processors (DSP), application-specific integrated circuits (ASIC), field-programmable gate arrays (FPGA), or other programmable logic devices, discrete gate or transistor logic devices, discrete hardware components, etc. A general-purpose processor may be a microprocessor or any conventional processor.

[0249] The memory 21 may be an internal storage unit of the electronic device 200. The memory 21 may also be an external storage device of the electronic device 200, such as a plug-in hard disk, a SmartMedia Card (SMC), a Secure Digital (SD) card, a Flash Card, etc. equipped on the electronic device 200. Furthermore, the memory 21 may include both an internal storage unit of the electronic device 200 and an external storage device. The memory 21 is used to store computer programs and other programs and data required by the electronic device 200. The memory 21 may also be used to temporarily store data that has been output or is about to be output.

[0250] An embodiment of the present application further provides a computer-readable storage medium, which stores a computer program. When the computer program is executed by a processor, the calibration method of the zero intermediate frequency signal transceiver of the above embodiment is implemented.

[0251] An embodiment of the present application provides a computer program product. When the computer program product is run on a mobile terminal, the mobile terminal implements the calibration method of the zero intermediate frequency signal transceiver of the above embodiment when executing the computer program product.

[0252] If the integrated unit is implemented as a software functional unit and sold or used as an independent product, it can be stored in a computer-readable storage medium. Based on this understanding, the present application implements all or part of the process of the above-mentioned embodiment method by instructing the relevant hardware through a computer program. The computer program can be stored in a computer-readable storage medium. When the computer program is executed by a processor, it can implement the steps of each of the above-mentioned method embodiments. The computer program includes computer program code, which can be in source code form, object code form, executable file, or some intermediate form. The computer-readable storage medium may include at least: any entity or device capable of carrying computer program code to the camera / electronic device, recording medium, computer memory, read-only memory (ROM), random access memory (RAM), electric carrier signal, telecommunication signal, and software distribution medium. For example, a USB flash drive, mobile hard disk, magnetic disk, or optical disk. In some jurisdictions, according to legislation and patent practice, computer-readable storage media cannot be electric carrier signals or telecommunication signals.

[0253] In the above embodiments, the description of each embodiment has its own focus. For parts that are not described or recorded in detail in a certain embodiment, reference can be made to the relevant description of other embodiments.

[0254] Those skilled in the art will appreciate that the units and algorithm steps of each example described in conjunction with the embodiments disclosed herein can be implemented in electronic hardware, or a combination of computer software and electronic hardware. Whether these functions are performed in hardware or software depends on the specific application and design constraints of the technical solution. Professional and technical personnel can use different methods to implement the described functions for each specific application, but such implementation should not be considered beyond the scope of this application.

[0255] The units described as separate components may or may not be physically separate, and the components shown as units may or may not be physical units, that is, they may be located in one place or distributed across multiple network units. Some or all of the units may be selected according to actual needs to achieve the purpose of the embodiments of the present application.

[0256] The above embodiments are only used to illustrate the technical solutions of the present application, rather than to limit them. Although the present application has been described in detail with reference to the aforementioned embodiments, those skilled in the art should understand that they can still modify the technical solutions described in the aforementioned embodiments, or make equivalent replacements for some of the technical features therein. These modifications or replacements do not deviate the essence of the corresponding technical solutions from the spirit and scope of the technical solutions of the various embodiments of the present application, and should all be included in the scope of protection of the present application.

Claims

1. A calibration method for a zero intermediate frequency signal transceiver, characterized in that: The calibration method comprises: Acquire a modulated radio frequency signal sent by a signal transmitter using a loopback link, and demodulate the radio frequency signal to obtain a baseband signal, wherein the radio frequency signal is a single-tone signal; Determining baseband spectrum information of a signal receiver according to the baseband signal; Based on the baseband spectrum information, determine the imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver, and the DC offset information; Determining a first optimal compensation value of the imbalance information based on the imbalance information and a preset first compensation value range of the imbalance information, and determining a second optimal compensation value of the DC bias information based on the DC bias information and a preset second compensation value range of the DC bias information; Calibrate the imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver according to the first optimal compensation value, and calibrate the DC bias information of the signal receiver according to the second optimal compensation value; The center frequency of the single tone signal is the same as the local oscillator frequency of the signal transmitter, the deviation value between the local oscillator frequency of the signal receiver and the local oscillator frequency of the signal transmitter is less than 1 / 4 of the baseband bandwidth, and the demodulating the radio frequency signal to obtain the baseband signal includes: Demodulate the radio frequency signal to obtain an in-phase signal in the baseband signal, wherein the in-phase signal is: Where I′(t) represents the in-phase signal in the baseband signal of the signal receiver, C Q1 represents the amplitude of the local oscillator leakage of the orthogonal signal of the signal transmitter, A1 represents the amplitude of the in-phase orthogonal signal of the signal transmitter, ω1 represents the local oscillator frequency of the signal transmitter, ω2 represents the local oscillator frequency of the signal receiver, C I1 represents the amplitude of the local oscillator leakage of the in-phase signal of the signal transmitter, Represents the angle of the in-phase and quadrature signals of the signal transmitter, C I2 A magnitude representing a local oscillator leakage of an in-phase signal of the signal receiver; Demodulate the radio frequency signal to obtain an orthogonal signal in the baseband signal, wherein the orthogonal signal is: Wherein, Q′(t) represents the orthogonal signal in the baseband signal of the signal receiver, A2 represents the amplitude of the in-phase orthogonal signal of the signal receiver, represents the angle of the in-phase and quadrature signals of the signal receiver, the C Q1 , C I1 , A1 and is the non-ideal characteristic of the signal transmitter, the C I2 , A2 and is a non-ideal characteristic of the signal receiver; Based on the in-phase signal in the baseband signal and the orthogonal signal in the baseband signal, the baseband signal is obtained, and the baseband signal is: in, represents the baseband signal, I′(t) represents the real part of the baseband signal, and jQ′(t) represents the imaginary part of the baseband signal.

2. The calibration method according to claim 1, characterized in that: The step of determining baseband spectrum information of the signal receiver according to the baseband signal includes: Performing Fourier transform on the baseband signal to determine baseband spectrum information of the signal receiver, the baseband spectrum information being: in, represents the baseband spectrum information of the signal receiver, C Q2 represents the amplitude of the local oscillator leakage of the orthogonal signal of the signal receiver, δ(ω+ω2-ω1) represents the center frequency of the single tone signal, δ(ω+ω1-ω2) represents the image frequency of the signal receiver, δ(ω) represents the local oscillator frequency of the signal receiver, and the C Q2 It is a non-rational characteristic of the signal receiver.

3. The calibration method according to claim 2, characterized in that: The step of determining the imbalance information of the amplitude or angle of the in-phase orthogonal signals of the signal receiver and the DC bias information based on the baseband spectrum information includes: Based on the baseband spectrum information, the imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver is determined as follows: Based on the baseband spectrum information, the DC bias information of the in-phase and quadrature signals of the signal receiver is determined as follows: [2(C I2 +j+C Q2 )]2πδ(ω).

4. The calibration method according to claim 3, characterized in that: Determining a first optimal compensation value of the imbalance information based on the imbalance information and a preset first compensation value range of the imbalance information, and determining a second optimal compensation value of the DC bias information based on the DC bias information and a preset second compensation value range of the DC bias information, including: By using an optimization algorithm, within a preset first compensation value range of the imbalance information, determine The first optimal compensation value of And using an optimization algorithm, within a preset second compensation value range of the DC bias information, determine [2(C I2 +j+C Q2 )|δ(ω) is the second best compensation value.

5. A calibration method for a zero intermediate frequency signal transceiver, characterized in that: The calibration method comprises: Acquire a modulated radio frequency signal sent by a signal transmitter using a loopback link, and demodulate the radio frequency signal to obtain a baseband signal, wherein the radio frequency signal is a single-tone signal; Determining baseband spectrum information of a signal receiver according to the baseband signal; Based on the baseband spectrum information, determine the imbalance information of the amplitude or angle of the in-phase orthogonal signal of the signal transmitter, and the local oscillator leakage information; Determining a first optimal compensation value of the imbalance information based on the imbalance information and a preset first compensation value range of the imbalance information, and determining a third optimal compensation value of the local oscillator leakage information based on the local oscillator leakage information and a preset third compensation value range of the local oscillator leakage information; Calibrate the imbalance information of the amplitude or angle of the in-phase orthogonal signal of the signal transmitter according to the first optimal compensation value, and calibrate the local oscillator leakage information of the signal transmitter according to the third compensation value; The center frequency of the single tone signal is the same as the local oscillator frequency of the signal receiver, the deviation value between the local oscillator frequency of the signal transmitter and the local oscillator frequency of the signal receiver is less than 1 / 4 of the baseband bandwidth, and the demodulating the radio frequency signal to obtain the baseband signal includes: Demodulate the radio frequency signal to obtain an in-phase signal in the baseband signal, wherein the in-phase signal is: Where I'(t) represents the in-phase signal in the baseband signal of the signal receiver, A1 represents the amplitude of the in-phase orthogonal signal of the signal transmitter, and C I1 represents the amplitude of the local oscillator leakage of the in-phase signal of the signal transmitter, w1 represents the local oscillator frequency of the signal transmitter, w2 represents the local oscillator frequency of the signal receiver, C Q1 represents the amplitude of the local oscillator leakage of the orthogonal signal of the signal transmitter, Represents the angle of the in-phase and quadrature signals of the signal transmitter, C I2 The amplitude of the local oscillator leakage representing the in-phase signal of the signal receiver; Demodulate the radio frequency signal to obtain an orthogonal signal in the baseband signal, wherein the orthogonal signal is: Where Q'(t) represents the orthogonal signal in the baseband signal of the signal receiver, represents the angle of the in-phase and quadrature signals at the signal receiver, Represents the angle of the in-phase and quadrature signals at the signal receiver, C Q2 is the irrational characteristic of the signal receiver, C Q1 , C I1 , A1 and is the non-ideal characteristic of the signal transmitter, C I2 , C Q2 and is a non-ideal characteristic of the signal receiver; Based on the in-phase signal in the baseband signal and the orthogonal signal in the baseband signal, the baseband signal is obtained, and the baseband signal is: in, represents the baseband signal, I′(t) represents the real part of the baseband signal, and jQ′(t) represents the imaginary part of the baseband signal.

6. A calibration device for a zero intermediate frequency signal transceiver, characterized in that: The calibration device comprises: An acquisition module is used to acquire a modulated radio frequency signal sent by a signal transmitter using a loopback link, and demodulate the radio frequency signal to obtain a baseband signal, wherein the radio frequency signal is a single-tone signal; A first determination module, configured to determine baseband spectrum information of a signal receiver according to the baseband signal; A second determination module, configured to determine, based on the baseband spectrum information, imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver, and direct current offset information; a third determination module, configured to determine a first optimal compensation value of the unbalance information based on the unbalance information and a preset first compensation value range of the unbalance information, and to determine a second optimal compensation value of the DC bias information based on the DC bias information and a preset second compensation value range of the DC bias information; a calibration module, configured to calibrate the imbalance information of the amplitude or angle of the in-phase and quadrature signals of the signal receiver according to the first optimal compensation value, and to calibrate the DC bias information of the in-phase and quadrature signals of the signal receiver according to the second optimal compensation value; The center frequency of the single tone signal is the same as the local oscillator frequency of the signal transmitter, and the deviation between the local oscillator frequency of the signal receiver and the local oscillator frequency of the signal transmitter is less than 1 / 4 of the baseband bandwidth; The acquisition module is further used to demodulate the radio frequency signal to obtain an in-phase signal in the baseband signal, wherein the in-phase signal is: Where I′(t) represents the in-phase signal in the baseband signal of the signal receiver, C Q1 represents the amplitude of the local oscillator leakage of the orthogonal signal of the signal transmitter, A1 represents the amplitude of the in-phase orthogonal signal of the signal transmitter, ω1 represents the local oscillator frequency of the signal transmitter, ω2 represents the local oscillator frequency of the signal receiver, C I1 represents the amplitude of the local oscillator leakage of the in-phase signal of the signal transmitter, Represents the angle of the in-phase and quadrature signals of the signal transmitter, C I2 A magnitude representing a local oscillator leakage of an in-phase signal of the signal receiver; Demodulate the radio frequency signal to obtain an orthogonal signal in the baseband signal, wherein the orthogonal signal is: Wherein, Q′(t) represents the orthogonal signal in the baseband signal of the signal receiver, A2 represents the amplitude of the in-phase orthogonal signal of the signal receiver, represents the angle of the in-phase and quadrature signals of the signal receiver, the C Q1 , C I1 , A1 and is the non-ideal characteristic of the signal transmitter, the C I2 , A2 and is a non-ideal characteristic of the signal receiver; Based on the in-phase signal in the baseband signal and the orthogonal signal in the baseband signal, the baseband signal is obtained, and the baseband signal is: in, represents the baseband signal, I′(t) represents the real part of the baseband signal, and jQ′(t) represents the imaginary part of the baseband signal.

7. A calibration device for a zero intermediate frequency signal transceiver, characterized in that: The calibration device comprises: An acquisition module is used to acquire a radio frequency signal sent by a signal transmitter, and demodulate the radio frequency signal to obtain a baseband signal, wherein the radio frequency signal is a single-tone signal; A first determination module, configured to determine baseband spectrum information of a signal receiver according to the baseband signal; A second determination module is used to determine the imbalance information of the amplitude or angle of the in-phase orthogonal signal of the signal transmitter and the local oscillator leakage information based on the baseband spectrum information; a third determining module, configured to determine a first optimal compensation value of the imbalance information based on the imbalance information and a preset first compensation value range of the imbalance information, and to determine a third optimal compensation value of the local oscillator leakage information based on the local oscillator leakage information and a preset third compensation value range of the local oscillator leakage information; a calibration module, configured to calibrate the imbalance information of the amplitude or angle of the in-phase orthogonal signal of the signal transmitter according to the first optimal compensation value, and to calibrate the local oscillator leakage information of the signal transmitter according to the third compensation value; The center frequency of the single tone signal is the same as the local oscillator frequency of the signal receiver, and the deviation value between the local oscillator frequency of the signal transmitter and the local oscillator frequency of the signal receiver is less than 1 / 4 of the baseband bandwidth; The acquisition module is also used to demodulate the radio frequency signal to obtain an in-phase signal in the baseband signal, where the in-phase signal is: Where I'(t) represents the in-phase signal in the baseband signal of the signal receiver, A1 represents the amplitude of the in-phase orthogonal signal of the signal transmitter, and C I1 represents the amplitude of the local oscillator leakage of the in-phase signal of the signal transmitter, w1 represents the local oscillator frequency of the signal transmitter, w2 represents the local oscillator frequency of the signal receiver, C Q1 represents the amplitude of the local oscillator leakage of the orthogonal signal of the signal transmitter, Represents the angle of the in-phase and quadrature signals of the signal transmitter, C I2 The amplitude of the local oscillator leakage representing the in-phase signal of the signal receiver; Demodulate the radio frequency signal to obtain an orthogonal signal in the baseband signal, wherein the orthogonal signal is: Where Q'(t) represents the orthogonal signal in the baseband signal of the signal receiver, represents the angle of the in-phase and quadrature signals at the signal receiver, Represents the angle of the in-phase and quadrature signals at the signal receiver, C Q2 is the irrational characteristic of the signal receiver, C Q1 , C I1 , A1 and is the non-ideal characteristic of the signal transmitter, C I2 , C Q2 and is a non-ideal characteristic of the signal receiver; Based on the in-phase signal in the baseband signal and the orthogonal signal in the baseband signal, the baseband signal is obtained, and the baseband signal is: in, represents the baseband signal, I′(t) represents the real part of the baseband signal, and jQ′(t) represents the imaginary part of the baseband signal.

8. An electronic device, characterized in that: The invention comprises a memory, a processor and a computer program stored in the memory and executable on the processor, wherein when the processor executes the computer program, the calibration method for a zero intermediate frequency signal transceiver according to any one of claims 1 to 5 is implemented.

9. A computer-readable storage medium storing a computer program, characterized in that: When the computer program is executed by a processor, the calibration method of a zero intermediate frequency signal transceiver according to any one of claims 1 to 5 is implemented.

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