A salient-pole reluctance type iron core and its design method

Abstract

The present invention discloses a salient-pole reluctance type iron core and its design method, belonging to the technical field of motor design. The method includes: in a two-dimensional Cartesian coordinate system, establishing a Laplace equation satisfied by the scalar magnetic potential distribution in the solution domain formed by the surfaces of the primary and secondary or stator and rotor of the motor facing the air gap, solving the general solution of the scalar magnetic potential in the Laplace equation, and further obtaining the functional relationship satisfied by the salient-pole reluctance type motor iron core to be designed; based on the functional relationship, setting the coordinate point interval to obtain the contour coordinates of the salient-pole reluctance type iron core. At the same time, based on the functional relationship designed by the present invention, with the goal of maximizing the fundamental wave specific permeance, solving for the iron core tooth height that maximizes the fundamental wave permeance, substituting the maximum iron core tooth height and other parameters into the above functional relationship, and solving for the iron core contour coordinates. The method provided by the present invention can accurately and quickly design the structure of the salient-pole reluctance type iron core and maximize the fundamental wave specific permeance amplitude without increasing the harmonic content.

Description

Technical Field

[0001] The present invention belongs to the technical field of motor design, and more specifically, relates to a salient-pole reluctance iron core and a design method thereof. Background Art

[0002] Salient-pole reluctance iron cores are widely used in devices such as reluctance motors and reluctance resolvers, and have advantages such as simple structure, firmness and reliability, and have received extensive attention in the field of motor design.

[0003] The shape of the salient-pole reluctance iron core is the key factor determining the air-gap specific permeance distribution of the above-mentioned devices, and the air-gap specific permeance distribution directly affects the performance of the devices. Therefore, some scholars have proposed an inverse design method to make the air-gap specific permeance distribution caused by the salient-pole reluctance iron core more sinusoidal, thereby reducing the harmonic content. The inverse design method can be mainly divided into two categories: the finite element method and the analytical method. The first method first solves the air-gap magnetic density under the initial shape of the iron core through the first type of boundary conditions, periodic or semi-periodic boundary conditions, and compares it with the ideal air-gap magnetic density with a sinusoidal distribution. Taking the deviation between the two as the convergence criterion, the shape of the iron core is changed according to certain rules until the deviation between the two is less than the set value, and finally the shape of the iron core is output. The second method first assumes that the magnetic field in the air gap only contains the normal component along the center line of the air gap, and then expresses the air-gap specific permeance distribution as a function of the air-gap length, and reversely solves the air-gap length by setting the ideal specific permeance distribution function, and finally obtains the shape of the iron core.

[0004] However, the above methods all have a certain gap from the ideal iron core shape. For the first method, too large a search step or deviation setting will lead to an unsatisfactory design result, and too small a search step or deviation setting will significantly increase the design duration, and the method can only obtain discrete results. For the second method, although the shape of the iron core can be obtained quickly, this method regards the air-gap magnetic field of the motor as one-dimensional and only considers the normal component of the air-gap magnetic field, but in fact, the air-gap magnetic field at most positions in the actual device contains more than just the normal component, so there is a large deviation in this method itself. In addition, neither method can directly obtain the iron core structure with the maximum fundamental specific permeance, and additional parametric scanning is required. Summary of the Invention

[0005] Aiming at the defects and improvement requirements of the prior art, the present invention provides a salient-pole reluctance iron core and a design method thereof, aiming to accurately and quickly design an ideal iron core shape.

[0006] To achieve the above object, according to one aspect of the present invention, a design method of a salient-pole reluctance iron core is provided, including the steps:

[0007] Step S1. In a two-dimensional Cartesian coordinate system, establish the Laplace equation satisfied by the scalar magnetic potential distribution within the solution domain, where the solution domain is the solution domain formed by the surfaces of the primary and secondary of a linear motor facing the air gap or the solution domain formed by the surfaces of the stator and rotor of a rotary motor facing the air gap; the secondary of the linear motor is a salient-pole reluctance core, and the rotor of the rotary motor is a salient-pole reluctance core;

[0008] Step S2. Solve the general solution of the scalar magnetic potential in the Laplace equation

[0009] Step S3. Solve the undetermined coefficients in the general solution to obtain the functional relationship between the dimensional parameters of the salient-pole reluctance core and the contour coordinates of the salient-pole reluctance core;

[0010] Step S4. Based on the functional relationship, set the coordinate point interval to obtain the contour coordinates of the salient-pole reluctance core.

[0011] Further, for the linear motor, the functional relationship is:

[0012]

[0013] In the formula:

[0014]

[0015] where τ t is the tooth pitch of the salient-pole reluctance core, h s is the tooth height of the salient-pole reluctance core, δ is the physical air-gap length, x and y are respectively the abscissa and ordinate of the salient-pole reluctance core in the Cartesian coordinate system, and the x direction is the longitudinal direction of the linear motor.

[0016] Further, for the rotary motor, the functional relationship is:

[0017]

[0018] In the formula:

[0019]

[0020] where R si is the inner radius of the motor stator, R ro is the outer radius of the motor rotor, N r is the number of salient poles of the rotor core, h s is the tooth height of the salient-pole reluctance core, and r and θ are respectively the radial distance and angle in the polar coordinate system.

[0021] Further, after step S3, it further includes the step: ​

[0022] Optimize the functional relationship with the objective of maximizing the fundamental wave specific permeance to obtain the optimal core tooth height h that maximizes the fundamental wave specific permeance smax The equation satisfied thereby, and use the optimal core tooth height h smax As the salient pole reluctance type core tooth height

[0023] Furthermore, for a linear motor, the equation satisfied by the optimal core tooth height h smax Is as follows

[0024]

[0025] Where τ t Is the tooth pitch of the salient pole reluctance type core, h smax Is the optimal core tooth height, and δ is the physical air gap length

[0026] Furthermore, for a rotary motor, the equation satisfied by the optimal core tooth height h smax Is as follows

[0027]

[0028] In the formula

[0029]

[0030] Where R si Is the inner radius of the motor stator, R ro Is the outer radius of the motor rotor, N r Is the number of salient poles of the rotor core, h smax Is the optimal core tooth height

[0031] Furthermore, after obtaining the optimal core tooth height h smax The following steps are further included

[0032] Compare the core yoke thickness d corresponding to the optimal core tooth height h smax With the preset minimum yoke thickness d min For comparison

[0033] If d < d min , then use the maximum core tooth height as the optimal core tooth height h smax , where the maximum core tooth height is the difference between the core height and the preset minimum yoke thickness d min

[0034] According to the second aspect of the present invention, there is provided a salient pole reluctance type core designed by the salient pole reluctance type core design method described in any one of the first aspects

[0035] ​According to the third aspect of the present invention, a salient pole reluctance type iron core is provided, and a functional relationship is satisfied between the dimensional parameters and the contour coordinates of the salient pole reluctance type iron core;

[0036] For a linear motor, the secondary of the linear motor is a salient pole reluctance type iron core, and the functional relationship is:

[0037]

[0038] In the formula:

[0039]

[0040] where τ t is the tooth pitch of the salient pole reluctance type iron core, h s is the tooth height of the salient pole reluctance type iron core, δ is the physical air gap length, x and y are respectively the abscissa and ordinate of the salient pole reluctance type iron core in the Cartesian coordinate system, and the x direction is the longitudinal direction of the linear motor;

[0041] For a rotary motor, the rotor of the rotary motor is a salient pole reluctance type iron core, and the functional relationship is:

[0042]

[0043] In the formula:

[0044]

[0045] where R si is the inner radius of the motor stator, R ro is the outer radius of the motor rotor, N r is the number of salient poles of the rotor iron core, h s is the tooth height of the salient pole reluctance type iron core, and r and θ are respectively the polar radius and angle in the polar coordinate system.

[0046] Furthermore, there is an optimal tooth height h of the salient pole reluctance type iron core that maximizes the fundamental specific permeance smax ;

[0047] For a linear motor, the equation satisfied by the optimal tooth height h smax is:

[0048]

[0049] where τ t is the tooth pitch of the salient pole reluctance type iron core, h smax is the optimal tooth height, and δ is the physical air gap length;

[0050] For a rotary motor, the equation satisfied by the optimal tooth height h smax is:

[0051]

[0052] In the formula:

[0053]

[0054] Wherein, R si is the inner radius of the motor stator, and R ro is the outer radius of the motor rotor, N r is the number of salient poles of the rotor core, and h smax is the optimal core tooth height.

[0055] Generally speaking, through the above technical solutions conceived by the present invention, the following beneficial effects can be achieved:

[0056] (1) For different types of motors, the design method of the present invention establishes the Laplace equation satisfied by the scalar magnetic potential distribution in the solution domain formed by the surfaces of the primary and secondary or stator and rotor of the motor facing the air gap in the two-dimensional Cartesian coordinate system. Based on the relationship between the general solution of the scalar magnetic potential of this equation and the structural parameters of the motor, the functional relationship satisfied by the salient pole reluctance motor core to be designed is obtained, and then the shape of the core is obtained. This analytical design method of the present invention is based on the two-dimensional Cartesian coordinate system and takes into account both the radial and tangential air gap magnetic fields of the motor. The shape of the designed core is more in line with the ideal core shape. Compared with the existing analytical methods, the finally obtained core shape is more accurate, and there are no defects in the finite element method, and the speed is faster.

[0057] (2) Further, based on the functional relationship designed by the present invention, with the goal of maximizing the fundamental wave specific permeance, the equation between the core tooth height that maximizes the fundamental wave specific permeance and other dimensional parameters of the salient pole reluctance core can be obtained. By directly using this equation, the structure that maximizes the fundamental wave specific permeance amplitude can be directly obtained without increasing the harmonic content, and there is no need for additional parametric scanning.

[0058] (3) The present invention provides a salient pole reluctance core. For different types of motors, by directly using the functional relationship between the dimensional parameters of the salient pole reluctance core and the contour coordinates of the salient pole reluctance core, the contour coordinates of the core can be directly solved, and the core structure can be accurately and quickly drawn.

[0059] All in all, compared with the design methods based on the finite element method or traditional analytical methods, the method provided by the present invention can quickly and accurately obtain the ideal shape of the salient pole reluctance core, and can directly obtain the structure that maximizes the fundamental wave specific permeance amplitude without increasing the harmonic content, and there is no need for additional parametric scanning, solving the problems of long design time or inaccurate design results in the existing methods. Description of the Drawings

[0060] Figure 1 The overall flowchart of a salient pole reluctance type iron core design method provided by the present invention;

[0061] Figure 2 The flowchart of a salient pole reluctance type iron core design method provided by the present invention;

[0062] Figure 3 The structure of the linear motor salient pole reluctance type iron core designed for Embodiment 1 of the present invention;

[0063] Figure 4 The structure of the rotary motor salient pole reluctance type iron core designed for Embodiment 2 of the present invention. Specific embodiments

[0064] In order to make the objectives, technical solutions and advantages of the present invention clearer, the present invention will be further described in detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are only used to explain the present invention and are not used to limit the present invention. In addition, the technical features involved in the various embodiments of the present invention described below can be combined with each other as long as they do not conflict with each other.

[0065] As Figure 1 shown, the design method of the salient pole reluctance type iron core provided by the present invention mainly includes the following steps:

[0066] Select the functional relationship for designing the iron core structure according to the type of motor. When the type of motor is a linear motor, select the functional relationship #1, and when the type of motor is a rotary motor, select the functional relationship #2.

[0067] Specifically, for a linear motor, the secondary adopts a salient pole reluctance type iron core structure, and the functional relationship #1 is:

[0068]

[0069] In the formula:

[0070]

[0071] where τ t is the tooth pitch of the salient pole reluctance type iron core, h s is the tooth height of the salient pole reluctance type iron core, δ is the physical air gap length, x and y are respectively the abscissa and ordinate of the salient pole reluctance type iron core in the Cartesian coordinate system, and the x direction is the longitudinal direction of the linear motor.

[0072] For a rotary motor, its rotor adopts a salient pole reluctance type iron core structure, and the selected functional relationship #2 is:

[0073]

[0074] In the formula:

[0075]

[0076] Among them, R si is the inner radius of the motor stator, and R ro is the outer radius of the motor rotor. N r is the number of salient poles of the rotor core. r and θ are the radial distance and angle in polar coordinates respectively. h s is the tooth height of the salient-pole reluctance core.

[0077] Substitute the parameters of the to-be-designed salient-pole reluctance core structure into the above function relationship #1 or function relationship #2, set the coordinate point interval, solve the coordinates of the core contour, and obtain the to-be-designed salient-pole reluctance core structure.

[0078] Specifically, for a linear motor, substitute the tooth pitch τ t of the salient-pole reluctance core, the tooth height h s of the core, and the air-gap length δ into the above function relationship #1, set the coordinate point interval, solve the abscissa x and ordinate y of the core, and then draw the core structure;

[0079] For a rotating motor, substitute the inner radius R si of the motor stator, the outer radius R ro of the motor rotor, the number of salient poles N r of the rotor core, and the tooth height h s of the core into the above function relationship #2, set the coordinate point interval, solve the radial distance r and angle θ of the core in polar coordinates, and then draw the core structure.

[0080] As a further preferred solution of the present invention, aiming at maximizing the fundamental-wave specific permeance, optimize the above function relationship #1 or function relationship #2 to obtain an equation between the optimal tooth height h smax that maximizes the fundamental-wave specific permeance and other dimensional parameters of the salient-pole reluctance core;

[0081] Specifically, for a linear motor, substitute the tooth pitch τ t of the salient-pole reluctance core and the air-gap length δ into Equation #1 to obtain the optimal tooth height h smax that maximizes the fundamental-wave specific permeance;

[0082] For a rotating motor, substitute the inner radius R si of the motor stator, the outer radius R ro of the motor rotor, and the number of salient poles N r of the rotor core into Equation #2 to obtain the optimal tooth height h smax that maximizes the fundamental-wave specific permeance;

[0083] Among them, Equation #1 is:

[0084]

[0085] Equation #2 is:

[0086]

[0087] The optimal core tooth height h with the maximum fundamental wave ratio permeability is obtained smax Substitute the other dimensional parameters of the salient-pole reluctance core into the corresponding function, set the coordinate point interval, and solve for the coordinates of the core outline. The number of coordinate points obtained is related to the coordinate point interval set when solving the equation. The smaller the step size and the greater the number of coordinate points, the more accurate the design result.

[0088] Specifically, for the linear motor, the tooth pitch τ of the salient pole reluctance core is t , optimal core tooth height h smax Substitute the air gap length δ into the above function relationship #1, set the coordinate point interval, solve the abscissa x and ordinate y of the core, and then draw the core structure;

[0089] For rotating motors, the inner radius R of the motor stator si , motor rotor outer radius R ro 、N number of salient poles of the rotor core r And the optimal core tooth height h smax Substitute the above function relationship #2, set the coordinate point interval, solve the polar diameter r and angle θ of the core in polar coordinates, and then draw the core structure.

[0090] As a further preferred solution of the present invention, the optimal core tooth height h is obtained. smax Finally, the steps include:

[0091] The optimal core tooth height h smax The corresponding core yoke thickness d and the preset minimum yoke thickness d min In comparison, if d<d min , then the maximum core tooth height is taken as the optimal core tooth height h smax , where the maximum core tooth height is the core height and the preset minimum yoke thickness d min The difference between

[0092] If d≥d min , the optimal core tooth height h is obtained smax This is the optimal tooth height.

[0093] Substitute the maximum core tooth height and other dimensional parameters of the salient-pole reluctance core into the corresponding functional relationship, set the coordinate point interval, and solve the coordinates of the core contour.

[0094] Specifically, if Figure 2 As shown, the functional relationship for designing the core structure according to the motor type is selected, including the following steps:

[0095] Step S1: In a two-dimensional Cartesian coordinate system, for a linear motor, establish the Laplace equation satisfied by the scalar magnetic potential distribution in the solution domain formed by the surfaces of the primary and secondary sides facing the air gap; for a rotary motor, establish the Laplace equation satisfied by the scalar magnetic potential distribution in the solution domain formed by the surfaces of the stator and rotor facing the air gap.

[0096] Step S2: Obtain the general solution of the scalar magnetic potential in the above equation.

[0097] Step S3: Solve for the undetermined coefficients in the general solution to obtain the tooth pitch τ of the salient-pole reluctance core, the tooth height h of the core, t the air gap length δ, and the functional relationship #1 between the abscissa and ordinate of the salient-pole reluctance core in the Cartesian coordinate system, or obtain the inner radius R of the motor stator, s the outer radius R of the motor rotor, si the number of salient poles N of the rotor core, ro and the tooth height h of the core, r as well as the functional relationship #2 between the polar radius r and the angle θ of the core in the polar coordinate system. s Specifically, for a linear motor, assume that the primary surface is smooth and the secondary adopts a salient-pole reluctance core structure. Let the surfaces of the primary and secondary sides facing the air gap be equipotential surfaces. The scalar magnetic potential distribution in the solution domain formed by them satisfies the Laplace equation, and its expression in the two-dimensional Cartesian coordinate system is:

[0098] wherein,

[0099]

[0100] represents the general solution of the scalar magnetic potential;

[0101] The general solution of the scalar magnetic potential is obtained by the method of separation of variables and organized as:

[0102]

[0103]

[0104]

[0105] From the fact that the scalar magnetic potential on the primary surface is 0, we can obtain:

[0106]

[0107] Then the general solution of the scalar magnetic potential can be simplified as:

[0108] ​​The magnetic field intensity is the negative gradient of the scalar magnetic potential, and the normal air-gap magnetic field distribution can be obtained:

[0109]

[0110] Assume that the normal air-gap magnetic field distribution on the primary surface only contains the average component and the fundamental wave component, and its expression is:

[0111]

[0112] In the formula, H av is the average magnetic field component, and H m is the amplitude of the fundamental wave magnetic field component.

[0113] Furthermore, we can obtain:

[0114]

[0115] Assume that the scalar magnetic potential on the secondary surface is 1, then we have:

[0116]

[0117] Based on this relationship, the functional relationship #1 is obtained.

[0118] For a rotating electrical machine, assuming that the stator surface is smooth and the rotor adopts a salient-pole reluctance core structure, and setting that the surfaces of the stator and rotor facing the air gap are equipotential scalar magnetic surfaces, the scalar magnetic potential distribution in the solution domain formed by the two satisfies the Laplace equation, and its expression in the polar coordinate system is:

[0119]

[0120] The general solution of the scalar magnetic potential is obtained by using the method of separation of variables and is sorted out as:

[0121]

[0122] In the formula, m0, m1, m2, A, B, C, and D are all undetermined coefficients.

[0123] From the fact that the scalar magnetic potential on the stator surface is 0, we can obtain:

[0124]

[0125] The magnetic field intensity is the negative gradient of the scalar magnetic potential, and the normal air-gap magnetic field distribution can be obtained:

[0126]

[0127] Assume that the normal air-gap magnetic field distribution on the stator surface only contains the average component and the fundamental wave component, and its expression is:

[0128]

[0129] Furthermore, we obtain:

[0130]

[0131] Let the scalar magnetic potential on the rotor surface be R si , then we have:

[0132]

[0133] Based on this relationship, the functional relationship #2 is finally solved.

[0134] It should be noted that in the actual iron core design, it is only necessary to directly adopt the functional relationship #1 or the functional relationship #2 provided by the present invention. Based on this, the present invention also provides a salient-pole reluctance iron core, and the parameters of the salient-pole reluctance iron core satisfy the functional relationship #1 or the functional relationship #2.

[0135] Specifically, the establishment processes of the above equations #1 and #2 are as follows:

[0136] From electromagnetic analysis, it can be seen that when the tooth pitch of the salient-pole reluctance iron core is very small, it will be difficult to manufacture sufficient air-gap specific permeance variation by continuously increasing the iron core tooth height h s Therefore, for a specific motor size and number of teeth, there is an optimal iron core tooth height h smax under the premise of not generating additional specific permeance harmonics, which makes the fundamental specific permeance reach the maximum.

[0137] For a linear motor, the point on the secondary surface farthest from the primary surface is located at x = τ t / 2. Substituting this angle into the functional relationship #1, we get:

[0138]

[0139] Let f1 = K0y - 1, Let f1' = f2', and solve to get:

[0140]

[0141] Also, since y0 = δ + h s , the equation can be transformed into equation #1.

[0142] For a rotating motor, the point on the rotor surface farthest from the stator surface is located at θ = π / N r . Substituting this angle into the functional relationship #2, we get:

[0143]

[0144] Let Let g1' = g2', and solve to get

[0145]

[0146] Also, since r = R ro -h s <R ro , thus this equation can be transformed into Equation #2.

[0147] It should be noted that in actual iron core design, it is only necessary to directly adopt Equation #1 or Equation #2 provided by the present invention.

[0148] In order to make the design method and advantages of the present invention clearer, the following will be described in conjunction with two specific embodiments.

[0149] Embodiment 1

[0150] This embodiment is directed to the design of a salient pole reluctance type iron core for a linear motor.

[0151] First, select Function Relationship #1;

[0152] Then, substitute the air gap length δ = 0.5×10 -3 m and the tooth pitch τ t = 28.6×10 -3 m into Equation #1, and solve for the iron core tooth height h that maximizes the fundamental specific permeance smax = 3.6×10 -3 m;

[0153] Secondly, substitute the above parameters into Function Relationship #1, and solve for the profile coordinates. Some of the coordinate points are as follows:

[0154] (0.00000000,0.0005000)

[0155] (0.00014229,0.0005001)

[0156] (0.00028458,0.0005004)

[0157] (0.00042687,0.0005009)

[0158] (0.00056915,0.0005016)

[0159] (0.00071144,0.0005025)

[0160] (0.00085373,0.0005036)

[0161] (0.00099602,0.0005049)

[0162] (0.00113831,0.0005065)

[0163] (0.00128060, 0.0005082)

[0164] ……

[0165] Finally, draw the iron core structure according to the solved profile coordinates as Figure 3 shown below.

[0166] Embodiment 2

[0167] This embodiment is designed for the salient pole reluctance iron core of a certain rotating electrical machine.

[0168] First, select the functional relationship #2.

[0169] Then, substitute the inner radius R of the stator si = 63.5×10 -3 m, the outer radius R of the rotor ro = 63.15×10 -3 m, and the number of rotor salient poles N r = 6 into Equation #2, and solve for the iron core tooth height h that maximizes the fundamental specific permeance smax = 5.6×10 -3 m;

[0170] Secondly, substitute the above parameters into the functional relationship #2, solve for the profile coordinates, and some of the coordinate points are as follows:

[0171] (0.063150, 0.000000)

[0172] (0.063148, 0.000441)

[0173] (0.063143, 0.000882)

[0174] (0.063135, 0.001322)

[0175] (0.063123, 0.001763)

[0176] (0.063108, 0.002204)

[0177] (0.063090, 0.002644)

[0178] (0.063068, 0.003085)

[0179] (0.063042, 0.003525)

[0180] (0.063014, 0.003964)

[0181] ……

[0182] Finally, draw the iron core structure according to the solved contour coordinates as Figure 4 shown.

[0183] For the design method of the present invention, for different types of motors, in the two-dimensional Cartesian coordinate system, a Laplace equation satisfied by the scalar magnetic potential distribution in the solution domain formed by the surface of the motor facing the air gap is established. Based on the relationship between the general solution of the scalar magnetic potential of this equation and the structural parameters of the motor, the functional relationship satisfied by the iron core of the salient pole reluctance motor to be designed is obtained (function relationship #1 for linear motors and function relationship #2 for rotary motors). Furthermore, the shape of the iron core is obtained. This analytical design method of the present invention is based on the two-dimensional Cartesian coordinate system and takes into account both the radial and tangential air gap magnetic fields of the motor. The designed shape of the iron core is more in line with the ideal iron core shape. Compared with the existing analytical methods, the designed shape of the iron core is more accurate, and there are no defects in the finite element method, and the speed is faster.

[0184] Furthermore, based on function relationship #1 or function relationship #2 designed by the present invention, with the goal of maximizing the fundamental wave specific permeance, the tooth height h of the iron core that maximizes the fundamental wave specific permeance can be obtained smax and equation #1 or equation #2 between the tooth height h of the iron core and other dimensional parameters of the salient pole reluctance type iron core. By directly using this equation, the structure that maximizes the fundamental wave specific permeance amplitude can be directly obtained without increasing the harmonic content, and there is no need for additional parametric scanning.

[0185] It is easy for those skilled in the art to understand that the above are only preferred embodiments of the present invention and are not used to limit the present invention. Any modifications, equivalent replacements, and improvements made within the spirit and principle of the present invention should be included in the protection scope of the present invention.

Claims

1. A salient pole reluctance type iron core design method, characterized in that, Including the steps: Step S1: In a two-dimensional Cartesian coordinate system, establish the Laplace equation satisfied by the scalar magnetic potential distribution within the solution domain, where the solution domain is the solution domain formed by the surfaces of the primary and secondary of the linear motor facing the air gap or the solution domain formed by the surfaces of the stator and rotor of the rotary motor facing the air gap; the secondary of the linear motor is a salient-pole reluctance core, and the rotor of the rotary motor is a salient-pole reluctance core; Step S2, solve the general solution of the scalar magnetic potential in the Laplace equation ; Step S3: Solve the general solution for the undetermined coefficients to obtain the functional relationship between the dimensional parameters of the salient-pole reluctance type iron core and the contour coordinates of the salient-pole reluctance type iron core; Step S4: Based on the function relationship, set the coordinate point interval to obtain the contour coordinates of the salient-pole reluctance core; For the linear motor, the function relationship is: In the formula: Among them, τ t is the tooth pitch of the salient pole reluctance type iron core, h s is the tooth height of the salient pole reluctance type iron core, δ is the physical air gap length, x and y are respectively the abscissa and ordinate of the salient pole reluctance type iron core in the Cartesian coordinate system, and the x direction is the longitudinal direction of the linear motor; For the rotary motor, the function relationship is: In the formula: Among them, R si is the inner radius of the motor stator, and R ro is the outer radius of the motor rotor. N r is the number of salient poles of the rotor core, h s is the tooth height of the salient-pole reluctance type iron core. r and θ are the pole radius and the angle in polar coordinates respectively.

2. The salient-pole reluctance type iron core design method according to claim 1, wherein After step S3, it further includes the step: Optimize the functional relationship with the goal of maximizing the fundamental wave specific permeance to obtain the optimal core tooth height h that maximizes the fundamental wave specific permeance smax The equation satisfied by smax is used as the salient pole reluctance type core tooth height.

3. The salient-pole reluctance type iron core design method according to claim 2, characterized in that For the linear motor, the optimal core tooth height h smax satisfies the following equation: Among them, τ t is the tooth pitch of the salient pole reluctance type iron core, h smax is the optimal tooth height of the iron core, and δ is the physical air gap length.

4. The salient pole reluctance type iron core design method according to claim 2, characterized in that For a rotating electrical machine, the optimal core tooth height h smax satisfies the following equation: In the formula: Among them, R si is the inner radius of the motor stator, and R ro is the outer radius of the motor rotor. N r is the number of salient poles of the rotor core, and h smax is the optimal core tooth height.

5. The salient-pole reluctance type iron core design method according to claim 2, characterized in that Obtain the optimal core tooth height h smax After that, it further includes the steps: Compare the optimal core tooth height h smax with the corresponding core yoke thickness d and the preset minimum yoke thickness d min ; If d < d min , then the maximum core tooth height is taken as the optimal core tooth height h smax , where the maximum core tooth height is the difference between the core height and the preset minimum yoke thickness d min .

6. A salient pole reluctance type iron core, characterized in that, Designed by the salient-pole reluctance core design method according to any one of claims 1-5.

7. A salient pole reluctance type iron core, characterized in that, There is a function relationship between the dimensional parameters of the salient-pole reluctance core and the contour coordinates of the salient-pole reluctance core; For the linear motor, the secondary of the linear motor is a salient-pole reluctance core, and the function relationship is: In the formula: Among them, τ t is the tooth pitch of the salient pole reluctance type iron core, h s is the tooth height of the salient pole reluctance type iron core, δ is the physical air gap length, x and y are respectively the abscissa and ordinate of the salient pole reluctance type iron core in the Cartesian coordinate system, and the x direction is the longitudinal direction of the linear motor; For the rotary motor, the rotor of the rotary motor is a salient-pole reluctance core, and the function relationship is: In the formula: Among them, R si is the inner radius of the motor stator, and R ro is the outer radius of the motor rotor. N r is the number of salient poles of the rotor core, h s is the tooth height of the salient pole reluctance type iron core. r and θ are the pole radius and angle in polar coordinates respectively.

8. The salient pole reluctance type iron core according to claim 7, wherein, The salient-pole reluctance type iron core has an optimal iron core tooth height h that maximizes the fundamental specific permeance smax ; For the linear motor, the optimal core tooth height h smax satisfies the following equation: where τ t is the tooth pitch of the salient-pole reluctance core, h smax is the optimal tooth height of the core, and δ is the physical air-gap length; For a rotating electrical machine, the optimal core tooth height h smax satisfies the following equation: In the formula: Among them, R si is the inner radius of the motor stator, and R ro is the outer radius of the motor rotor. N r is the number of salient poles of the rotor core, and h smax is the optimal core tooth height.

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