A magnetic coupling-based energy transmission insulation power supply system

Abstract

This invention provides a power supply system for energy-transfer insulators based on magnetic coupling. The system includes: a high-current generator, an energy-harvesting transformer, a high-frequency power conversion device, a magnetic coupler, and an AC power supply. The high-current generator generates a high current simulating the operating conditions of a transmission line. The energy-harvesting transformer, connected in series with the high-current generator, senses the electrical energy available for use by the high-frequency power conversion device from the high current. The high-frequency power conversion device, connected to the output terminal of the energy-harvesting transformer, converts the electrical energy into high-frequency AC power. The magnetic coupler, connected to the output terminal of the high-frequency power conversion device, transmits the high-frequency AC power to the input terminal of the energy-transfer insulator. The AC power supply, connected to the high-voltage terminal of the energy-transfer insulator, provides a high-frequency power voltage to the energy-transfer insulator. This invention solves the insulation problem between the energy-harvesting transformer and the high-voltage terminal of the tested energy-transfer insulator, ensuring safety during the testing process.

Description

Technical Field

[0001] The embodiments of the present invention relate to the field of wireless power transmission, and more particularly to a power supply system based on magnetic coupling power transfer insulators. Background Technology

[0002] Online monitoring devices are an effective measure to ensure the safe and reliable operation of transmission lines. Due to the wide distribution and long distances of transmission lines, magnetic resonant coupling wireless power transfer is often used. Among magnetic resonant coupling wireless power transfer methods, the wireless power transfer scheme based on multi-stage magnetic resonant wireless power transfer insulators is closest to practical applications. This scheme combines the power transfer insulators of transmission lines with multi-stage magnetic resonant coupling coils, achieving twice the result with half the effort. Therefore, before the wireless power transfer scheme based on multi-stage magnetic resonant wireless power transfer insulators is put into practical application, the power transmission performance testing of multi-stage magnetic resonant wireless power transfer insulators is particularly important.

[0003] In current multi-stage magnetic resonance wireless power transfer insulator testing systems, high-current generators and AC power supplies are often used to provide the high current and high voltage required for testing multi-stage magnetic resonance wireless power transfer insulators. The output terminal of the power harvesting transformer and the AC power supply are directly connected to the high-voltage terminal of the power transfer insulator through wires. The insulation between the AC power supply and the power harvesting transformer is difficult to guarantee reliably, and even serious leakage may occur. Summary of the Invention

[0004] To ensure insulation between the AC power supply and the energy harvesting transformer and avoid leakage, this invention proposes a power supply system based on magnetic coupling and an energy transfer insulator.

[0005] In a first aspect, the present invention provides a power supply system based on a magnetically coupled energy transfer insulator, the system comprising:

[0006] High current generating device, energy harvesting transformer, high frequency power conversion device, magnetic coupler, AC power supply;

[0007] A high-current generator is used to generate high currents simulating the operating conditions of power transmission lines.

[0008] An energy harvesting transformer, connected in series with a high-current generator, is used to sense electrical energy in a high-current source that can be utilized by a high-frequency power conversion device.

[0009] A high-frequency power conversion device is connected to the output terminal of an energy harvesting transformer and is used to convert electrical energy into high-frequency AC power.

[0010] A magnetic coupler is connected to the output of a high-frequency power conversion device and is used to transmit high-frequency AC power to the input of a power insulator.

[0011] An AC power supply is connected to the high-voltage end of the energy-transfer insulator to provide the energy-transfer insulator with a high-frequency power voltage.

[0012] Considering that existing power transfer insulator testing systems use high-current generators and AC power supplies to simulate the high current and high voltage of actual transmission lines, and that the output terminal of the power harvesting transformer and the AC power supply are directly connected to the high-voltage end of the power transfer insulator via wires, the insulation between the AC power supply and the power harvesting transformer is difficult to reliably guarantee. Therefore, the system of this invention changes the connection between the output terminal of the power harvesting transformer and the high-voltage end of the power transfer insulator from a direct wire connection to a wireless power transmission method based on magnetic coupling. This eliminates the constraints of wires. The output terminal of the power harvesting transformer is connected to the input terminal of the high-frequency power conversion device, and the high-frequency AC current is transmitted from low voltage to high voltage through a magnetic coupler. There is no wire connection between the transmitting coil and the receiving coil in the magnetic coupler, thus solving the insulation problem between the power harvesting transformer and the high-voltage end of the tested power transfer insulator and reliably ensuring the safe operation of the power transfer insulator testing system.

[0013] In conjunction with the first aspect, in a first embodiment of the first aspect, the magnetic coupler includes a receiving coil and a transmitting coil; both the receiving coil and the transmitting coil are DD coils arranged coaxially with the energy-transmitting insulator.

[0014] The magnetic field generated by the magnetic coupler coil can couple with the embedded coil in the power insulator, making it impossible to accurately measure the power and efficiency of the power insulator. In the above embodiment, both the receiving and transmitting coils in the magnetic coupler are DD coils arranged coaxially with the power insulator. This limits the mutual magnetic flux between the DD coil and the embedded coil in the power insulator to zero, achieving decoupling between the magnetic coupler coil and the embedded coil in the power insulator. This avoids the coupling effect between the magnetic field generated by the magnetic coupler coil and the embedded coil in the power insulator, thus allowing for accurate measurement of the power and efficiency of the power insulator.

[0015] In conjunction with the first aspect, in the second embodiment of the first aspect, the system further includes: a transmitter compensation network and a receiver compensation network;

[0016] The input of the transmitter compensation network is connected to the output of the high-frequency power conversion device, and the output of the transmitter compensation network is connected to the input of the magnetic coupler.

[0017] The input of the receiving end compensation network is connected to the output of the magnetic coupler, and the output of the receiving end compensation network is connected to the input of the energy transfer insulator.

[0018] The transmitter compensation network and receiver compensation network are used to ensure that the output current of the high-frequency power conversion device is the same as the input current of the power insulator.

[0019] In the process of wirelessly transmitting the harvested current to the high-voltage end of the power insulator using a magnetic coupler, the current received at the high-voltage end of the power insulator is affected by the electrical parameters of the magnetic coupler. The current input to the power insulator is no longer the same as the current when the high-frequency power conversion device is wired to the power insulator. Therefore, in this embodiment of the invention, a transmitter compensation network and a receiver compensation network are added to ensure that the output current of the high-frequency power conversion device is the same as the input current of the power insulator, which can better simulate the actual situation of the power insulator under various transmission line operating conditions.

[0020] In conjunction with the first embodiment of the first aspect, in the third embodiment of the first aspect, the transmitting coil is excluded from a spherical region centered on the centroid of the DD coil in the receiving coil, the radius of which is determined based on the insulation distance between the receiving coil and the transmitting coil.

[0021] In conjunction with the third embodiment of the first aspect, in the fourth embodiment of the first aspect, both the receiving coil and the transmitting coil are confined within a square region, the side length of which is determined based on the radius of the spherical region.

[0022] In conjunction with the first embodiment of the first aspect, in the fifth embodiment of the first aspect, the number of turns of the receiving coil is determined by the following formula:

[0023] 4*n*d <k4*L

[0024] 2*n*d <k5*W

[0025] Where n is the number of turns of the receiving coil, d is the diameter of the Litz wire in the receiving coil, which is determined by the coil current through finite element simulation; k4 and k5 are constants, determined by finite element simulation, and L and W are the length and width of the receiving coil, respectively.

[0026] In conjunction with the first embodiment of the first aspect, in the sixth embodiment of the first aspect, the insulation distance between the transmitting coil and ground is determined according to the following formula:

[0027] d2≥U1 / (E*K T )*f2(d2)

[0028] Where d2 is the insulation distance between the transmitting coil and ground; U1 is the voltage of the equalizing ring; E is the allowable field strength of the air gap; K T It is the atmospheric condition correction factor, K T =k1*k2, where k1 and k2 are the air density correction factor and humidity correction factor, respectively; f2 is the non-uniformity coefficient of the spherical plate electrode, f2 = 0.9*(1+d2 / r2), and r2 is the equivalent radius of the spherical plate electrode.

[0029] In conjunction with the second embodiment of the first aspect, in the seventh embodiment of the first aspect, the parameters in the transmitter compensation network and the receiver compensation network are determined by the following formula:

[0030]

[0031] Where ω is the angular frequency, L p L is used to compensate for the self-inductance of the transmitting coil in the transmitting end compensation network. s To compensate for the self-inductance of the receiving coil in the receiving end compensation network, M ps C0 is the mutual inductance between the transmitting and receiving coils, C0 is the parallel compensation capacitor of the transmitting compensation network, and L0 is the series compensation inductance of the transmitting compensation network. p C is the series compensation capacitor for the transmitter compensation network. s This is a series compensation capacitor for the receiving end compensation network.

[0032] In conjunction with the first aspect, in the eighth embodiment of the first aspect, the high current generating device includes a high current generator, a protective resistor and an adjustable resistor, wherein the high current generator, the protective resistor and the adjustable resistor are connected in series.

[0033] High current generator, used to generate high current;

[0034] Protective resistors are used to protect the circuitry in high-current generating devices.

[0035] Adjustable resistors are used to regulate large currents under different operating conditions.

[0036] In conjunction with the first aspect, in the ninth embodiment of the first aspect, the minimum permissible radius of curvature of the input lead of the energy-transfer insulator is determined by the relationship between the maximum electric field of the energy-transfer insulator and the radius of curvature of the input lead. Attached Figure Description

[0037] To more clearly illustrate the specific embodiments of the present invention or the technical solutions in the prior art, the drawings used in the description of the specific embodiments or the prior art will be briefly introduced below. Obviously, the drawings described below are some embodiments of the present invention. For those skilled in the art, other drawings can be obtained from these drawings without creative effort.

[0038] Figure 1 This is a schematic diagram of a scenario for a power supply system based on magnetic coupling insulators, according to an exemplary embodiment.

[0039] Figure 2 This is a schematic diagram of the magnetic coupler 5 structure in an example;

[0040] Figure 3This is a diagram of the magnetic field distribution in the space surrounding the magnetic coupler 5 in one example. Detailed Implementation

[0041] The technical solution of the present invention will now be clearly and completely described with reference to the accompanying drawings. Obviously, the described embodiments are only some, not all, of the embodiments of the present invention. Based on the embodiments of the present invention, all other embodiments obtained by those skilled in the art without creative effort are within the scope of protection of the present invention.

[0042] Furthermore, the technical features involved in the different embodiments of the present invention described below can be combined with each other as long as they do not conflict with each other.

[0043] To ensure insulation between the AC power supply and the energy harvesting transformer and avoid leakage, this invention proposes a power supply system based on magnetic coupling and an energy transfer insulator.

[0044] Figure 1 This is a schematic diagram of a scenario for a magnetically coupled power supply system for a power insulator, according to an exemplary embodiment. The system provides the power insulator 11 with high current and high voltage, simulating an actual transmission line. The system includes: a high-current generating device 1, an energy harvesting transformer 2, a high-frequency power conversion device 3, an AC power supply 4, and a magnetic coupler 5.

[0045] High current generating device 1 is used to generate high current under simulated power transmission line operating conditions.

[0046] The current transformer 2 (CT) is connected in series with the high current generator 1 to sense the electrical energy in the high current that can be used by the high frequency power conversion device 3.

[0047] The high-frequency power conversion device 3 is connected to the output terminal of the energy harvesting transformer 2 and is used to convert electrical energy into high-frequency AC power.

[0048] Alternating Current (AC) power supply 4 is connected to the high-voltage end of the energy-transferring insulator 11 and is used to provide the energy-transferring insulator 11 with a high-frequency power voltage. Here, high voltage refers to a voltage exceeding 10kV.

[0049] The magnetic coupler 5 is connected to the output terminal of the high-frequency power conversion device 3 and is used to transmit high-frequency AC power to the input terminal of the power insulator 11.

[0050] In an optional embodiment, the power insulator 11 can be a multi-stage magnetic resonant wireless power insulator, and the number of embedded coils in the power insulator 11 is not specifically limited.

[0051] Considering that existing power transfer insulator testing systems use a high-current generator 1 and an AC power supply 4 to simulate the high current and high voltage of actual transmission lines, and that the output terminal of the power extraction transformer 2 and the AC power supply 4 are both directly connected to the high-voltage end of the power transfer insulator 11 via wires, the insulation between the AC power supply 4 and the power extraction transformer 2 is difficult to reliably guarantee. Therefore, the system of this embodiment changes the connection between the output terminal of the power extraction transformer 2 and the high-voltage end of the power transfer insulator 11 from a direct wire connection to a wireless power transmission method based on magnetic coupling, thus eliminating the constraints of wires. The output terminal of the power extraction transformer 2 is connected to the input terminal of the high-frequency power conversion device 3, and the high-frequency AC current is transmitted from low voltage to high voltage through the magnetic coupler 5. There is no wire connection between the transmitting coil and the receiving coil in the magnetic coupler 5, solving the insulation problem between the power extraction transformer 2 and the high-voltage end of the power transfer insulator 11, and reliably ensuring the safe operation of the power transfer insulator testing system.

[0052] In one example, the magnetic coupler 5 includes a receiving coil and a transmitting coil; both the receiving coil and the transmitting coil are DD coils arranged coaxially with the energy-transmitting insulator 11. Figure 2 The diagram shows the structure of the magnetic coupler 5. Both the receiving coil and the transmitting coil in the magnetic coupler 5 are DD coils and are arranged coaxially with the embedded coil of the energy transfer insulator 11. Figure 3 This is a diagram showing the magnetic field distribution around the magnetic coupler 5.

[0053] The magnetic field generated by the coil in the magnetic coupler 5 and the embedded coil in the power insulator 11 will have a coupling effect, which will lead to the inability to accurately measure the transmission power and transmission efficiency of the power insulator 11. In the above embodiment, both the receiving coil and the transmitting coil in the magnetic coupler 5 are DD coils arranged coaxially with the power insulator 11. The mutual magnetic flux between the DD coil and the embedded coil in the power insulator 11 is limited to 0, thereby achieving decoupling between the coil in the magnetic coupler 5 and the embedded coil in the power insulator 11. This avoids the coupling effect between the magnetic field generated by the coil in the magnetic coupler 5 and the embedded coil in the power insulator 11, and thus the transmission power and transmission efficiency of the power insulator 11 can be accurately measured.

[0054] When the power insulator 11 is a multi-stage magnetic resonant wireless power insulator, the transmitting coil and receiving coil in the magnetic coupler 5 are arranged coaxially with the multi-stage magnetic resonant wireless power insulator. This limits the mutual magnetic flux coupling between the DD coil and the embedded coil of the multi-stage magnetic resonant wireless power insulator to 0, thereby achieving decoupling between the coil in the magnetic coupler 5 and the embedded coil of the multi-stage magnetic resonant wireless power insulator, i.e., M pn =0 and M sn =0, where M pn This represents the mutual inductance between the transmitting coil of magnetic coupler 5 and the embedded coil of the nth energy-transferring insulator, M. snThis represents the mutual inductance between the receiving coil of the magnetic coupler 5 and the embedded coil of the nth power transmission insulator, where n represents the nth embedded coil of the multi-stage magnetic resonant wireless power transmission insulator, n = 1, 2, 3, ...

[0055] In an alternative embodiment, the transmitting coil is excluded from a spherical region centered on the centroid of the DD coil in the receiving coil, the radius of which is determined based on the insulation distance between the receiving coil and the transmitting coil.

[0056] In this embodiment of the invention, the radius of the spherical region is determined by the following formula:

[0057] R = d1 * k

[0058] Where R is the radius of the spherical region, d1 is the insulation distance between the receiving coil and the transmitting coil in the magnetic coupler 5, and k is the margin coefficient. For example, the margin coefficient k is taken as 1.66, and the final radius R of the spherical region is determined to be 5cm.

[0059] In an optional embodiment, the insulation distance between the receiving coil and the transmitting coil in the magnetic coupler 5 is determined by the following formula:

[0060] d1≥U1 / (E*K T )*f1(d1)

[0061] Where d1 is the insulation distance between the receiving coil and the transmitting coil in magnetic coupler 5; U1 is the voltage of the equalizing ring; E is the allowable field strength of the air gap; K T It is the atmospheric condition correction factor, K T =k1*k2, where k1 and k2 are the air density correction factor and humidity correction factor, respectively, which can be obtained by referring to relevant standards for high-voltage discharge experiments; f1 is the non-uniformity coefficient of the parallel cylindrical electrode, f1 = 0.9d1 / 2r1ln((d1+2r1) / 2r1), where r1 is the equivalent radius of the parallel cylindrical electrode, obtained by calibration measurement with vernier calipers. The measurement reading after the vernier calipers are caliped at a distance of 3mm-5mm from the tip is r1. For example, U1 is 35kV, and the allowable field strength E of the air gap is 30kV / cm; atmospheric condition correction factor K T Taking 0.987, the insulation distance d1 between the receiving coil and the transmitting coil in magnetic coupler 5 was finally determined to be 3.2cm.

[0062] In an alternative embodiment, considering the coupling coefficient of the magnetic coupler 5 and the space constraints under the test system conditions, both the receiving coil and the transmitting coil are confined within a square region, the side length of which is determined based on the radius of the spherical region.

[0063] In this embodiment of the invention, the side length of the square region is determined by the following formula:

[0064] l <k3*R

[0065] Where l is the side length of the square region; k3 is the scaling factor, determined through finite element simulation; and R is the radius of the spherical region. For example, k3 is set to 5, and the final dimensions of the receiving coil and transmitting coil in the magnetic coupler 5 are determined to be 150×200mm.

[0066] In an alternative embodiment, the number of turns of the receiving coil is determined by the following formula:

[0067] 4*n*d <k4*L

[0068] 2*n*d <k5*W

[0069] Where n is the number of turns in the receiving coil; d is the diameter of the Litz wire in the receiving coil, determined by finite element simulation based on the coil current; k4 and k5 are constants, determined by finite element simulation; L and W are the length and width of the receiving coil, respectively. The number of turns in the transmitting coil is determined in the same way as the number of turns in the receiving coil. For example, the diameter d of the Litz wire used in the coil is determined to be 1.5 mm by finite element simulation based on the coil current; the constants k4 and k5 are determined to be 0.5 and 0.4 respectively by finite element simulation, and finally the number of turns n of both the receiving coil and the transmitting coil in the magnetic coupler 5 is determined to be 15.

[0070] In an optional embodiment, the insulation distance between the transmitting coil of the magnetic coupler 5 and ground, i.e., the distance between the transmitting coil and the low-voltage end of the energy-transmitting insulator 11, is determined by the following formula:

[0071] d2≥U1 / (E*K T )*f2(d2)

[0072] Where d2 is the insulation distance between the transmitting coil and ground; U1 is the voltage of the equalizing ring; E is the allowable field strength of the air gap; K T It is the atmospheric condition correction factor, K T =k1*k2, where k1 and k2 are the air density correction factor and humidity correction factor, respectively, which can be obtained by referring to relevant standards for high-voltage discharge experiments; f2 is the non-uniformity coefficient of the spherical plate electrode, f2 = 0.9*(1+d2 / r2), where r2 is the equivalent radius of the spherical plate electrode, obtained by calibration with vernier calipers. For example, the system voltage U1 is 35kV, the allowable field strength E of the air gap is 30kV / cm; the atmospheric condition correction factor K... T Taking 0.987, the insulation distance d2 between the transmitting coil of magnetic coupler 5 and ground was finally determined to be 3.2cm.

[0073] Table 1 shows the geometric and electrical parameters of magnetic coupler 5 in one example.

[0074] Table 1 Geometric and electrical parameters of magnetic coupler 5

[0075]

[0076] During the wireless transmission of the harvested current to the high-voltage end of the power insulator 11 using the magnetic coupler 5, the current received at the high-voltage end of the power insulator 11 is affected by the electrical parameters of the magnetic coupler 5. The current input to the power insulator 11 is no longer the same as the current when the high-frequency power conversion device 3 is wired to the power insulator 11. To ensure that the output current of the high-frequency power conversion device 3 is the same as the input current of the power insulator 11, and to better simulate the actual conditions of the power insulator 11 under various transmission line operating conditions, the system also includes a transmitter compensation network 6 and a receiver compensation network 7. The input of the transmitter compensation network 6 is connected to the output of the high-frequency power conversion device 3, and the output of the transmitter compensation network 6 is connected to the input of the magnetic coupler 5. The input of the receiver compensation network 7 is connected to the output of the magnetic coupler 5, and the output of the receiver compensation network 7 is connected to the input of the power insulator 11.

[0077] In an optional embodiment, the parameters in the transmitter compensation network 6 and the receiver compensation network 7 are determined by the following formula:

[0078]

[0079] Where ω is the angular frequency, L p To compensate for the self-inductance of the transmitting coil in the transmitting end compensation network 6, L s To compensate for the self-inductance of the receiving coil in the receiving end compensation network 7, M ps C0 is the mutual inductance between the transmitting and receiving coils, C0 is the parallel compensation capacitor of the transmitting compensation network 6, and L0 is the series compensation inductance of the transmitting compensation network 6. p C is the series compensation capacitor for the transmitter compensation network 6. s This is the series compensation capacitor for the receiving end compensation network 7.

[0080] In this embodiment of the invention, the transmitting-end compensation network 6 and the receiving-end compensation network 7 form an LCC-S topology. In this topology, the current transfer ratio at both ends of the compensation network is I. o / I in =M ab / L0, where I in To compensate for the input current of the transmitter compensation network 6, I o To compensate for the output current of the receiving end compensation network 7, let L0 = M. ps To ensure that the current transfer ratio is 1, that is, the current in the current harvesting transformer 2 remains unchanged after passing through the magnetic coupler 5.

[0081] Table 2 shows the compensation parameter values ​​in the transmitter compensation network 6 and receiver compensation network 7 in one example, where the angular frequency ω is π×106rad / s.

[0082] Table 2 Compensation parameter configuration results

[0083]

[0084] exist Figure 1 In the middle, the high current generating device 1 includes a high current generator 8, a protective resistor 9 and an adjustable resistor 10, which are connected in series.

[0085] High current generator 8, used to generate high current;

[0086] Protective resistor 9 is used to protect the circuit in the high current generating device 1;

[0087] An adjustable resistor of 10 is used to adjust the high current under different operating conditions.

[0088] In one example, when the energy-transfer insulator 11 is connected to the system, the minimum permissible radius of curvature of the input lead of the energy-transfer insulator 11 is determined by the relationship between the maximum electric field of the energy-transfer insulator 11 and the radius of curvature of the input lead.

[0089] In this embodiment of the invention, the finite element method can be used to calculate the relationship between the maximum electric field of the energy-transferring insulator 11 and the radius of curvature of the lead wires on the surface of the energy-transferring insulator 11 according to the Poisson equation, thereby obtaining the minimum allowable radius of curvature r of the lead wires of the energy-transferring insulator 11. In this embodiment of the invention, the minimum allowable radius of curvature r is 1 cm.

[0090] In one example, the distance between the horizontal section of the lead wire of the power insulator 11 and the top of the equipotential ring 12 is determined by the following formula:

[0091] d3≥U1 / (E*K T )*f3(d3)

[0092] Where d3 is the distance between the horizontal section of the lead-out wire of the energy-transferring insulator 11 and the top of the equalizing ring 12; U1 is the voltage of the equalizing ring; E is the allowable field strength of the air gap; K T It is the atmospheric condition correction factor, K T =k1*k2, where k1 and k2 are the air density correction factor and humidity correction factor, respectively, which can be obtained by referring to the relevant standards for high-voltage discharge experiments; f3 is the non-uniformity coefficient of the spherical plate electrode, f3 = 0.9*(1+d3 / r3), r3 = min(r a ,r b ),r a Let r be the radius of curvature of the conductor. bLet f3(d3) be the radius of curvature of the energy-transmitting insulator 11 at the nearest point to the conductor. Let f3(d3) and K... T Substituting the expression into the above equation, the inequality regarding d3 can be solved to obtain the minimum distance d3. For example, the equalizing ring voltage U1 is taken as 35kV; the allowable field strength E of the air gap is taken as 30kV / cm; and the atmospheric condition correction factor K... T Taking 0.987, the final distance d3 between the horizontal section of the lead-out wire of the energy-transmitting insulator 11 and the top of the equalizing ring 12 is determined to be 2.8cm.

[0093] In one example, the distance between the vertical segment of the lead-out wire of the energy-transferring insulator 11 and the tip of the equalizing ring 12 is determined by the following formula:

[0094] d4≥U1 / (E*K T )*f4(d4)

[0095] Where d4 is the distance between the vertical section of the lead-out wire of the energy-transferring insulator 11 and the tip of the equalizing ring 12; f4 is the non-uniformity coefficient of the ball plate electrode, f4 = 0.9 * (1 + d4 / r3), and r3 = min(r a ,r b ),r a Let r be the radius of curvature of the conductor. b Let be the radius of curvature of the nearest end of the energy-transfer insulator 11 and the conductor. For example, the equalizing ring voltage U1 is 35kV; the allowable field strength E of the air gap is 30kV / cm; and the atmospheric condition correction factor K... T Taking 0.987, the distance d4 between the horizontal section of the lead wire of the energy-transmitting insulator 11 and the top of the equalizing ring 12 was finally determined to be 3cm.

[0096] In one example, the distance between the lead-out outlet of the power transfer insulator 11 and the high-voltage terminal of the power transfer insulator 11 is determined by the following formula:

[0097] d5=U / (E l *K T )

[0098] Where d5 is the distance between the outlet of the lead wire of the power insulator 11 and the high-voltage end of the power insulator 11; U is the system voltage, E l E represents the allowable surface flashover field strength per unit distance in air. For example, with a system voltage U of 35kV, the allowable surface flashover field strength per unit distance in air is E. l Take 10 kV / cm, atmospheric condition correction factor K T Taking 0.987, the final distance d5 between the outlet of the lead wire of the energy transfer insulator 11 and the high-voltage end of the energy transfer insulator was determined to be 3.6cm.

[0099] It should be noted that, in this document, relational terms such as "first" and "second" are used merely to distinguish one entity or operation from another, and do not necessarily require or imply any such actual relationship or order between these entities or operations. Furthermore, the terms "comprising," "including," or any other variations thereof are intended to cover non-exclusive inclusion, such that a process, method, article, or apparatus that comprises a list of elements includes not only those elements but also other elements not expressly listed, or elements inherent to such a process, method, article, or apparatus. Unless otherwise specified, an element defined by the phrase "comprising one..." does not exclude the presence of other identical elements in the process, method, article, or apparatus that includes the element.

[0100] The above are merely specific embodiments of the present invention, enabling those skilled in the art to understand or implement the invention. Various modifications to these embodiments will be readily apparent to those skilled in the art, and the general principles defined herein may be implemented in other embodiments without departing from the spirit or scope of the invention. Therefore, the present invention is not to be limited to the embodiments shown herein, but is to be accorded the widest scope consistent with the principles and novel features claimed herein.

Claims

1. A power supply system based on magnetic coupling energy transfer insulators, characterized in that, The system includes: a high current generating device, an energy harvesting transformer, a high frequency power conversion device, a magnetic coupler, and an AC power supply; The high current generating device is used to generate a high current simulating the operating conditions of a power transmission line. The energy harvesting transformer is connected in series with the high current generating device to sense the electrical energy in the high current that can be utilized by the high-frequency power conversion device. The high-frequency power conversion device is connected to the output terminal of the energy harvesting transformer and is used to convert the electrical energy into high-frequency AC power. The magnetic coupler is connected to the output terminal of the high-frequency power conversion device and is used to transmit the high-frequency AC power to the input terminal of the power insulator. The AC power supply is connected to the high-voltage end of the energy-transferring insulator and is used to provide the energy-transferring insulator with a high-frequency power voltage. The minimum permissible radius of curvature of the input lead of the energy-transfer insulator is determined by the relationship between the maximum electric field of the energy-transfer insulator and the radius of curvature of the input lead.

2. The system according to claim 1, characterized in that, The magnetic coupler includes a receiving coil and a transmitting coil; both the receiving coil and the transmitting coil are DD coils arranged coaxially with the energy-transmitting insulator.

3. The system according to claim 1, characterized in that, The system also includes: a transmitter compensation network and a receiver compensation network; The input terminal of the transmitter compensation network is connected to the output terminal of the high-frequency power conversion device, and the output terminal of the transmitter compensation network is connected to the input terminal of the magnetic coupler. The input end of the receiving end compensation network is connected to the output end of the magnetic coupler, and the output end of the receiving end compensation network is connected to the input end of the energy-transmitting insulator. The transmitting end compensation network and the receiving end compensation network are used to ensure that the output current of the high-frequency power conversion device is the same as the input current of the energy-transfer insulator.

4. The system according to claim 2, characterized in that, The transmitting coil is excluded from a spherical region centered on the centroid of the DD coil in the receiving coil, the radius of which is determined based on the insulation distance between the receiving coil and the transmitting coil.

5. The system according to claim 4, characterized in that, Both the receiving coil and the transmitting coil are confined within a square region, the side length of which is determined based on the radius of the spherical region.

6. The system according to claim 2, characterized in that, The number of turns of the receiving coil is determined by the following formula: in, n The number of turns of the receiving coil. d The diameter of the Litz wire in the receiving coil is determined by finite element simulation based on the coil current. k 4. k 5 is a constant, determined through finite element simulation. L , W These are the length and width of the receiving coil, respectively.

7. The system according to claim 2, characterized in that, The insulation distance between the transmitting coil and ground is determined by the following formula: in, d 2 represents the insulation distance between the transmitting coil and ground; U 1 represents the voltage of the equalizing ring; E It is the allowable field strength of the air gap; K T It is an atmospheric condition correction factor. , in k 1, k 2 represents the air density correction factor and humidity correction factor, respectively; f 2. Take the non-uniformity coefficient of the ball plate electrode , r 2 represents the equivalent radius of the ball plate electrode.

8. The system according to claim 3, characterized in that, The parameters in the transmitter compensation network and the receiver compensation network are determined by the following formula: in, ω Angular frequency, L p The self-inductance of the transmitting coil in the transmitting end compensation network is... L s The self-inductance of the receiving coil in the compensation network at the receiving end is used to compensate for the loss. M ps For the mutual inductance between the transmitting coil and the receiving coil, C 0 represents the parallel compensation capacitor of the transmitter compensation network. L 0 represents the series compensation inductance of the transmitting end compensation network. C p This refers to the series compensation capacitor in the transmitter compensation network. C s This refers to the series compensation capacitor of the receiving end compensation network.

9. The system according to claim 1, characterized in that, The high current generating device includes a high current generator, a protective resistor, and an adjustable resistor, wherein the high current generator, the protective resistor, and the adjustable resistor are connected in series. The high-current generator is used to generate a high current; The protective resistor is used to protect the circuit in the high current generating device; The adjustable resistor is used to adjust the large current under different operating conditions.

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