A L\S band dual-frequency common aperture filtering antenna array and communication equipment

Abstract

The present invention discloses an L\S band dual-frequency common aperture filter antenna array and communication equipment, belonging to the field of communication antennas. The antenna array includes: a metal floor; a plurality of array-arranged magnetic resonance near-field parasitic filter antennas, including a dielectric substrate four, an L-shaped radiation metal strip arranged on an end face of the dielectric substrate four, a parasitic semi-circular metal strip and a coaxial device A; and a plurality of microstrip filter antennas, including a dielectric substrate three arranged on the metal floor, a dielectric substrate two arranged parallel to the dielectric substrate three, a parasitic metal patch, a coaxial device B and a Y-shaped radiation metal strip. The antenna array of the present invention can effectively reduce the hetero-frequency coupling between L\S band antennas by utilizing the filtering characteristics, and the L\S band antennas are compactly arranged by combining vertical and horizontal placement, and antenna units of different operating frequencies will not generate shielding and coupling, while realizing the compact and miniaturized layout of the common aperture array.

Description

Technical Field

[0001] The present invention relates to the field of communication antennas, and in particular to an L\S band dual-frequency common aperture filtering antenna array and communication equipment. Background Art

[0002] Faced with miniaturized, multi-task, and multi-functional wireless communication scenarios, co-aperture antenna arrays have attracted much attention due to their unique advantages of multi-frequency operation, small size, and high array utilization. Since antennas of different frequency bands and different standards need to be closely installed on the same surface, the electromagnetic interference between frequency bands is serious. Therefore, the use of filtering antennas to achieve the suppression of heterogeneous coupling of co-aperture antennas has become a research hotspot in the field of antennas for space-constrained mobile terminal platforms. In addition, co-aperture antennas also need to select appropriate antenna types, such as: patch antennas and slot antennas, slot antennas and slot antennas, dipole antennas and slot antennas, etc. The above methods are certainly effective in achieving co-aperture antenna performance, but they will increase the complexity and cost of co-aperture antenna design.

[0003] Chinese patent document CN 118073846 A (application number 2024102742550) discloses a highly selective filtering antenna for mobile terminals. The antenna uses lumped inductance and capacitance elements to achieve filtering effects. It has high manufacturing costs and low radiation efficiency and is only suitable for mobile phone antenna applications. Chinese patent number CN 117060053 A (application number 2023109290460) discloses a low-profile filtering dielectric resonator antenna based on metal bridge loading. The antenna requires an irregular resonant cavity and has a complex antenna structure. In addition, the above patents do not consider the application scenarios of co-aperture arrays and are not suitable for multi-frequency application environments.

[0004] Therefore, it is of great value to invent a compact dual-frequency co-aperture filtering antenna array with simple structure and high performance. Summary of the invention

[0005] In view of the shortcomings of the prior art, the present invention proposes an L\S band dual-frequency common aperture filtering antenna array and communication equipment.

[0006] The purpose of the present invention can be achieved through the following technical solutions:

[0007] An L\S band dual-frequency common aperture filtering antenna array, comprising:

[0008] Metal flooring;

[0009] A plurality of array-arranged magnetic resonant near-field parasitic filter antennas, comprising a dielectric substrate 4, an L-shaped radiating metal strip arranged on one end surface of the dielectric substrate 4, and a coaxial device A, and a parasitic semi-annular metal strip arranged on the other end surface of the dielectric substrate 4;

[0010] And, a plurality of microstrip filter antennas arranged between adjacent magnetic resonance near-field parasitic filter antennas, including a dielectric substrate three arranged on a metal floor, a dielectric substrate two arranged parallel to the dielectric substrate three, a parasitic metal patch arranged on an end surface of the dielectric substrate two away from the dielectric substrate three, a coaxial device B, and a Y-shaped radiation metal strip arranged on an end surface of the dielectric substrate three close to the dielectric substrate two;

[0011] The inner conductors of the coaxial device A and the coaxial device B are connected to the L-shaped radiating metal strip and the Y-shaped radiating metal strip respectively, and the outer conductors are connected to the metal floor;

[0012] The plane where the L-shaped radiating metal strip is located is perpendicular to the plane where the Y-shaped radiating metal strip is located;

[0013] The L-shaped radiating metal strip and the Y-shaped radiating metal strip can respectively suppress the frequencies of the magnetic resonance near-field parasitic filter antenna and the microstrip filter antenna, thereby achieving dual-band out-of-band coupling suppression.

[0014] Optionally, the long side of the L-shaped radiation metal strip is used to control the out-of-band radiation suppression performance, and its length is related to the working frequency band of another frequency band antenna, which is approximately a quarter of the wavelength.

[0015] Optionally, the side branches of the Y-shaped radiation metal strip are used to control the out-of-band radiation suppression performance, and the length of the side branches is related to the working frequency band of another frequency band antenna, which is about a quarter of the wavelength.

[0016] Optionally, the magnetic resonance near-field parasitic filter antenna units are placed vertically on the metal floor at a certain interval, and the interval is less than half of its wavelength; the microstrip filter antenna units are placed horizontally on the metal floor at a certain interval, and the horizontal and longitudinal intervals are less than half of its wavelength.

[0017] Optionally, the metal floor, the L-shaped radiating metal strip, the parasitic semi-circular metal strip, the Y-shaped radiating metal strip, and the parasitic metal patch are made of copper.

[0018] Optionally, the dielectric substrate is made of Rogers 5880 or other high-frequency circuit dielectric board material.

[0019] Beneficial effects of the present invention:

[0020] 1. The present invention utilizes L-shaped radiating metal strip and Y-shaped radiating metal strip feeding methods to introduce corresponding radiation zero points in the working frequency bands of L\S band antennas respectively, without introducing additional coupling suppression structure, and can achieve high isolation (>30dB) and independent operation of high and low frequency antennas.

[0021] 2. The magnetic resonance near-field parasitic filter antenna unit of the present invention is small in size and low in profile. It is placed vertically and does not occupy horizontal space. The microstrip filter antenna unit is placed in the horizontal space between the antenna units. The high and low frequency antenna units efficiently utilize the cross-sectional size. There is no shielding or coupling between the units. The low frequency unit has little shielding effect on the high frequency antenna radiation pattern. The array as a whole is easy to conform and low RCS design. The L-band patch array spacing is less than 0.41L-band wavelength, and the S-band patch array spacing is less than 0.48S-band wavelength. The overall size is greatly reduced, meeting the conditions for large-angle scanning grating lobes of the array antenna, which is convenient for the design and application of subsequent phased array systems. BRIEF DESCRIPTION OF THE DRAWINGS

[0022] The present invention will be further described below in conjunction with the accompanying drawings.

[0023] Figure 1 It is an overall schematic diagram of the dual-frequency common-aperture filtering antenna of the present invention;

[0024] Figure 2 It is a structural diagram of the magnetic resonance near-field parasitic filtering antenna unit of the present invention;

[0025] Figure 3 It is a structural diagram of the microstrip filtering antenna unit of the present invention;

[0026] Figure 4 A top view of the dual-frequency common-aperture filtering antenna of the present invention;

[0027] Figure 5 The impedance and gain curves of the microstrip filtering antenna unit of the present invention;

[0028] Figure 6 The impedance and gain curves of the magnetic resonance near-field parasitic filter antenna unit of the present invention;

[0029] Figure 7 is the impedance curve of the common aperture array of the present invention;

[0030] Figure 8 is the isolation coefficient between the magnetic resonance near-field parasitic filter antenna and the microstrip filter antenna in the middle of the common aperture array of the present invention;

[0031] Fig. 9 It is the isolation coefficient between the magnetic resonance near-field parasitic filter antenna and the microstrip filter antenna at both ends of the common aperture array of the present invention.

[0032] In the figure: 1—metal floor, 2—dielectric substrate 2, 3—dielectric substrate 3, 4—dielectric substrate 4, 5—parasitic semi-annular metal strip, 6—L-shaped radiating metal strip, 7—parasitic metal patch, 8—Y-shaped radiating metal strip, 901—coaxial device A, 902—coaxial device B. DETAILED DESCRIPTION

[0033] The following will be combined with the drawings in the embodiments of the present invention to clearly and completely describe the technical solutions in the embodiments of the present invention. Obviously, the described embodiments are only part of the embodiments of the present invention, not all of the embodiments. Based on the embodiments of the present invention, all other embodiments obtained by ordinary technicians in this field without creative work are within the scope of protection of the present invention.

[0034] like Figure 1 As shown, in some embodiments of the present invention, a low-profile, compact and miniaturized L\S band dual-frequency common-aperture filtering antenna array is disclosed, and the antenna array includes a metal floor 1, a magnetic resonant near-field parasitic filtering antenna and a microstrip filtering antenna.

[0035] The magnetic resonance near-field parasitic filter antenna is arranged in a 1×3 array on a metal substrate 1, and includes a dielectric substrate 4, an L-shaped radiating metal strip 6 arranged on one end surface of the dielectric substrate 4, a coaxial device A901, and a parasitic semi-annular metal strip 5 arranged on the other end surface of the dielectric substrate 4;

[0036] The microstrip filter antenna is arranged between adjacent magnetic resonance near-field parasitic filter antennas, and is arranged in a 2×2 array on the metal substrate 1, including a dielectric substrate 3 3 arranged on the metal floor 1, a dielectric substrate 2 2 arranged parallel to the dielectric substrate 3 3, a parasitic metal patch 7 arranged on the end surface of the dielectric substrate 2 2 away from the dielectric substrate 3 3, a coaxial device B902, and a Y-shaped radiation metal strip 8 arranged on the end surface of the dielectric substrate 3 3 close to the dielectric substrate 2 2. The parasitic metal patch 7 is etched on the upper surface of the dielectric substrate 2 2; the Y-shaped radiation metal strip 8 is etched on the upper surface of the dielectric substrate 3 3.

[0037] The inner conductors of the coaxial device A901 and the coaxial device B902 are respectively connected to the L-shaped radiating metal strip 6 and the Y-shaped radiating metal strip 8, and the outer conductors are connected to the metal floor 1. In some embodiments of the present invention, the coaxial device A901 and the coaxial device B902 may adopt the same specifications.

[0038] The plane where the L-shaped radiation metal strip 6 is located is perpendicular to the plane where the Y-shaped radiation metal strip 8 is located.

[0039] As an embodiment of the present invention, Figure 2 As shown, the lengths of the dielectric substrate 2 and the dielectric substrate 3 are =50mm, width is =50mm; the length of the parasitic metal patch 7 is =29.8mm, width is =29.8mm; the main branch length of the Y-shaped radiation metal strip 8 is =26mm, width is =2mm, the length of the side branches is =15mm, the gap between the side branches and the main branches is =4.5mm. The side branch works as a shorter quarter-wavelength open-ended transmission line, and its operating frequency is: in c is the speed of light, L is the length of the side branch, ε re is the equivalent dielectric constant. The calculated radiation zero point is approximately 1.78 GHz.

[0040] The parasitic semi-annular metal strip 5 and the L-shaped radiation metal strip 6 are respectively etched on the upper and lower surfaces of the dielectric substrate 4; the extra branches of the Y-shaped radiation metal strip 8 and the lateral branches of the L-shaped radiation metal strip 6 are used to introduce corresponding radiation zero points and filtering effects to achieve hetero-frequency coupling suppression.

[0041] As an embodiment of the present invention, Figure 3 As shown, the length of the dielectric substrate 4 is =10mm, width is =45mm~50mm; the width of the parasitic semi-annular metal strip 5 is =45mm~50mm, strip width is =2.3mm, inner height is = 7.2mm; the transverse branch length of the L-shaped radiation metal strip 6 is =32mm, width is =1mm, vertical branch length is =5mm, width is =1mm. The lateral branches work as a quarter-wavelength open-ended transmission line, and its operating frequency is: in c is the speed of light, L is the length of the transverse branch, ε re is the equivalent dielectric constant. The calculated radiation zero point is about 2.3 GHz.

[0042] The magnetic resonance near-field parasitic filter antenna array is placed vertically on the metal floor 1, and the microstrip filter antenna array is placed horizontally on the metal floor 1, and the two are arranged alternately.

[0043] As an embodiment of the present invention, Figure 4 As shown, the lateral distance and radial distance of each dielectric substrate 2 are respectively =64.5mm, =64.5mm, which corresponds to 0.48 wavelength of the working frequency 2.3GHz. The lateral distances of the dielectric substrates 4 are =70mm. This distance corresponds to 0.41 wavelengths of the operating frequency of 1.78GHz.

[0044] In some other embodiments of the present invention, HFSS18.0 is used to simulate and analyze the low-profile, compact and miniaturized L\S band dual-frequency common aperture filter antenna array in the above embodiment. After simulation and analysis, the parameters and dimensions of some antennas are shown in Table 1 below:

[0045]

[0046] According to the above parameters, HFSS is used to analyze the S11 parameters and isolation parameters of the low-profile, compact and miniaturized L\S band dual-frequency common aperture filter antenna array in the above embodiment, and the analysis results are as follows:

[0047] like Figure 5 As shown, the -10dB impedance curve bandwidth of the high-frequency array element of the common-aperture antenna of the embodiment of the present invention is 0.2GHz, from 2.22GHz to 2.42GHz, and the relative bandwidth is 8.6%; its gain response has a suppression effect of about 12.5dB near 1.78GHz.

[0048] like Figure 6 As shown, the -10dB impedance curve bandwidth of the low-frequency array element of the common-aperture antenna of the embodiment of the present invention is 0.02GHz, from 1.76GHz to 1.79GHz, and the relative bandwidth is 1.6%; its gain response has a suppression effect of about 30dB near 2.3GHz.

[0049] like Figure 7 As shown, after the common-aperture antenna array of the embodiment of the present invention is formed, the impedance matching ranges of the high-frequency and low-frequency antennas are 1.76 GHz to 1.79 GHz and 2.22 GHz to 2.42 GHz, respectively, and the relative bandwidths are 1.6% and 8.6%, respectively.

[0050] like Figure 8 As shown, the isolation coefficients of the co-aperture array intermediate magnetic resonance near-field parasitic filter antenna and the microstrip filter antenna in the embodiment of the present invention have suppression effects of 32 dB and 35 dB at 1.9 GHz and 2.3 GHz, respectively.

[0051] like Fig. 9 As shown, the isolation coefficients of the magnetic resonant near-field parasitic filter antennas at both ends of the co-aperture array and the microstrip filter antennas of the embodiment of the present invention have suppression effects of 37 dB and 37 dB at 1.9 GHz and 2.3 GHz, respectively.

[0052] In the description of this specification, the description with reference to the terms "one embodiment", "example", "specific example", etc. means that the specific features, structures, materials or characteristics described in conjunction with the embodiment or example are included in at least one embodiment or example of the present invention. In this specification, the schematic representation of the above terms does not necessarily refer to the same embodiment or example. Moreover, the specific features, structures, materials or characteristics described can be combined in any one or more embodiments or examples in a suitable manner.

[0053] The above shows and describes the basic principles, main features and advantages of the present invention. Those skilled in the art should understand that the present invention is not limited to the above embodiments, and the above embodiments and descriptions are only for explaining the principles of the present invention. Without departing from the spirit and scope of the present invention, the present invention may have various changes and improvements, and these changes and improvements all fall within the scope of the present invention to be protected.

Claims

1. An L\S band dual-frequency common aperture filtering antenna array, characterized in that: include: Metal flooring; A plurality of array-arranged magnetic resonance near-field parasitic filter antennas include a dielectric substrate 4, an L-shaped radiating metal strip and a coaxial device A arranged on one end face of the dielectric substrate 4, and a parasitic semi-circular metal strip arranged on the other end face of the dielectric substrate 4; and a plurality of microstrip filter antennas arranged between adjacent magnetic resonance near-field parasitic filter antennas, including a dielectric substrate 3 arranged on a metal floor, a dielectric substrate 2 arranged parallel to the dielectric substrate 3, a parasitic metal patch arranged on the end face of the dielectric substrate 2 away from the dielectric substrate 3, a coaxial device B, and a Y-shaped radiating metal strip arranged on the end face of the dielectric substrate 3 close to the dielectric substrate 2; wherein the inner conductors of the coaxial device A and the coaxial device B are respectively connected to the L-shaped radiating metal strip and the Y-shaped radiating metal strip, and the outer conductors are both connected to the metal floor; the plane where the L-shaped radiating metal strip is located is perpendicular to the plane where the Y-shaped radiating metal strip is located; the L-shaped radiating metal strip and the Y-shaped radiating metal strip can respectively suppress the frequencies of the magnetic resonance near-field parasitic filter antenna and the microstrip filter antenna, thereby realizing dual-band out-of-band coupling suppression.

2. The L\S band dual-frequency common aperture filtering antenna array according to claim 1, characterized in that: The length of the long side of the L-shaped radiating metal strip is one quarter of the wavelength of the microstrip filtering antenna.

3. The L\S band dual-frequency common aperture filtering antenna array according to claim 1, characterized in that: The length of the side branches of the Y-shaped radiating metal strip is one quarter of the wavelength of the magnetic resonance near-field parasitic filter antenna.

4. The L\S band dual-frequency common aperture filtering antenna array according to claim 1, characterized in that: The L-shaped radiating metal strip, the Y-shaped radiating metal strip, the parasitic semi-annular metal strip and the parasitic metal patch are processed by etching.

5. The L\S band dual-frequency common aperture filtering antenna array according to claim 1, characterized in that: The metal floor, the L-shaped radiating metal strip, the parasitic semi-circular metal strip, the Y-shaped radiating metal strip and the parasitic metal patch are made of copper.

6. The L\S band dual-frequency common aperture filtering antenna array according to claim 1, characterized in that: The material of the dielectric substrate 2, the dielectric substrate 3 and the dielectric substrate 4 is Rogers 5880.

7. The L\S band dual-frequency common aperture filtering antenna array according to claim 1, characterized in that: At least two of the microstrip filter antennas are arranged between at least two adjacent magnetic resonance near-field parasitic filter antennas.

8. The L\S band dual-frequency common aperture filtering antenna array according to claim 1, characterized in that: The spacing between adjacent magnetic resonance near-field parasitic filter antennas is less than half the wavelength of the magnetic resonance near-field parasitic filter antennas.

9. The L\S band dual-frequency common aperture filtering antenna array according to claim 1, characterized in that: The distance between adjacent microstrip filter antennas is less than half the wavelength of the microstrip filter antennas.

10. A communication device, characterized in that: It comprises the L\S band dual-frequency common aperture filtering antenna array as described in any one of claims 1 to 9.

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