Dual-frequency artificial magnetic conductor

Abstract

The utility model discloses a kind of dual-frequency artificial magnetic conductor, the dual-frequency artificial magnetic conductor includes substrate, ground plane and radiation structure;Radiation structure includes multiple array arrangement sub-radiation unit;Sub-radiation unit includes multiple T-shaped openwork structure, arc T-shaped structure and center structure;Arc T-shaped structure is located in the center structure far from the center of sub-radiation unit side;Center structure includes the arc T-shaped subpart and circular subpart of connection arrangement;Arc T-shaped subpart includes the first edge of the center of sub-radiation unit side far from, arc T-shaped structure includes the second edge of the center of sub-radiation unit side close to;First edge is located in the second edge far from the center of sub-radiation unit side.The dual-frequency artificial magnetic conductor of the utility model has certain different polarization electromagnetic wave vertical incidence insensitivity and incidence electromagnetic wave different incidence angle insensitivity, can reduce the radiation of antenna to human body, improve the security of wearable device.

Description

Technical Field

[0001] This utility model relates to the field of wireless communication technology, and in particular to a dual-frequency artificial magnetic conductor. Background Technology

[0002] With the rapid development of wearable wireless devices, they are becoming increasingly important in areas such as wireless personal area networks (WLANs), wireless body area networks (WBAs), and fifth-generation (5G) technology. Along with the advancements in these wireless communication technologies, related applications are constantly emerging, such as medical monitoring, sports rehabilitation training, and health detection. For example, in medical monitoring applications, patients can monitor their health using wearable devices, sending personal health monitoring data to a smart platform built on 5G technology via electromagnetic wave frequencies. This data is then analyzed and transmitted back via electromagnetic wave frequencies for the patient to receive, thus achieving the function of wireless medical health monitoring. In these wearable applications, the antennas that enable signal transmission and reception and information exchange are typically worn close to the body, such as on the shoulders or arms. Currently, the electromagnetic radiation generated when using wearable devices poses a potential threat to human health; therefore, to ensure human safety, it is necessary to reduce the radiation emitted by the antennas in wearable devices.

[0003] Currently, wearable devices can achieve in-phase reflection of incident waves by loading artificial magnetic conductors, which has yielded significant results in improving antenna gain and reducing back radiation. However, existing artificial magnetic conductor structures still have many shortcomings when applied to dual-band wearable antennas, such as poor structural flexibility, sensitivity to electromagnetic waves with different polarizations or different incident angles, and difficulty in adapting to different wearing parts. These factors lead to unstable performance and potential safety issues in wearable devices. Utility Model Content

[0004] The purpose of this invention is to solve the technical problems described in the background section. To this end, a dual-frequency artificial magnetic conductor is provided, which has polarization insensitivity, incident wave angle insensitivity, and good reflection effect, so as to reduce the radiation of the antenna to the human body and protect human safety.

[0005] This utility model provides a dual-frequency artificial magnetic conductor, comprising:

[0006] Base;

[0007] The ground plane located on one side of the substrate;

[0008] A radiating structure located on the other side of the substrate; the radiating structure includes m*n arrayed radiating units; each radiating unit includes a central region and an edge region surrounding the central region; the radiating unit also includes multiple T-shaped hollow structures, multiple arc-shaped T-shaped structures, and a central structure;

[0009] Multiple T-shaped hollow structures are located in the edge region, and the arc-shaped T-shaped structure and the central structure are both located in the central region. The arc-shaped T-shaped structure is located on the side of the central structure away from the center of the radiating unit, and the center of the central structure coincides with the center of the radiating unit. The central structure includes an arc-shaped T-shaped portion and a circular portion connected together. The arc-shaped T-shaped portion is located on the side of the circular portion away from the center of the radiating unit, and the arc-shaped T-shaped portion and the arc-shaped T-shaped structure are arranged alternately.

[0010] The arc-shaped T-shaped portion includes a first edge on the side away from the center of the radiating unit, and the first edge protrudes toward the side away from the center of the radiating unit; the arc-shaped T-shaped structure includes a second edge on the side close to the center of the radiating unit, and the second edge is recessed toward the side close to the center of the radiating unit; the first edge is located on the side of the second edge away from the center of the radiating unit.

[0011] Where m≥2, n≥2, and m and n are both integers.

[0012] Optionally, the radiating element includes two first boundaries and two second boundaries; the two first boundaries are arranged along a first direction and both extend along a second direction, and the two second boundaries are arranged along the second direction and both extend along the first direction; the first direction and the second direction intersect.

[0013] Along the first direction, the minimum dimension ω1 between the two first boundaries satisfies: 23.2mm ≤ ω1 ≤ 23.5mm;

[0014] Within the same radiating unit, the ground plane includes two third boundaries and two fourth boundaries; the two third boundaries are arranged along a first direction and both extend along a second direction, and the two fourth boundaries are arranged along the second direction and both extend along the first direction; along the first direction, the minimum dimension W between the two third boundaries satisfies: 23.9mm≤W≤24.3mm.

[0015] Optionally, the T-shaped hollow structure includes a first hollow portion and a second hollow portion connected together; the extending direction of the first hollow portion intersects with the extending direction of the second hollow portion;

[0016] The minimum dimension ω2 between the first hollowed-out portion and the first boundary satisfies: 2.3mm≤ω2≤2.8mm;

[0017] The minimum dimension ω3 between the second hollowed-out portion and the first boundary satisfies: 11.1mm ≤ ω3 ≤ 11.3mm;

[0018] The second hollowed-out portion includes a first hollowed-out edge and a second hollowed-out edge, and the minimum dimension ω4 between the first hollowed-out edge and the second hollowed-out edge satisfies: 0.2mm≤ω4≤3.5mm.

[0019] Optionally, the arc-shaped T-structure includes an arc-shaped portion and a connecting portion connected together;

[0020] The arc-shaped portion includes a first end and a second end, and the angle θ1 formed between the line connecting the first end and the center of the radiating unit and the line connecting the second end and the center of the radiating unit satisfies: 34°≤θ1≤49°;

[0021] The length L of the connecting portion satisfies 2.09mm≤L≤2.49mm; the width ω5 of the connecting portion satisfies 0.1mm≤ω5≤2.5mm.

[0022] Optionally, the dimension r1 between the first edge and the center of the radiating element satisfies: 7mm ≤ r1 ≤ 7.3mm;

[0023] The circular portion includes a third edge, and the dimension r2 between the third edge and the center of the radiating unit satisfies: 4.72mm≤r2≤5.02mm.

[0024] Optionally, the connecting portion includes a third end on the side away from the center of the radiating unit;

[0025] The dimension r3 between the third end and the center of the radiating unit satisfies: 8.1mm≤r3≤8.5mm.

[0026] Optionally, the central axis of the arc-shaped T-shaped structure is collinear with the central axis of the T-shaped hollow structure.

[0027] Optionally, the included angle θ2 between the central axis of the arc-shaped T-shaped structure and the central axis of the T-shaped hollow structure satisfies: 0°<θ2≤30°.

[0028] Optionally, the substrate may include a flexible substrate.

[0029] Optionally, both the radiating structure and the ground plane include a flexible conductive layer.

[0030] The technical solution provided by this utility model embodiment involves a dual-frequency artificial magnetic conductor formed by stacking a ground plane, a substrate, and a radiating structure. The radiating structure includes m*n arrayed radiating units, each unit consisting of multiple T-shaped perforated structures, an arc-shaped T-shaped structure, and a central structure. The multiple T-shaped perforated structures are located in the edge region, while the arc-shaped T-shaped structures and the central structure are located in the central region. The arc-shaped T-shaped structures are located on the side of the central structure furthest from the center of the radiating units, and the center of the central structure coincides with the center of the radiating units. The central structure includes a connected arc-shaped T-shaped portion and a circular portion. The arc-shaped T-shaped portion is located on the side of the circular portion furthest from the center of the radiating units, and the arc-shaped T-shaped portions and arc-shaped T-shaped structures are arranged alternately. This results in a compact structure for the radiating unit. By adjusting the size and relative position of the gaps between the T-shaped perforated structures, the arc-shaped T-shaped structures, and the central structure, the reflection phase characteristics of the dual-frequency artificial magnetic conductor can be adjusted. The arc-shaped T-shaped section includes a first edge on the side furthest from the center of the radiating element, and a second edge on the side closer to the center of the radiating element. The first edge is located on the side of the second edge furthest from the center of the radiating element. Where m ≥ 2, n ≥ 2, and both m and n are integers, meaning the radiating structure consists of at least 2*2 arrayed radiating elements. This dual-frequency artificial magnetic conductor has a compact structure and small electrical dimensions, making it compatible with both single-band and dual-band antennas. Furthermore, the dual-frequency artificial magnetic conductor exhibits good reflection properties, reducing antenna radiation to the human body and thus protecting human safety. Attached Figure Description

[0031] Figure 1 A top view schematic diagram of a dual-frequency artificial magnetic conductor provided for an embodiment of this utility model;

[0032] Figure 2 A top view of the ground within a single radiating unit provided in an embodiment of this utility model;

[0033] Figure 3 A schematic diagram of the structure of a first single radiating unit provided in an embodiment of this utility model;

[0034] Figure 4 Phase reflection characteristics and total internal reflection characteristics curves of the dual-frequency artificial magnetic conductor provided for embodiments of this utility model;

[0035] Figure 5 A schematic diagram showing the effect of perpendicular incidence of electromagnetic waves with different polarizations on the reflection phase characteristics of a dual-frequency artificial magnetic conductor, provided for an embodiment of this utility model.

[0036] Figure 6 A schematic diagram showing the effect of different incident angles of the incident electromagnetic wave on the reflection phase characteristics of the dual-frequency artificial magnetic conductor, provided for an embodiment of this utility model.

[0037] Figure 7 A comparison diagram of the reflection coefficients of a dual-band antenna with and without an artificial magnetic conductor, provided for embodiments of this utility model;

[0038] Figure 8 A 2D far-field radiation pattern at 2.45 GHz for an antenna with a dual-frequency artificial magnetic conductor provided in an embodiment of this utility model;

[0039] Figure 9 A 3D far-field radiation pattern at 2.45 GHz for an antenna with a dual-frequency artificial magnetic conductor provided in an embodiment of this utility model;

[0040] Figure 10 A 2D far-field radiation pattern at 5.8 GHz for an antenna with a dual-frequency artificial magnetic conductor provided in an embodiment of this utility model;

[0041] Figure 11 A 3D far-field radiation pattern at 5.8 GHz for an antenna with a dual-frequency artificial magnetic conductor provided in an embodiment of this utility model;

[0042] Figure 12 A schematic diagram illustrating the simulated specific absorption rate at 2.45 GHz for a dual-band antenna with a dual-frequency artificial magnetic conductor loaded on 1g of human tissue, provided as an embodiment of this utility model.

[0043] Figure 13 A schematic diagram illustrating the simulated specific absorption rate at 2.45 GHz for a dual-band antenna loaded with a dual-frequency artificial magnetic conductor in 10g of human tissue, provided as an embodiment of this utility model.

[0044] Figure 14 A schematic diagram illustrating the simulated specific absorption rate at 5.8 GHz for a dual-band antenna with a dual-frequency artificial magnetic conductor loaded on 1g of human tissue, provided for an embodiment of this utility model.

[0045] Figure 15 A schematic diagram illustrating the simulated specific absorption rate at 5.8 GHz for a dual-band antenna loaded with a dual-frequency artificial magnetic conductor in 10g of human tissue, provided as an embodiment of this utility model.

[0046] Figure 16 for Figure 3 Enlarged diagram of the corresponding AA region;

[0047] Figure 17 A schematic diagram of an equivalent resonant circuit for a radiating unit provided for an embodiment of this utility model;

[0048] Figure 18 for Figure 17 Schematic diagrams of the reflection phase curves corresponding to the radiating unit and the equivalent resonant circuit, respectively;

[0049] Figure 19 This is a schematic diagram of the structure of a second single radiating unit provided in an embodiment of the present invention;

[0050] Figure 20 for Figure 19 A schematic diagram showing the effect of perpendicularly incident polarized electromagnetic waves on the reflection phase characteristics of a dual-frequency artificial magnetic conductor.

[0051] Figure 21 A schematic diagram of the actual bending test results of a dual-band antenna with a loaded dual-frequency artificial magnetic conductor provided in an embodiment of this utility model. Detailed Implementation

[0052] To enable those skilled in the art to better understand the present invention, the technical solutions of the present invention will be clearly and completely described below with reference to the accompanying drawings of the embodiments. Obviously, the described embodiments are only some embodiments of the present invention, and not all embodiments. Based on the embodiments of the present invention, all other embodiments obtained by those skilled in the art without creative effort should fall within the protection scope of the present invention.

[0053] It should be noted that the terms "first," "second," etc., used in the specification, claims, and accompanying drawings of this utility model are used to distinguish similar objects and are not necessarily used to describe a specific order or sequence. It should be understood that such data can be interchanged where appropriate so that the embodiments of this utility model described herein can be implemented in sequences other than those illustrated or described herein.

[0054] Figure 1 This is a top view schematic diagram of a dual-frequency artificial magnetic conductor provided in an embodiment of the present invention. Figure 2 This is a top view of the ground within a single radiating element, as provided in an embodiment of the present invention. Figure 3 A schematic diagram of the structure of a first single radiating unit provided in the embodiment of this utility model is shown below. Figures 1-3As shown, the dual-frequency artificial magnetic conductor includes: a substrate 10; a ground plane 20 located on one side of the substrate 10; and a radiating structure 30 located on the other side of the substrate 10. The radiating structure 30 includes m*n arrayed radiating units 30-1. Each radiating unit 30-1 includes a central region aa and an edge region bb surrounding the central region aa. The radiating unit 30-1 also includes multiple T-shaped hollow structures 301, multiple arc-shaped T-shaped structures 302, and a central structure 303. The multiple T-shaped hollow structures 301 are located in the edge region bb, and the arc-shaped T-shaped structures 302 and the central structure 303 are both located in the central region aa. The arc-shaped T-shaped structure 302 is located on the side of the central structure 303 away from the center O of the radiating unit, and the center of the central structure 303 coincides with the center O of the radiating unit. The central structure 303 includes a plurality of arc-shaped T-shaped portions 3031 and a circular portion 3032 connected together. The arc-shaped T-shaped portions 3031 are located on the side of the circular portion 3032 away from the center O of the radiating unit, and the arc-shaped T-shaped portions 3031 and the arc-shaped T-shaped structure 302 are arranged alternately. The arc-shaped T-shaped portions 3031 include a first edge 31 on the side away from the center O of the radiating unit, and the first edge 31 protrudes toward the side away from the center O of the radiating unit. The arc-shaped T-shaped structure 302 includes a second edge 32 on the side close to the center O of the radiating unit, and the second edge 32 is recessed toward the side close to the center O of the radiating unit. The first edge 31 is located on the side of the second edge 32 away from the center O of the radiating unit. Wherein, m≥2, n≥2, and m and n are both integers.

[0055] Specifically, the ground plane 20 and the radiating structure 30 are located on opposite sides of the substrate 10, meaning the substrate 10 can serve as the bearing surface for both the ground plane 20 and the radiating structure 30, forming a sandwich structure of "radiating structure 30 - substrate 10 - ground plane 20". In other words, the dual-frequency artificial magnetic conductor includes a ground plane 20, a substrate 10, and a radiating structure 30 stacked together.

[0056] Specifically, the radiating structure 30 includes m*n arrayed radiating elements 30-1; where m ≥ 2, n ≥ 2, and both m and n are integers, meaning the radiating structure 30 consists of at least 2×2 arrayed radiating elements 30-1. For example, Figure 1 The radiation structure 30 shown is composed of 4×4 arrayed radiation units 30-1. It is understood that the number of radiation units 30-1 can also be 3×3, 3×2, 3×4 or 5×5, etc. Those skilled in the art can set the number of radiation units 30-1 in the radiation structure 30 according to actual needs.

[0057] Specifically, the radiating unit 30-1 includes a central region aa and an edge region bb surrounding the central region aa. The radiating unit 30-1 also includes multiple T-shaped hollow structures 301, arc-shaped T-shaped structures 302, and a central structure 303; the multiple T-shaped hollow structures 301 are located in the edge region bb, and the arc-shaped T-shaped structures 302 and the central structure 303 are both located in the central region aa. Multiple T-shaped hollow structures 301 can be formed by etching the edge region bb of the entire conductive material layer, with each T-shaped hollow structure 301 located in the edge region bb of each radiating unit 30-1. Arc-shaped T-shaped structures 302 and the central structure 303 can be formed by etching the central region aa of the entire conductive material layer. The central structure 303 includes an arc-shaped T-shaped portion 3031 and a circular portion 3032 connected together. The arc-shaped T-shaped portion 3031 is located on the side of the circular portion 3032 away from the center O of the radiating unit. The shape of the central structure 303 is similar to a gear structure, with the arc-shaped T-shaped portion 3031 surrounding the same circular portion 3032. The arc-shaped T-shaped portions 3031 and the arc-shaped T-shaped structures 302 are arranged alternately, meaning that the arc-shaped T-shaped portions 3031 are located between two adjacent arc-shaped T-shaped structures 302, or vice versa. It should be noted that there is a gap between the arc-shaped T-shaped structures 302 and the arc-shaped T-shaped portions 3031.

[0058] Specifically, the arc-shaped T-shaped portion 3031 includes a first edge 31 on the side away from the center O of the radiating unit, and the first edge 31 protrudes outward from the side away from the center O of the radiating unit. Multiple arc-shaped T-shaped portions 3031 are arranged around the center O of the radiating unit, and the lines connecting the multiple first edges 31 lie on the same circumference, with the center of this circumference coinciding with the center O of the radiating unit. The arc-shaped T-shaped structure 302 includes a second edge 32 on the side closer to the center O of the radiating unit, and the second edge 32 is recessed towards the side closer to the center O of the radiating unit. Multiple arc-shaped T-shaped structures 302 are arranged around the center O of the radiating unit, and the lines connecting the multiple second edges 32 lie on the same circumference, with the center of this circumference coinciding with the center O of the radiating unit. Furthermore, the first edge 31 is located on the side of the second edge 32 away from the center O of the radiating unit, meaning that the first edge 31 is farther from the center O of the radiating unit than the second edge 32. It should be noted that there is a gap between the first edge 31 and the edge of the arc-shaped T-shaped structure 302 on the side away from the center O of the radiating unit.

[0059] Specifically, by setting up a T-shaped hollow structure 301, an arc-shaped T-shaped structure 302, and a central structure 303, the structure of the radiation unit 30-1 is compact. By adjusting the size of the gaps and the relative positions of the T-shaped hollow structure 301, the arc-shaped T-shaped structure 302, and the central structure 303, the reflection phase characteristics of the dual-frequency artificial magnetic conductor unit can be adjusted. Figure 4 The phase reflection characteristics and total internal reflection characteristics curves of the dual-frequency artificial magnetic conductor provided for embodiments of this utility model are as follows: Figure 4 As shown, the red curve represents the total internal reflection characteristic curve, and the black curve represents the phase reflection characteristic curve. Thus, the zero-phase reflection point can be determined through the black curve, and the zero-phase reflection point represents the operating frequency of this dual-frequency artificial magnetic conductor. Figure 4 It can be seen that the frequencies corresponding to the zero-phase points are 2.45GHz and 5.8GHz. The red curve represents the electromagnetic wave reflection coefficient. As shown by the red curve, the emission coefficient corresponding to the lowest point of the red curve is approximately -1.5dB, meaning that nearly 85% or more of the electromagnetic waves are reflected. This indicates that the dual-frequency artificial magnetic conductor has good reflection performance. Specifically, by loading a dual-frequency artificial magnetic conductor onto the antenna, in-phase reflection of the incident wave can be achieved, resulting in significant improvements in antenna gain and reduction of back radiation. The 2.45GHz band can be used as the operating frequency for high-speed wireless personal area networks, supporting communication technologies such as Bluetooth and Zigbee. Furthermore, to avoid potential congestion issues in the 2.45GHz band and provide more options to ensure data transmission stability, the 5.8GHz band is also introduced, allowing the dual-frequency artificial magnetic conductor unit to achieve in-phase reflection of the incident wave simultaneously in two frequency bands. The operating frequency of the dual-frequency artificial magnetic conductor provided in this embodiment meets communication protocol standards and avoids electromagnetic compatibility issues with other components.

[0060] Considering the inevitable positional shifts of wearable devices during use, the dual-band artificial magnetic conductor should be insensitive to the incident wave angle. Furthermore, given that wearable antennas may employ different polarization methods such as circular or linear polarization, the dual-band artificial magnetic conductor unit should be adaptable to antennas with different polarizations. Therefore, the designed dual-band artificial magnetic conductor should possess polarization insensitivity to meet the needs of various scenarios.

[0061] Specifically, Figure 5 This is a schematic diagram illustrating the effect of perpendicularly incident electromagnetic waves of different polarizations on the reflection phase characteristics of a dual-frequency artificial magnetic conductor, as provided in this embodiment of the invention. Figure 5As shown, taking polarization angles of 0°, 30°, 60° and 90° as examples, when electromagnetic waves with different polarization angles are perpendicularly incident on the dual-frequency artificial magnetic conductor, the phase reflection characteristics remain unchanged. That is, the reflection phase characteristic curves corresponding to different polarization angles almost overlap, which fully demonstrates that the dual-frequency artificial magnetic conductor is insensitive to the perpendicular incidence of electromagnetic waves with different polarizations. Figure 6 This is a schematic diagram illustrating the effect of different incident angles of the incident electromagnetic wave on the reflection phase characteristics of a dual-frequency artificial magnetic conductor, as provided in an embodiment of this utility model. Figure 6 As shown, when the incident angle of the incident electromagnetic wave increases from 0° to 60°, the zero-phase reflection at the low resonant frequency, i.e., 2.45GHz, has a negligible impact. Compared to the low resonant frequency, the zero-phase reflection at the high resonant frequency, i.e., 5.8GHz, has a slightly more significant impact, but the reflection frequency is still within the ±-90° range and does not affect the reflection effect of the dual-frequency artificial magnetic conductor at this frequency. Therefore, the dual-frequency artificial magnetic conductor provided in this embodiment of the present invention has the characteristic of being insensitive to different incident angles of the incident electromagnetic wave, which can effectively suppress the surface waves of the antenna, reduce the radiation of the antenna to the human body, and improve the antenna gain.

[0062] Figure 7 A comparison diagram of the reflection coefficient effects of a dual-band antenna without and with a dual-frequency artificial magnetic conductor provided for embodiments of this utility model is shown below. Figure 7 As shown, the curve corresponding to the antenna without a dual-frequency artificial magnetic conductor (i.e., only the antenna) is blue. The measured curve corresponding to the dual-band antenna with a dual-frequency artificial magnetic conductor is green, and the simulated curve corresponding to the dual-band antenna with a dual-frequency artificial magnetic conductor is red. The selected antennas operate at frequencies of 2.45 GHz and 5.85 GHz. Taking a dual-frequency artificial magnetic conductor with a 4*4 radiating element as an example, comparing the three curves reveals that after adding the dual-frequency artificial magnetic conductor, the reflection coefficient decreases from -19.07 dB to -25.56 dB at the low resonant frequency (2.45 GHz) and from -20.9 dB to -37.69 dB at the high resonant frequency (5.8 GHz). The measured and simulated results show small errors, demonstrating the good performance of the dual-frequency artificial magnetic conductor.

[0063] Figure 8 The 2D far-field radiation pattern of the antenna with a dual-frequency artificial magnetic conductor at 2.45 GHz provided in this embodiment of the invention. Figure 9 The 3D far-field radiation pattern of the antenna with a dual-frequency artificial magnetic conductor at 2.45 GHz provided for an embodiment of this utility model is shown below. Figure 8 and Figure 9As shown, the difference between the front and back lobes is greater than 15 dBi at 2.45 GHz. After loading the dual-frequency artificial magnetic conductor, the actual gain increased from 2.6 dBi to 7.19 dBi, indicating that the dual-frequency artificial magnetic conductor can play a good role in reflection, reducing back radiation and enhancing the actual gain.

[0064] Figure 10 The 2D far-field radiation pattern of the antenna with a dual-frequency artificial magnetic conductor at 5.8 GHz provided in this embodiment of the present invention is shown. Figure 11 The 3D far-field radiation pattern of the antenna with a dual-frequency artificial magnetic conductor at 5.8 GHz provided for an embodiment of this utility model is shown below. Figure 10 and Figure 11 As shown, the difference between the front and back lobes is greater than 20 dBi at 5.8 GHz. After loading the dual-frequency artificial magnetic conductor, the actual gain increased from 3.86 dBi to 10.1 dBi, indicating that the dual-frequency artificial magnetic conductor can play a good role in reflection, reducing back radiation and enhancing the actual gain.

[0065] Figure 12 This diagram illustrates the simulated specific absorptivity of a dual-band antenna with a dual-frequency artificial magnetic conductor loaded onto 1g of human tissue at 2.45GHz, as provided in this embodiment of the invention. Figure 13 A schematic diagram illustrating the simulated specific absorption rate at 2.45 GHz for a dual-band antenna with a dual-frequency artificial magnetic conductor loaded onto 10g of human tissue, as provided in this embodiment of the invention. Figure 12 and Figure 13 As shown, through simulation using electromagnetic field full-wave simulation software, at 2.45GHz, the specific absorptivity of the dual-band antenna with dual-frequency artificial magnetic conductor is 0.188W / kg (for 1g of human tissue) and 0.105W / kg (for 10g of human tissue), respectively. It can be seen that the dual-frequency artificial magnetic conductor can effectively reduce the radiation intensity of the antenna to the human body and reduce the specific absorptivity of the wearable antenna. That is, the dual-frequency artificial magnetic conductor can effectively suppress the back lobe radiation of the antenna and ensure the safety of the human body.

[0066] Figure 14 This diagram illustrates the simulated specific absorptivity at 5.8 GHz for a dual-band antenna with a dual-frequency artificial magnetic conductor loaded onto 1g of human tissue, as provided in an embodiment of this utility model. Figure 15 A schematic diagram illustrating the simulated specific absorption rate at 5.8 GHz for a dual-band antenna with a dual-frequency artificial magnetic conductor loaded onto 10g of human tissue, as provided in this embodiment of the invention. Figure 14 and Figure 15As shown, through simulation using electromagnetic field full-wave simulation software, at 5.8 GHz, the specific absorptivity of the dual-band antenna with dual-frequency artificial magnetic conductor is 0.174 W / kg (for 1g of human tissue) and 0.076 W / kg (for 10g of human tissue), respectively. It can be seen that the dual-frequency artificial magnetic conductor can effectively reduce the radiation intensity of the antenna to the human body and reduce the specific absorptivity of the wearable antenna. That is, the dual-frequency artificial magnetic conductor can effectively suppress the back lobe radiation of the antenna and ensure the safety of the human body.

[0067] The dual-frequency artificial magnetic conductor provided in this embodiment of the invention has a radiating structure comprising m*n arrayed radiating units. Each radiating unit consists of three parts: multiple T-shaped hollow structures, arc-shaped T-shaped structures, and a central structure. The multiple T-shaped hollow structures are located in the edge region, while the arc-shaped T-shaped structures and the central structure are located in the central region. The arc-shaped T-shaped structures are located on the side of the central structure furthest from the center of the radiating units, and the center of the central structure coincides with the center of the radiating units. The central structure includes an arc-shaped T-shaped portion and a circular portion connected together. The arc-shaped T-shaped portion is located on the side of the circular portion furthest from the center of the radiating units, and the arc-shaped T-shaped portions and arc-shaped T-shaped structures are arranged alternately. This results in a compact structure for the radiating unit. By adjusting the size and relative position of the gaps between the T-shaped hollow structures, arc-shaped T-shaped structures, and the central structure, the reflection phase characteristics of the dual-frequency artificial magnetic conductor unit can be adjusted. The dual-frequency artificial magnetic conductor has a compact structure and small electrical size, which facilitates the integration of wearable antennas with other devices. It can also be adapted to corresponding single-band and dual-band antennas. Furthermore, the dual-frequency artificial magnetic conductor has a good reflection effect, which can reduce the radiation of the antenna to the human body, thereby protecting the safety of the human body.

[0068] Optional, continue to refer to Figure 2 and Figure 3 The radiating element 30-1 includes two first boundaries 30-11 and two second boundaries 30-12; the two first boundaries 30-11 are along a first direction (e.g., Figure 3 Arranged in the X direction shown, and all along the second direction (as shown in the figure). Figure 3 As shown in the diagram, the two second boundaries 30-12 extend along the second direction Y and both extend along the first direction X; the first direction X intersects the second direction Y; along the first direction X, the minimum dimension ω1 between the two first boundaries 30-11 satisfies: 23.2mm≤ω1≤23.5mm; within the same radiating element 30-1, the ground plane 20 includes two third boundaries 201 and two fourth boundaries 202; the two third boundaries 201 are arranged along the first direction X and both extend along the second direction Y, and the two fourth boundaries 202 are arranged along the second direction Y and both extend along the first direction X; along the first direction X, the minimum dimension W between the two third boundaries 202 satisfies: 23.9mm≤W≤24.3mm.

[0069] Specifically, within the same radiation unit 30-1, there can be four T-shaped hollow structures 301, corresponding to the first boundary 30-11 and the second boundary 30-12 respectively. That is, four T-shaped hollow structures 301 are respectively set at the boundary positions of the radiation unit 30-1.

[0070] For example, when the ω1 of the T-shaped hollow structure 301 changes from 23mm to 23.6mm, the lower zero-phase reflection frequency shifts from 2.54GHz to 2.34GHz, while the higher-frequency zero-phase reflection frequency remains almost unchanged. The T-shaped hollow structure 301 can dominate the resonance at low frequencies. For example, if only the T-shaped hollow structure 301 is provided in the radiating unit 30-1, without the arc-shaped T-shaped structure 302 and the central structure 303, then the T-shaped hollow structure 301 can dominate the resonance at low frequencies, at which point the zero-phase reflection frequency is 2.41GHz and the reflection coefficient at zero phase is -1.02dB.

[0071] For details, please refer to [link / reference]. Figure 3 The radiating element 30-1 includes two first boundaries 30-11 and two second boundaries 30-12. The two first boundaries 30-11 are arranged along a first direction X and both extend along a second direction Y. The two second boundaries 30-12 are arranged along the second direction Y and both extend along the first direction X. That is, the shape of the radiating element 30-1 can be rectangular. Along the first direction X, the minimum dimension ω1 between the two first boundaries 30-11 satisfies: 23.2mm≤ω1≤23.5mm. This is beneficial for ensuring that the size of the radiating element 30-1 is moderate, which is beneficial for etching within the radiating element 30-1. On the other hand, it is also beneficial for ensuring that the structure of the radiating element 30-1 is compact.

[0072] It should be noted that physical size refers to the actual geometric dimensions of an object, while electrical size is related to the wavelength of the electromagnetic wave. Specifically, electrical size can be the ratio of physical size to the wavelength of the electromagnetic wave. Here, λ is the wavelength of the electromagnetic wave corresponding to the low-frequency center frequency of 2.45 GHz. For example, in the first direction X, the minimum electrical size between the two first boundaries 30-11 can be 0.189λ-0.192λ.

[0073] For details, please refer to [link / reference]. Figure 2The ground plane 20 includes two third boundaries 201 and two fourth boundaries 202. The two third boundaries 201 are arranged along the first direction X and both extend along the second direction Y. The two fourth boundaries 202 are arranged along the second direction Y and both extend along the first direction X. That is, the shape of the ground plane 20 within a radiating unit 30-1 can be rectangular. Along the first direction X, the minimum dimension W between the second boundaries 202 satisfies: 23.9mm≤W≤24.3mm. This ensures that within the same radiating unit 30-1, the size of the radiating unit 30-1 is slightly smaller than the size of the ground plane 20, and the size of the radiating unit 30-1 is slightly smaller than the size of the substrate 10. This is beneficial for the array arrangement of the radiating units 30-1 on the substrate 10 and also helps to ensure the conductivity of the ground plane 20.

[0074] For example, the minimum electrical dimension between the first direction X and the second boundary 202 can be 0.195λ-0.198λ.

[0075] For example, the shape of the radiating element 30-1 can be square.

[0076] Optional, continue to refer to Figure 3 The T-shaped hollow structure 301 includes a first hollow portion 3011 and a second hollow portion 3012 connected together; the extension direction of the first hollow portion 3011 intersects the extension direction of the second hollow portion 3012; the minimum dimension ω2 between the first hollow portion 3011 and the first boundary 30-11 satisfies: 2.3mm≤ω2≤2.8mm; the minimum dimension ω3 between the second hollow portion 3012 and the first boundary 30-11 satisfies: 11.1mm≤ω3≤11.3mm; the second hollow portion 3012 includes a first hollow edge 30121 and a second hollow edge 30122, and the minimum dimension ω4 between the first hollow edge 30121 and the second hollow edge 30122 satisfies: 0.2mm≤ω4≤3.5mm.

[0077] Specifically, by limiting 2.3mm≤ω2≤2.8mm, 11.1mm≤ω3≤11.3mm, and 0.2mm≤ω4≤3.5mm, the compactness of the radiating unit 30-1 structure can be achieved on the one hand, and the resonance at low frequencies can be dominated by the T-shaped hollow structure 301 on the other hand. At this time, the zero-phase reflection frequency is 2.41GHz, and the reflection coefficient at zero phase is -1.02dB.

[0078] For example, the minimum electrical dimension between the first cutout portion 3011 and the first boundary 30-11 can be 0.018λ-0.023λ. The minimum electrical dimension between the second cutout portion 3012 and the first boundary 30-11 can be 0.090λ-0.092λ. The minimum electrical dimension between the first cutout edge 30121 and the second cutout edge 30122 can be 0.001λ-0.029λ.

[0079] Optional, Figure 16 for Figure 3 A magnified diagram of the corresponding AA region, as shown below. Figure 3 and Figure 16 As shown, the arc-shaped T-structure 302 includes an arc-shaped portion 3021 and a connecting portion 3022 connected together; the arc-shaped portion 3021 includes a first end A and a second end B, and the line connecting the first end A and the center O of the radiating unit and the line connecting the second end B and the center O of the radiating unit form an angle θ1 that satisfies: 34°≤θ1≤49°; the length L of the connecting portion 3022 satisfies 2.09mm≤L≤2.49mm; the width ω5 of the connecting portion 3022 satisfies 0.1mm≤ω5≤2.5mm.

[0080] Specifically, an angle θ1 is formed between the line OA connecting the first end A to the center O of the radiating element and the line OB connecting the second end B to the center O of the radiating element. The larger the angle θ1, the larger the arc length of arc AB; the smaller the angle θ1, the smaller the arc length of arc AB. By setting 34°≤θ1≤49°, the angle θ1 can be kept moderate, which is beneficial to ensuring that the arc length of arc AB is moderate. The length L of the connecting section 3022 satisfies 2.09mm≤L≤2.49mm; the width ω5 of the connecting section 3022 satisfies 0.1mm≤ω5≤2.5mm. On the one hand, this ensures the compact structure of the radiating unit 30-1, and on the other hand, it helps to ensure that the T-shaped hollow structure 301 and the central structure 303 are coupled through the arc-shaped T-shaped structure 302. The low resonant frequency is shifted to 2.45GHz, and the high resonant frequency is shifted to 5.8GHz. The reflection coefficient of the low resonant frequency is -1.4dB, and the reflection coefficient of the high resonant frequency is -0.6dB. Thus, the dual-frequency artificial magnetic conductor has good in-phase reflection in both the 2.45GHz and 5.8GHz dual-bands.

[0081] For example, the electrical dimension of the angle formed between the first end A and the line OA connecting the center O of the radiating unit, and the second end B and the line OB connecting the center O of the radiating unit, can be 0.277λ-0.400λ.

[0082] For example, the electrical length of the connecting portion 3022 can be 0.017λ-0.020λ, and the electrical width of the connecting portion 3022 can be 0.001λ-0.020λ.

[0083] Optional, continue to refer to Figure 3 The dimension r1 between the first edge 31 and the center O of the radiating unit satisfies: 7mm≤r1≤7.3mm; the circular portion 3032 includes a third edge 33, and the dimension r2 between the third edge 33 and the center O of the radiating unit satisfies: 4.72mm≤r2≤5.02mm.

[0084] For example, when r1 changes from 7.1 mm to 7.4 mm, the lower zero-phase reflection frequency hardly changes, while the higher zero-phase reflection frequency shifts from 5.8 GHz to 5.36 GHz.

[0085] Specifically, by setting 7mm≤r1≤7.3mm and 4.72mm≤r2≤5.02mm, it can be ensured that the central structure 303 dominates the resonance at high frequencies. When there is only the central structure 303 and no T-shaped hollow structure 301 or arc-shaped T-shaped structure 302, the zero-phase reflection frequency is 8.17GHz and the reflection coefficient at zero phase is -0.7dB.

[0086] For example, the electrical dimension between the first edge 31 and the center O of the radiating unit can be 0.057λ-0.059λ, and the electrical dimension between the third edge 33 and the center O of the radiating unit can be 0.038λ-0.041λ.

[0087] Optional, continue to refer to Figure 3 The connecting portion 3022 includes a third end C on the side away from the center of the radiating element; the dimension r3 between the third end C and the center O of the radiating element satisfies: 8.1mm≤r3≤8.5mm.

[0088] Specifically, the third end C is located on the circumference BB. Therefore, the dimension r3 between the third end C and the center O of the radiating element is equal to the dimension from the center O of the radiating element to any point on the circumference BB. For example, when r3 changes from 8.3mm to 8.5mm, the lower zero-phase reflection frequency shifts from 2.45GHz to 2.33GHz, and the higher zero-phase reflection frequency shifts from 5.8GHz to 5.66GHz. Since 7mm≤r1≤7.3mm, by setting 8.1mm≤r3≤8.5mm, the size of the gap between the first edge 31 and the circumference BB can be adjusted according to the dimensions of r1 and r3, thereby adjusting the reflection phase characteristics of the dual-frequency artificial magnetic conductor unit to ensure that the dual-frequency artificial magnetic conductor has a better reflection effect, which can reduce the radiation of the antenna to the human body and thus protect the safety of the human body.

[0089] For example, the electrical dimension between the third end C and the center O of the radiating unit can be 0.066λ-0.069λ.

[0090] Figure 17 This is a schematic diagram of an equivalent resonant circuit for a radiating unit provided in an embodiment of the present invention. Figure 18 for Figure 17 The corresponding reflection phase curves of the radiating element and the equivalent resonant circuit are shown in the schematic diagrams. (Refer to...) Figure 3 , Figure 17 and Figure 18 When ω1 = 23.40 mm, W = 24 mm, ω2 = 2.60 mm, ω3 = 11.20 mm, ω4 = 1.00 mm, ω5 = 0.80 mm, r1 = 7.10 mm, r2 = 4.82 mm, r3 = 8.30 mm, L = 2.29 mm, and θ1 = 42°, the equivalent resonant circuit consists of three inductors and two capacitors. The second inductor L2 is connected in parallel with the first capacitor C1, then in series with the second capacitor C2, then in parallel with the third inductor L3, and finally in series with the first inductor L1. The loop formed by the second inductor L2 and the first capacitor C1 mainly affects the reflection phase characteristics at higher frequencies; the entire loop affects the reflection phase characteristics at 2.45 GHz and 5.8 GHz. (Continue to refer to...) Figure 18 The red curve almost overlaps with the black curve, meaning that the reflection phase characteristics of the equivalent resonant circuit and the radiating unit are basically consistent.

[0091] For example, the capacitance value of the first capacitor C1 can be 1.59nF, the capacitance value of the second capacitor C2 can be 1.45nF, the inductance value of the first inductor L1 can be 3.55nH, the inductance value of the second inductor L2 can be 0.70nH, and the inductance value of the third inductor L3 can be 1.98nH.

[0092] Optional, continue to refer to Figure 3 The central axis M of the arc-shaped T-shaped structure 302 is collinear with the central axis N of the T-shaped hollow structure 301.

[0093] Specifically, the connecting section 3022 is symmetrical about the central axis M, and the T-shaped hollow structure 301 is symmetrical about the central axis N. The central axis M of the arc-shaped T-shaped structure 302 is collinear with the central axis N of the T-shaped hollow structure 301, that is, the central axis M and the central axis N coincide, and the angle between the central axis M and the central axis N is zero. This ensures good reflection effect of the dual-frequency artificial magnetic conductor, reduces the radiation of the antenna to the human body, and protects human safety.

[0094] Optional, Figure 19 A schematic diagram of the structure of a second single radiating unit provided in an embodiment of this utility model is shown below. Figure 19 As shown, the included angle θ2 between the central axis M of the arc-shaped T-shaped structure 302 and the central axis N of the T-shaped hollow structure 301 satisfies: 0°<θ2≤30°.

[0095] Specifically, the central axis M of the arc-shaped T-structure 302 does not coincide with the central axis N of the T-shaped hollow structure 301, and the included angle θ2 between them satisfies: 0° < θ2 ≤ 30°. In other words, compared to Figure 3 For the radiating unit 30-1, the position of the T-shaped hollow structure 301 remains unchanged, while the arc-shaped T-shaped structure 302 rotates at an angle of θ2.

[0096] Figure 20 for Figure 19 A schematic diagram illustrating the effect of perpendicularly incident polarized electromagnetic waves on the reflection phase characteristics of a dual-frequency artificial magnetic conductor, as shown below. Figure 20 As shown, taking θ2 = 30° and polarization angles of 0°, 15°, and 30° as examples, the zero-phase reflection frequency in the low-frequency band remains unaffected, while the zero-phase reflection frequency in the higher-frequency band shifts slightly upward. However, the flexible dual-frequency artificial magnetic conductor unit structure can still achieve reflection at 2.45 GHz and 5.8 GHz, indicating that internal structure rotation has almost no impact on the function of the dual-frequency artificial magnetic conductor unit structure. Furthermore, internal structure rotation can reduce the alignment accuracy of the arc-shaped T-shaped structure and the T-shaped hollow structure, simplifying the fabrication process. It also allows for diverse configurations of the radiating unit structure, thereby enabling greater flexibility in the dual-frequency artificial magnetic conductor configuration.

[0097] Optional, continue to refer to Figure 1 The substrate 10 includes a flexible substrate.

[0098] Specifically, the substrate 10 includes a flexible substrate, so that the dual-frequency artificial magnetic conductor has certain bending resistance, strong applicability, and maintains good robustness while conforming to the human body.

[0099] For example, the flexible substrate can be made of felt material, which has a relatively low dielectric constant, i.e., a dielectric constant of 1.2. This results in lower dielectric loss, reducing energy loss during electromagnetic wave propagation and ensuring communication stability. It is understood that other flexible materials with low dielectric constants can also be used for the flexible substrate to ensure user comfort and conformal performance; those skilled in the art can flexibly replace these materials according to actual needs.

[0100] Figure 21 This is a schematic diagram illustrating the actual bending test results of a dual-band antenna with a loaded dual-frequency artificial magnetic conductor provided in an embodiment of this utility model. (Refer to...) Figure 1 and Figure 21 When a dual-band antenna with a dual-frequency artificial magnetic conductor is bent along the first direction X, wherein the bending axis is parallel to the second direction Y, and Figure 21 The blue curve represents the bending radius r. x=50mm corresponding to the reflection phase curve, the red curve represents the bending radius r x =75mm corresponds to the reflection phase curve, and the green curve represents the bending radius r. x The reflection phase curve corresponding to 100mm shows a slight shift at the 2.45GHz and 5.8GHz frequencies, but this does not affect the overall performance of the structure. This indicates that the dual-frequency artificial magnetic conductor maintains good robustness.

[0101] For example, the thickness of the substrate 10 can be 2.5 mm. For example, the materials of the radiating structure 30 and the ground plane can both be conductive cloth, and the thickness of the conductive cloth can be 0.9 mm. For example, the electrical dimensions of the dual-frequency artificial magnetic conductor can be a cube with a length of 0.2λ, a width of 0.2λ, and a height of 0.02λ, i.e., 0.2λ × 0.2λ × 0.02λ. Compared with the smaller point size of traditional dual-frequency artificial magnetic conductors, the dual-frequency artificial magnetic conductor structure provided in this embodiment of the present invention is compact.

[0102] Optional, continue to refer to Figure 1 Where m = 4 and n = 4, the radiation structure 30 comprises 4×4 arrayed radiation elements 30-1. The table below exemplarily shows the actual gains of the dual-frequency artificial magnetic conductor when m = 3, n = 3; m = 3, n = 4; m = 4, n = 4; and m = 5, n = 5.

[0103]

[0104]

[0105] As shown in the table above, the first resonant point can be at a frequency of 2.45 GHz, and the second resonant point can be at a frequency of 5.8 GHz. (Continue to refer to...) Figure 9 When m=4 and n=4, the gain corresponding to the first resonant point is 7.19 dBi. (Continue to refer to...) Figure 11 When m=4 and n=4, the gain corresponding to the second resonant point is 10.10dBi. Thus, the preferred embodiment of the radiation structure 30 includes 4×4 arrayed radiation units 30-1.

[0106] Optionally, both the radiating structure 30 and the ground plane 20 include a flexible conductive layer. The flexible conductive layer can be a flexible conductive layer made of conductive fiber cloth, or it can be a conductive layer formed of silver paste or copper foil.

[0107] Note that the above description is merely a preferred embodiment of the present invention and the technical principles employed. Those skilled in the art will understand that the present invention is not limited to the specific embodiments described herein, and various obvious changes, readjustments, combinations, and substitutions can be made without departing from the scope of protection of the present invention. Therefore, although the present invention has been described in detail through the above embodiments, the present invention is not limited to the above embodiments. Many other equivalent embodiments may be included without departing from the concept of the present invention, and the scope of the present invention is determined by the scope of the appended claims.

Claims

1. A dual-frequency artificial magnetic conductor, characterized in that, include: Base; The ground plane located on one side of the substrate; A radiating structure located on the other side of the substrate; the radiating structure includes m*n arrayed radiating units; each radiating unit includes a central region and an edge region surrounding the central region; the radiating unit also includes multiple T-shaped hollow structures, multiple arc-shaped T-shaped structures, and a central structure; Multiple T-shaped hollow structures are located in the edge region, and the arc-shaped T-shaped structure and the central structure are both located in the central region. The arc-shaped T-shaped structure is located on the side of the central structure away from the center of the radiating unit, and the center of the central structure coincides with the center of the radiating unit. The central structure includes an arc-shaped T-shaped portion and a circular portion connected together. The arc-shaped T-shaped portion is located on the side of the circular portion away from the center of the radiating unit, and the arc-shaped T-shaped portion and the arc-shaped T-shaped structure are arranged alternately. The arc-shaped T-shaped portion includes a first edge on the side away from the center of the radiating unit, and the first edge protrudes toward the side away from the center of the radiating unit; the arc-shaped T-shaped structure includes a second edge on the side close to the center of the radiating unit, and the second edge is recessed toward the side close to the center of the radiating unit; the first edge is located on the side of the second edge away from the center of the radiating unit. Where m≥2, n≥2, and m and n are both integers.

2. The dual-frequency artificial magnetic conductor according to claim 1, characterized in that, The radiating element includes two first boundaries and two second boundaries; the two first boundaries are arranged along a first direction and both extend along a second direction, and the two second boundaries are arranged along the second direction and both extend along the first direction; the first direction and the second direction intersect. Along the first direction, the minimum dimension ω1 between the two first boundaries satisfies: 23.2mm ≤ ω1 ≤ 23.5mm; Within the same radiating unit, the ground plane includes two third boundaries and two fourth boundaries; the two third boundaries are arranged along a first direction and both extend along a second direction, and the two fourth boundaries are arranged along the second direction and both extend along the first direction; along the first direction, the minimum dimension W between the two third boundaries satisfies: 23.9mm≤W≤24.3mm.

3. The dual-frequency artificial magnetic conductor according to claim 2, characterized in that, The T-shaped hollow structure includes a first hollow section and a second hollow section connected together; the extending direction of the first hollow section intersects with the extending direction of the second hollow section; The minimum dimension ω2 between the first hollowed-out portion and the first boundary satisfies: 2.3mm≤ω2≤2.8mm; The minimum dimension ω3 between the second hollowed-out portion and the first boundary satisfies: 11.1mm ≤ ω3 ≤ 11.3mm; The second hollowed-out portion includes a first hollowed-out edge and a second hollowed-out edge, and the minimum dimension ω4 between the first hollowed-out edge and the second hollowed-out edge satisfies: 0.2mm≤ω4≤3.5mm.

4. The dual-frequency artificial magnetic conductor according to claim 1, characterized in that, The arc-shaped T-shaped structure includes an arc-shaped portion and a connecting portion; The arc-shaped portion includes a first end and a second end, and the line connecting the first end and the center of the radiating unit and the line connecting the second end and the center of the radiating unit form an angle θ1 that satisfies: 34≤θ1≤49°; The length L of the connecting part satisfies 2.09mm≤L≤2.49mm; the width ω5 of the connecting part satisfies 0.1mm≤ω5≤2.5mm.

5. The dual-frequency artificial magnetic conductor according to claim 1, characterized in that, The dimension r1 between the first edge and the center of the radiating element satisfies: 7mm ≤ r1 ≤ 7.3mm; The circular portion includes a third edge, and the dimension r2 between the third edge and the center of the radiating unit satisfies: 4.72mm≤r2≤5.02mm.

6. The dual-frequency artificial magnetic conductor according to claim 4, characterized in that, The connecting portion includes a third end on the side furthest from the center of the radiating unit; The dimension r3 between the third end and the center of the radiating unit satisfies: 8.1mm≤r3≤8.5mm.

7. The dual-frequency artificial magnetic conductor according to claim 1, characterized in that, The central axis of the arc-shaped T-shaped structure is collinear with the central axis of the T-shaped hollow structure.

8. The dual-frequency artificial magnetic conductor according to claim 1, characterized in that, The included angle θ2 between the central axis of the arc-shaped T-shaped structure and the central axis of the T-shaped hollow structure satisfies: 0°<θ2≤30°.

9. The dual-frequency artificial magnetic conductor according to claim 1, characterized in that, The substrate includes a flexible substrate.

10. The dual-frequency artificial magnetic conductor according to claim 1, characterized in that, Both the radiating structure and the ground plane include a flexible conductive layer.

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