Device for compensating voltage or current

Abstract

To provide an active compensation device for compensating a first current which is inputted in a common mode to two or more large current paths which are connected to a first device.SOLUTION: An active compensation device 100 includes two or more large current paths 111, 112 for transmitting second currents I21, I22 supplied by a second device 200 to a first device 300, a detection unit 120 that detects first currents I11, I12 and generates an output signal corresponding to the first currents, an amplifier unit 130 that amplifies the output signal of the detection unit, a compensation unit 160 that generates compensation current based on the amplification current and supplies the compensation current to each of the at least two large current paths, a first disturbance protection unit connected in parallel to an output end of the detection unit 120 generating the output signal, and a second disturbance protection unit connected in parallel to an input end of the compensation unit. The first disturbance protection unit and the second disturbance protection unit include transient voltage suppressor diode elements.SELECTED DRAWING: Figure 1

Description

[Technical field]

[0001] An embodiment of the present invention relates to an active current (and / or voltage) compensation device that actively compensates for current and / or voltage input in common mode on two or more high current paths connecting two devices. [Background technology]

[0002] In general, electrical equipment such as home appliances, industrial electrical products, and electric vehicles emit noise during operation. For example, noise can be emitted through power lines due to the switching operation of a power conversion device in an electronic device. If left unchecked, this noise can not only be harmful to the human body, but can also cause malfunctions or failures in surrounding components and other electronic devices. The electromagnetic interference that electronic devices cause to other devices is called EMI (Electromagnetic Interference), and among these, noise transmitted via wires and wiring on boards is called conducted emission (CE) noise.

[0003] In order for electronic devices to operate without damaging peripheral components and other devices, the amount of EMI noise radiation in all electronic products is strictly regulated. Therefore, most electronic products must include a noise reduction device (e.g., EMI filter) to reduce EMI noise current to meet the regulations on noise radiation. For example, white goods such as air conditioners, electric vehicles, aerospace, and energy storage systems (ESS (Energy Storage Systems)) must include EMI filters. Conventional EMI filters use a common mode choke (CM choke), which is a passive filter, to reduce common mode (CM) noise in conducted radiation (CE) noise.

[0004] Meanwhile, with the release of high power products, the needs for current / voltage compensation devices for high power systems are increasing. However, in high power / high current systems, the noise reduction performance of common mode (CM) chokes drops sharply due to magnetic saturation. Therefore, in order to prevent magnetic saturation and maintain noise reduction performance in high power / high current systems, it has been necessary to increase the size and number of common mode chokes in the past, but this causes problems such as a significant increase in the size and price of current compensation devices for high power products. Summary of the Invention [Problem to be solved by the invention]

[0005] The present invention is directed to remedying the above problems, and provides a compensation device for reducing common mode (CM) noise.

[0006] Also, the present invention has been made to improve the above-mentioned problems, and provides a compensation device with a reduced size of a detection unit and improved productivity.

[0007] Another object of the present invention is to provide a compensation device that outputs a compensation current to the side from which EMI noise is radiated, regardless of the magnitude of the load on the side from which the EMI noise is radiated.

[0008] However, these challenges are exemplary and the scope of the invention is not limited thereto. [Means for solving the problem]

[0009] According to one embodiment of the present invention, an active compensation device that actively compensates for a first current input in a common mode to each of at least two or more high current paths connected to a first device includes at least two or more high current paths that transmit a second current supplied by a second device to the first device, a detection unit that detects the first current on the high current path and generates an output signal corresponding to the first current, an amplification unit that amplifies the output signal of the detection unit and generates an amplified current, a compensation unit that generates a compensation current based on the amplified current and flows the compensation current through each of the at least two or more high current paths, a first disturbance protection unit connected in parallel to an output end of the detection unit that generates the output signal, and a second disturbance protection unit connected in parallel to an input end of the compensation unit, wherein the first disturbance protection unit and the second disturbance protection unit include a transient voltage suppressor (TVS (Transient Voltage Suppression)) diode element, and the junction capacitance of the TVS diode element may be several hundred pF or less.

[0010] According to one embodiment, the first disturbance protection unit and the second disturbance protection unit have a first impedance when a voltage less than a predetermined critical voltage is applied to the output terminal of the detection unit and the input terminal of the compensation unit, and have a second impedance lower than the first impedance when a voltage equal to or greater than the predetermined critical voltage is applied to the output terminal of the detection unit and the input terminal of the compensation unit.

[0011] According to an embodiment, the detection unit may include a detection transformer including a primary side disposed on the high current path and a secondary side that outputs the output signal to the amplification unit.

[0012] According to one embodiment, in the first disturbance protection unit, the primary side may limit a voltage equal to or greater than a critical voltage induced in the secondary side to a voltage equal to or less than the critical voltage based on the voltage applied to the at least two or more large current paths, and transmit the limit to the amplifier unit.

[0013] According to one embodiment, the compensation unit includes a primary side arranged on a path connecting the output terminal of the amplifier unit and a reference potential of the amplifier unit, and a secondary side included in the compensation unit and arranged on a path connecting a compensation capacitor unit connected to the large current path and a reference potential of the active compensation device, and in the second disturbance protection unit, the secondary side limits a voltage equal to or greater than a critical voltage induced on the primary side to a voltage equal to or less than the critical voltage based on the voltage applied to the at least two or more large current paths, and transmits the voltage to the amplifier unit.

[0014] Other aspects, features, and advantages in addition to those described above will become apparent from the following detailed description, claims, and drawings. Effect of the Invention

[0015] According to various embodiments of the present invention configured as described above, it is possible to provide an active current / voltage compensation device that does not significantly increase the price, area, volume, or weight even in a high-power system.

[0016] Active compensation devices according to various embodiments of the present invention may have reduced cost, area, volume, and weight compared to passive compensation devices that include CM chokes.

[0017] Furthermore, the current compensation device according to an embodiment of the present invention can provide a compensation device that is not parasitic on the CM choke and can operate independently.

[0018] In addition, the active compensation devices according to various embodiments of the present invention have an active circuit end that is electrically isolated from the power line, thereby enabling the elements included in the active circuit end to be stably protected.

[0019] In addition, an active compensation device according to an embodiment of the present invention can provide a current compensation device that can perform a current compensation function regardless of the load of the surrounding conditions on the side where EMI noise is radiated. Of course, the scope of the present invention is not limited to these effects. [Brief description of the drawings]

[0020] [Figure 1] FIG. 1 shows a schematic configuration of a system including an active compensation device 100 according to an embodiment of the present invention. [Diagram 2] FIG. 2 is a diagram illustrating an example of the embodiment shown in FIG. [Diagram 3] FIG. 3 shows a more specific example of the embodiment shown in FIG. 2, and shows a schematic diagram of a compensation device 100A according to an embodiment of the present invention. [Figure 4A] FIG. 4A is a diagram illustrating the operation of the detection transformer 120A, which is an example of the detection unit 120 according to an embodiment of the present invention. [Figure 4B] FIG. 4B is a diagram illustrating the operation of the detection transformer 120A, which is an example of the detection unit 120 according to an embodiment of the present invention. [Figure 5A] FIG. 5A is a diagram illustrating a sensing transformer 120A including a core 123A of an openable and closable clamp structure according to one embodiment of the present invention. [Figure 5B] FIG. 5B is a diagram illustrating a sensing transformer 120A including a core 123A with an openable and closable clamp structure according to one embodiment of the present invention. [Figure 6] FIG. 6 is a diagram illustrating the currents IL1 and IL2 that flow through the compensation capacitor section 150A. [Figure 7] FIG. 7 illustrates a schematic diagram of an active compensation device 100A-1 according to one embodiment of the present invention. [Figure 8] FIG. 8 illustrates a schematic diagram of an active compensation device 100A-2 according to one embodiment of the present invention. [Figure 9A] FIG. 9A illustrates a schematic diagram of a compensation device 100A-3 according to one embodiment of the present invention. [Figure 9B] FIG. 9B is a simplified diagram of the amplifier of FIG. 9A. [Figure 10A] FIG. 10A is a diagram illustrating an amplifier unit 130A-4 of a compensation device 100A-4 according to an embodiment of the present invention. [Figure 10B] FIG. 10B is a diagram illustrating an amplifier unit 130A-4 of a compensation device 100A-4 according to an embodiment of the present invention. [Figure 11] FIG. 11 is a diagram illustrating a schematic configuration of a compensation device 100B according to another embodiment of the present invention. [Figure 12] FIG. 12 is a diagram illustrating a schematic configuration of a compensation device 100C according to still another embodiment of the present invention. [Figure 13] FIG. 13 is a diagram illustrating a schematic configuration of a system in which the compensation device 100B according to the embodiment shown in FIG. 11 is used, according to an embodiment of the present invention. [Figure 14] FIG. 14 shows a schematic diagram of a system including an active compensation device 101 according to one embodiment of the invention. [Figure 15] FIG. 15 is a schematic diagram of a specific example of the compensation device 101 according to the embodiment shown in FIG. [Figure 16] FIG. 16 is a diagram illustrating a schematic configuration of a compensation device 101C according to an embodiment of the present invention. [Figure 17] FIG. 17 shows a schematic configuration of a system including a compensation device 102 according to an embodiment of the present invention. [Figure 18] FIG. 18 illustrates a schematic diagram of a compensation device 102A according to one embodiment of the present invention. [Figure 19] FIG. 19 illustrates a schematic diagram of a compensation device 102A-1 according to one embodiment of the present invention. [Figure 20] FIG. 20 illustrates a schematic diagram of a compensation device 102A-2 according to one embodiment of the present invention. [Figure 21] FIG. 21 is a diagram illustrating a schematic configuration of a compensation device 102B according to an embodiment. [Figure 22] FIG. 22 is a diagram illustrating a schematic configuration of a compensation device 102C according to another embodiment of the present invention. [Figure 23] FIG. 23 is a diagram illustrating a schematic configuration of a compensation device 102D according to another embodiment of the present invention. [Figure 24]FIG. 24 is a diagram illustrating a schematic configuration of a system including a compensation device 103 according to an embodiment of the present invention. [Diagram 25] FIG. 25 is a diagram illustrating a schematic configuration of a compensation device 103A for use in a two-wire system according to one embodiment of the present invention. [Figure 26A] FIG. 26A is a diagram illustrating a malfunction detector 60A according to one embodiment. [Figure 26B] FIG. 26B is a diagram illustrating a malfunction detector 60A according to one embodiment. [Figure 26C] FIG. 26C is a diagram illustrating a malfunction detector 60A according to one embodiment. [Figure 27] FIG. 27 is a diagram illustrating a schematic configuration of a compensation device 103B according to another embodiment of the present invention. [Figure 28] FIG. 28 is a diagram illustrating a schematic configuration of a system including a compensation device 104 according to an embodiment of the present invention. [Figure 29] FIG. 29 is a diagram illustrating a schematic configuration of a compensation device 104A used in a three-phase, four-wire system according to one embodiment of the present invention. [Diagram 30] FIG. 30 is a diagram illustrating the configuration and operation of a first balance section 70A according to one embodiment. [Diagram 31] FIG. 31 is a diagram illustrating the configuration and operation of a second balance section 80A according to one embodiment. [Diagram 32] FIG. 32 is a diagram showing a schematic configuration of a compensation device 104B used in a three-phase three-wire system according to another embodiment of the present invention. [Diagram 33] FIG. 33 is a diagram illustrating a schematic configuration of a compensation device 104C according to still another embodiment of the present invention. [Diagram 34] FIG. 34 is a diagram illustrating a schematic configuration of a compensation device 104D used in a three-phase four-wire system according to still another embodiment of the present invention. [Diagram 35] FIG. 35 is a diagram illustrating a schematic configuration of a system including a compensation device 105 according to an embodiment of the present invention. [Diagram 36]FIG. 36 is a diagram illustrating a schematic configuration of a compensation device 105A used in a three-phase four-wire system according to one embodiment of the present invention. [Figure 37] FIG. 37 is a diagram illustrating a process in which the compensation current IC generated by the compensation transformer section 140A is distributed to the large current paths 111A, 112A, 113A, and 114A through the compensation capacitor section 150A and the second balance section 80A. [Figure 38] FIG. 38 is a diagram for explaining the process in which the output impedances Zeq31, Zeq32, Zeq33, and Zeq34 are adjusted by the second balance section 80A and the output impedance adjuster 50A. [Figure 39] FIG. 39 is a diagram showing a schematic configuration of a compensation device 105B used in a three-phase three-wire system according to another embodiment of the present invention. [Diagram 40] FIG. 40 shows a schematic diagram of a system including an active compensation device 106 according to an embodiment of the present invention. [Diagram 41] FIG. 41 shows a more specific example of the embodiment shown in FIG. 40 in which two amplifier units are used. [Diagram 42] FIG. 42 illustrates a specific example of the active compensation device 106A1. [Diagram 43] FIG. 43 shows a more specific example of the embodiment shown in FIG. 40, and shows a schematic diagram of a system including an active compensation device 106B according to an embodiment of the present invention. [Diagram 44] FIG. 44 illustrates a schematic diagram of a compensation device 106B1 as an example of the compensation device 106B illustrated in FIG. [Diagram 45] FIG. 45 illustrates a schematic diagram of an active compensation device 106B2 as another example of the active compensation device 106B illustrated in FIG. [Figure 46] FIG. 46 shows a schematic configuration of a system including an active compensation device 106D according to another embodiment of the present invention. [Figure 47] FIG. 47 shows a schematic configuration of a system including an active compensation device 106F according to an embodiment of the present invention. [Figure 48] FIG. 48 is a schematic diagram of a compensation device 106F1 as an example of the active compensation device 106F shown in FIG. [Figure 49] FIG. 49 illustrates a compensation device 106F2 as another example of the active compensation device 106F illustrated in FIG. [Figure 50] FIG. 50 shows a schematic configuration of a system including a compensation device 107 according to an embodiment of the present invention. [Figure 51] FIG. 51 shows a more specific example of the embodiment shown in FIG. 50, and shows a schematic diagram of a compensation device 107B according to an embodiment of the present invention. [Figure 52] FIG. 52 shows a schematic diagram of compensation devices 107C1 and 107C2 according to an embodiment of the present invention, as a specific example of the compensation device shown in FIG. [Diagram 53] FIG. 53 shows a schematic diagram of compensation devices 107C1 and 107C2 according to an embodiment of the present invention, as a specific example of the compensation device shown in FIG. [Figure 54] FIG. 54 shows a schematic configuration of a system including a compensation device 107D according to another embodiment of the present invention. [Figure 55] FIG. 55 illustrates an outline of the functional configuration of an active compensation device 106E according to another embodiment of the present invention. [Figure 56] FIG. 56 illustrates a schematic diagram of an active compensation device 106E1 as an example of the active compensation device 106E illustrated in FIG. [Figure 57] FIG. 57 illustrates a schematic diagram of an active compensation device 106E2 as another example of the active compensation device 106E illustrated in FIG. [Figure 58] FIG. 58 is a diagram showing a schematic configuration of a system including a compensation device 108 according to an embodiment of the present invention. [Figure 59] FIG. 59 is a diagram illustrating a schematic configuration of a compensation device 108A for use in a second wire system according to one embodiment of the present invention. [Figure 60] FIG. 60 is a diagram for explaining a specific operation of compensation device 108A according to one embodiment of the present invention. [Figure 61] FIG. 61 is a diagram illustrating a reduction in impedance of the compensation capacitor section in compensation device 108A according to one embodiment of the present invention. [Figure 62] FIG. 62 is a diagram illustrating the flow of the first currents I11 and I12 in the compensation device 108A according to one embodiment of the present invention. [Figure 63] FIG. 63 is a simulation graph comparing the noise reduction performance of a VSCC compensator 108A according to one embodiment of the present invention and a passive EMI filter (or passive compensator) having a capacitance value similar to that of the VSCC compensator 108A. [Figure 64] FIG. 64 is a diagram showing a schematic configuration of a compensation device 108B according to another embodiment of the present invention. DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

[0021] The present invention can be modified in various ways and can have various embodiments, and specific embodiments are illustrated in the drawings and described in detail in the detailed description. The advantages and features of the present invention, as well as methods for achieving them, will become clearer with reference to the embodiments described in detail below in conjunction with the drawings. However, the present invention is not limited to the embodiments disclosed below, and can be realized in various forms.

[0022] Hereinafter, embodiments of the present invention will be described in detail with reference to the accompanying drawings. When describing the embodiments with reference to the drawings, the same or corresponding components are given the same or similar reference numerals, and duplicate descriptions thereof will be omitted.

[0023] In the following examples, terms such as first and second are used to distinguish one component from another, not in a limiting sense. In the following examples, singular expressions include plural expressions unless a different meaning is clearly intended in the context. In the following examples, terms such as "include" or "have" mean that a feature or component described in the specification is present, and do not preclude the possibility that one or more other features or components may be added. In the drawings, the size of components may be enlarged or reduced for convenience of explanation. If an embodiment can be realized in another way, the order of certain steps may be performed in an order different from the order described. In the following examples, when it is said that a region, component, part, unit, module, etc. are connected, it includes not only the case where the region, component, part, unit, module is directly connected, but also the case where another region, component, part, unit, module is interposed between the region, component, part, module, and module and the region, component, part, module is indirectly connected.

[0024] For example, the size and shape of each component shown in the drawings are arbitrarily shown for convenience of explanation, and the present invention is not necessarily limited to the drawings.

[0025] An active compensator or compensator as referred to in this document may include a current compensator and / or a voltage compensator, and the term current compensator is interchangeable with voltage compensator. Furthermore, at least a part of the compensation devices according to different embodiments may be applied to the various compensation devices according to the various embodiments described below.

[0026] 1 illustrates a schematic configuration of a system including an active compensation apparatus 100 according to an embodiment of the present invention. The active compensation apparatus 100 may actively compensate for first currents I11 and I12 (e.g., EMI noise currents) input in common mode (CM) from a first device 300 through two or more large current paths 111 and 112.

[0027] Referring to FIG. 1, the active compensation device 100 may include a detection section 120, an amplification section 130, and a compensation section 160.

[0028] In this specification, the first device 300 may be a device of various forms that uses the power source supplied by the second device 200. For example, the first device 300 may be a load that is driven using the power source supplied by the second device 200. The first device 300 may also be a load (e.g., an electric vehicle) that stores energy using the power source supplied by the second device 200 and is driven using the stored energy. However, the first device 300 is not limited to this.

[0029] In this specification, the second device 200 may be a device of various forms for supplying power to the first device 300 in the form of current and / or voltage. For example, the second device 200 may be a device that generates and supplies power, or may be a device that supplies power generated by another device (for example, a charging device for an electric vehicle). Of course, the second device 200 may be a device that supplies stored energy. However, the present invention is not limited to this. A power conversion device may be located on the first device 300 side. For example, the first currents I11 and I12 may be input to the compensation device 100 by the switching operation of the above-mentioned power conversion device. That is, the first current I11 and I12 may correspond to a noise source on the first device 300 side, or may correspond to a noise receiver on the second device 200 side.

[0030] The two or more high current paths 111 and 112 may be paths for transmitting the power source supplied by the second device 200, i.e., the second currents I21 and I22 to the first device 300, and may be, for example, power lines. For example, each of the two or more high current paths 111 and 112 may be a live line and a neutral line. At least a part of the high current paths 111 and 112 may pass through the compensation device 100. The second currents I21 and I22 may be alternating currents having a frequency in a second frequency band. The second frequency band may be, for example, a band of 50 Hz to 60 Hz.

[0031] Furthermore, the two or more high current paths 111 and 112 may be paths through which noise generated in the first device 300, i.e., the first currents I11 and I12, are transmitted to the second device 200. The first currents I11 and I12 may be input to a common mode for each of the two or more high current paths 111 and 112. The first currents I11 and I12 may be currents that are unintentionally generated from the first device 300 due to various causes. For example, the first currents I11 and I12 may be noise currents generated by a virtual capacitance between the first device 300 and the surrounding environment. Alternatively, the first currents I11 and I12 may be noise currents generated by a switching operation of a power conversion device of the first device 300. The first currents I11 and I12 may be currents having a frequency in a first frequency band. The first frequency band may be a frequency band higher than the second frequency band described above. The first frequency band may be, for example, a band between 150 KHz and 30 MHz.

[0032] On the other hand, the two or more high current paths 111 and 112 may include two paths as shown in Figure 1, or may include three paths or four paths as shown in Figures 8 and 9. The number of high current paths 111 and 112 may vary depending on the type and / or form of the power source used by the first device 300 and / or the second device 200.

[0033] The detection unit 120 may sense the first currents I11 and I12 on the two or more high current paths 111 and 112 and generate output signals corresponding to the first currents I11 and I12. That is, the detection unit 120 may mean a means for sensing the first currents I11 and I12 on the high current paths 111 and 112. At least a part of the high current paths 111 and 112 may pass through the detection unit 120 to detect the first currents I11 and I12, but a part of the detection unit 120 where an output signal is generated by detection may be insulated from the high current paths 111 and 112. For example, the detection unit 120 may be realized by a detection transformer. The detection transformer may sense the first currents I11 and I12 on the high current paths 111 and 112 while being insulated from the high current paths 111 and 112.

[0034] According to an embodiment, the detection unit 120 may be differentially connected to the input terminal of the amplification unit 130 .

[0035] The amplifier 130 may be electrically connected to the detector 120 and may amplify the output signal output by the detector 120 to generate an amplified output signal. In the present invention, "amplification" by the amplifier 130 may mean adjusting the magnitude and / or phase of the target to be amplified. The amplifier 130 may be realized by various means and may include active elements. In one embodiment, the amplifier 130 may include an OP-AMP. For example, the amplifier 130 may include a plurality of passive elements such as resistors and capacitors in addition to the OP-AMP. In another embodiment, the amplifier 130 may include a BJT (Bipolar Junction Transistor). For example, the amplifier 130 may include a plurality of passive elements such as resistors and capacitors in addition to the BJT. However, without being limited thereto, the means for "amplification" described in the present invention may be used without being limited as the amplifier 130 of the present invention. The reference potential (reference potential 2) of the amplifier 130 and the reference potential (reference potential 1) of the compensation device 100 may be potentials that are distinct from each other.

[0036] The amplifier 130 may receive power from a third unit 400 that is distinct from the first unit 300 and / or the second unit 200, amplify the output signal output by the detector 120, and generate an amplified current. In this case, the third unit 400 may be a device that receives power from a power source that is not related to the first unit 300 and the second unit 200, and generates an input power supply for the amplifier 130. Alternatively, the third unit 400 may be a device that receives power from any one of the first unit 300 and the second unit 200, and generates an input power supply for the amplifier 130.

[0037] The compensation unit 160 may generate a compensation current based on the output signal amplified by the amplifier unit 130. The output side of the compensation unit 160 may be connected to the large current paths 111 and 112 to pass compensation currents IC1 and IC2 through the large current paths 111 and 112, but may be insulated from the amplifier unit 130. For example, the compensation unit 160 may include a compensation transformer for the above-mentioned insulation. For example, the output signal of the amplifier unit 130 may flow through the primary side of the compensation transformer, and a compensation current based on the above-mentioned output signal may be generated on the secondary side of the compensation transformer.

[0038] The compensation unit 160 may inject or extract compensation currents IC1 and IC2 into or from the two or more high current paths 111 and 112 through the two or more high current paths 111 and 112, respectively, to cancel the first currents I11 and I12. According to an embodiment, the compensation currents IC1 and IC2 may have the same magnitude and opposite phase to the first currents I11 and I12, but are not limited thereto.

[0039] FIG. 2 is a diagram illustrating an example of the embodiment shown in FIG. Referring to FIG. 2, the compensation section 160 may include a compensation transformer section 140 and a compensation capacitor section 150 .

[0040] The compensation transformer unit 140 may be electrically connected to the amplifier unit 130 and generate a compensation current based on the output signal amplified by the amplifier unit 130 described above.

[0041] The compensation transformer section 140 may be electrically connected to a path connecting the output end of the amplifier section 130 and a reference potential (reference potential 2) of the amplifier section 130 to generate a compensation current. The compensation transformer section 140 may be electrically connected to a path connecting the compensation capacitor section 150 and a reference potential (reference potential 1) of the current compensation device 100. The reference potential (reference potential 2) of the amplifier section 130 and the reference potential (reference potential 1) of the current compensation device 100 may be potentials distinct from each other.

[0042] The compensation capacitor section 150 can provide a path through which the compensation currents IC1 and IC2 generated by the compensation transformer section 140 flow to each of two or more large current paths.

[0043] According to an embodiment, the compensation capacitor unit 150 may be realized as a compensation capacitor unit 150 that provides a path through which the current generated by the compensation transformer unit 140 flows to each of the two or more high current paths 111 and 112. In this case, the compensation capacitor unit 150 may include at least two or more compensation capacitors that connect a reference potential (reference potential 1) of the current compensation device 100 to each of the two or more high current paths 111 and 112.

[0044] The current compensation device 100 configured as described above may sense and actively compensate for specific conditions of current on two or more high current paths 111 and 112, and may be applied to high current, high voltage, and / or high power systems despite the miniaturization of the device 100.

[0045] Meanwhile, according to an embodiment, the detection unit 120 may have a through opening into which at least two or more high current paths are inserted. The detection unit 120 may sense a first current on the inserted two or more high current paths and generate an output signal corresponding to the sensed first current.

[0046] In one embodiment, the detection unit 120 may be realized as a detection transformer including a core having a through opening and generating an output signal based on a magnetic flux density generated by a first current on at least two or more high current paths. In this case, the core may be an openable and closable clamp structure, and may be realized such that, in an open state, each of the at least two or more high current paths is inserted inside the core.

[0047] In one embodiment, the term "clamp structure" may refer to a structure in which an outer portion of a core is configured to be openable and closable. For example, the outer portion of the core of the clamp structure may be configured to be in an open state so that the high-current paths 111 and 112 are inserted into the through openings. Thereafter, the open outer portion of the core may be closed to prevent the inserted high-current paths 111 and 112 from being removed.

[0048] However, the above description of the detector 120 is merely an example, and the concept of the present invention is not limited thereto. Therefore, a current sensing means that is coupled to a path (or conductor) through which a current to be sensed flows in a form of being "inserted" therein may be used as the detector 120 of the present invention without any limitation.

[0049] Fig. 3 shows a more specific example of the embodiment shown in Fig. 2, and illustrates a compensation device 100A according to an embodiment of the present invention. The compensation device 100A may actively compensate for first currents I11 and I12 (e.g., noise currents) input in common mode to two large current paths 111A and 112A connected to a first device 300A, respectively.

[0050] Referring to FIG. 2, the compensation device 100A may include a sensing transformer 120A, an amplifier section 130A, and a compensation section 160A.

[0051] In one embodiment, the detection unit 120 may include a detection transformer 120A. In this case, the detection transformer 120A may be a means for sensing the first currents I11 and I12 on the high current paths 111A and 112A in a state insulated from the high current paths 111A and 112A. The detection transformer 120A may detect the first currents I11 and I12, which are noise currents input from the first device 300A side to the high current paths 111A and 112A (e.g., power lines).

[0052] The detection transformer 120A may include a primary side 121A arranged on the high current paths 111A and 112A and a secondary side 122A differentially connected to the input terminal of the amplifier unit 130A. The detection transformer 120A may generate an induced current in the secondary side 122A (e.g., secondary winding) based on the magnetic flux density induced by the first currents I11 and I12 in the primary side 121A (e.g., primary winding) arranged on the high current paths 111A and 112A. The primary side 121A of the detection transformer 120A may be, for example, a winding in which the first high current path 111A and the second high current path 112A are wound around one core. However, the present invention is not limited thereto, and the primary side 121A of the detection transformer 120A may be in a form in which the first high current path 111A and the second high current path 112A pass through the core.

[0053] Specifically, the magnetic flux density induced by the first current I11 on the first large current path 111A (e.g., a live line) and the magnetic flux density induced by the first current I12 on the second large current path 112A (e.g., a neutral line) may be configured to overlap (or reinforce). At this time, the second currents I21 and I22 also flow on the large current paths 111A and 112A, but the magnetic flux density induced by the second current (I21) on the first large current path 111A and the magnetic flux density induced by the first current (I22) on the second large current path (112A) may be configured to cancel each other out. Also, as an example, in the detection transformer 120A, the magnitude of the magnetic flux density induced by the first currents I11 and I12 in a first frequency band (e.g., a band having a range of 150 KHz to 30 MHz) may be configured to be greater than the magnitude of the magnetic flux density induced by the second currents I21 and I22 in a second frequency band (e.g., a band having a range of 50 Hz to 60 Hz).

[0054] In this manner, the detection transformer 120A may be configured such that the magnetic flux densities induced by the second currents I21 and I22 cancel each other out, and only the first currents I11 and I12 are sensed. That is, the current induced in the secondary side 122A of the detection transformer 120A may be a current obtained by converting the first currents I11 and I12 at a constant ratio.

[0055] For example, in the detection transformer 120A, the winding ratio between the primary side 121A and the secondary side 122A is 1:N. sen In this case, the current induced in the secondary side 122A is 1 / N of the first currents I11 and I12. senThe secondary side 122A of the detection transformer 120A may be connected to the input end of the amplifier unit 130A. For example, the secondary side 122A of the detection transformer 120A may be differentially connected to the input end of the amplifier unit 130A to supply an induced current to the amplifier unit 130A. Alternatively, depending on the configuration of the amplifier unit 130A, the secondary side 122A of the detection transformer 120A may be disposed on a path connecting the input end of the amplifier unit 130A and a reference potential (reference potential 2) of the amplifier unit 130A. That is, one end of the secondary side 122A may be connected to the input end of the amplifier unit 130A, and the other stage of the secondary side 122A may be connected to the reference potential (reference potential 2) of the amplifier unit 130A.

[0056] The amplifier unit 130A may correspond to the above-described amplifier unit 130. The amplifier unit 130A may amplify the current sensed by the detection transformer 120A and induced in the secondary side 122A. For example, the amplifier unit 130A may amplify the magnitude of the induced current at a certain ratio and / or adjust the phase.

[0057] The compensation unit 160A may correspond to the compensation unit 160 described above. The compensation unit 160A may include a compensation transformer 140A and a compensation capacitor unit 150A. The amplified current amplified by the amplifier unit 130A described above flows to the primary side 141A of the compensation transformer 140A.

[0058] The compensation transformer 140A may be a means for isolating the amplifier section 130A including the active element from the high current paths 111A and 112A. In other words, the compensation transformer 140A may be a means for generating (on the secondary side 142A) a compensation current to be injected into the high current paths 111A and 112A based on the amplified current while being insulated from the high current paths 111A and 112A.

[0059] The compensation transformer 140A may include a primary side 141A differentially connected to the output terminal of the amplifier unit 130A, and a secondary side 142A connected to the large current paths 111A and 112A. The compensation transformer 140A may induce a compensation current in the secondary side 142A (e.g., a secondary winding) based on the magnetic flux density induced by the amplified current flowing through the primary side 141A (e.g., a primary winding).

[0060] At this time, the secondary side 142A may be disposed on a path connecting the compensation capacitor section 150A described later and the reference potential (reference potential 1) of the current compensation device 100A. That is, one end of the secondary side 142A may be connected to the large current paths 111A and 112A through the compensation capacitor section 150A, and the other end of the secondary side 142A may be connected to the reference potential (reference potential 1) of the compensation device 100A. On the other hand, the primary side 141A of the compensation transformer 140A, the amplifier section 130A, and the secondary side 122A of the detection transformer 120A may be connected to a reference potential (reference potential 2) that is distinguished from the remaining components of the compensation device 100A. The reference potential (reference potential 1) of the current compensation device 100A and the reference potential (reference potential 2) of the amplifier section 130A may be distinguished.

[0061] In this manner, the present invention allows the components generating the compensation current to operate in an isolated state by using a different reference potential and a different power supply for the components generating the compensation current than for the remaining components, thereby improving the reliability of the compensation device 100A.

[0062] In the compensation transformer 140A, the winding ratio between the primary side 141A and the secondary side 142A is 1:N. inj Then, the current induced in the secondary side 142A is 1 / N of the current (i.e., the amplified current) flowing in the primary side 141A. inj It may be double.

[0063] The current transformed through the compensation transformer 140A may be injected as compensation currents IC1 and IC2 into the high current paths 111A and 112A (e.g., power lines) through the compensation capacitor section 150A. As described above, the compensation capacitor section 150A can provide a path through which the current generated by the compensation transformer 140A flows into each of the two high current paths 111A and 112A.

[0064] According to one embodiment, the compensation currents IC1 and IC2 may have the same magnitude and opposite phase as the first currents I11 and I12 to cancel the first currents I11 and I12. Thus, the magnitude of the current gain of the amplifier section 130A is N sen N inj It may be designed to be.

[0065] The compensation capacitor unit 150A may include two Y-capacitors, one end of which is connected to the secondary side 142A of the compensation transformer 140A and the other end of which is connected to the high current paths 111A and 112A. One end of each of the two Y-caps may share a node connected to the secondary side 142A of the compensation transformer 140A, and the opposite ends of each of the two Y-caps may have nodes connected to the first high current path 111A and the second high current path 112A, respectively.

[0066] The compensation capacitor unit 150A may cause the compensation currents IC1 and IC2 induced by the compensation transformer 140A to flow in the power line. For example, the compensation currents IC1 and IC2 compensate (or cancel) the first currents I11 and I12, so that the current compensation device 100A can reduce noise. The compensation device 100A may achieve an isolated structure by utilizing a compensation transformer 140A and a sensing transformer 120A.

[0067] 4A and 4B are diagrams illustrating the operation of the detection transformer 120A, which is an example of the detection unit 120 according to an embodiment of the present invention.

[0068] In particular, FIG. 4A is a diagram illustrating the principle by which the detection transformer 120A generates the first induced current ID1.

[0069] For ease of explanation, the following description will be given on the assumption that the primary side 121A and secondary side 122A of the detection transformer 120A are configured as shown in Fig. 4A. In other words, the following description will be given on the assumption that the windings of the large current paths 111A and 112A and secondary side 122A are wound around the core 123A of the detection transformer 120A in consideration of the direction in which the magnetic flux and / or magnetic flux density is generated.

[0070] When a first current I11 is input to the large current path 111A, a magnetic flux density B11 can be induced in the core 123A. Similarly, when a first current I12 is input to the large current path 112A, a magnetic flux density B12 can be induced in the core 123A.

[0071] A first induced current ID1 may be induced in the winding of the secondary side 122A due to the induced magnetic flux densities B11 and B12.

[0072] In this manner, the detection transformer 120A may be configured so that the first magnetic flux densities B11 and B12 induced by the first currents I11 and I12 can overlap (or reinforce each other) and generate a first induced current ID1 corresponding to the first currents I11 and I12 on the secondary side 122A that is insulated from the two or more high current paths 111A and 112A.

[0073] On the other hand, the sensing transformer 120A may be configured such that the second magnetic flux density induced by the second currents I21 and I22 flowing through the two or more large current paths 111A and 112A, respectively, satisfies a predetermined magnetic flux density condition.

[0074] FIG. 4B is a diagram illustrating second magnetic flux densities B21 and B22 induced in the detection transformer 120A by the second currents I21 and I22.

[0075] As in Fig. 4A, the following description is based on the assumption that the primary side 121A and secondary side 122A of the detection transformer 120A are configured as shown in Fig. 4B. In other words, the following description is based on the assumption that the windings of two or more large current paths 111A and 112A and secondary side 122A are wound around the core 123A of the detection transformer 120A in consideration of the direction in which the magnetic flux and / or magnetic flux density is generated.

[0076] When the second current I21 is input to the large current path 111A, a magnetic flux density B21 can be induced in the core 123A. Similarly, when the second current I22 is input (or output) to the large current path 112A, a magnetic flux density B22 can be induced in the core 123A.

[0077] The detection transformer 120A may be configured such that the second magnetic flux densities B21 and B22 induced by the second currents I21 and I22 (flowing through the two or more high current paths 111A and 112A, respectively) satisfy a predetermined magnetic flux density condition, which may be a condition in which the magnetic flux densities are offset from each other as shown in FIG.

[0078] In other words, the detection transformer 120A may be configured so that the second induced current ID2 induced by the second currents I21 and I22 flowing through the two or more large current paths 111A and 112A, respectively, satisfies a predetermined second induced current condition. In this case, the predetermined second induced current condition may be a condition in which the magnitude of the second induced current ID2 is less than a predetermined critical magnitude.

[0079] In this manner, the sensing transformer 120A may be configured such that the second magnetic flux densities B21 and B22 induced by the second currents I21 and I22 cancel each other out, and only the first currents I11 and I12 are sensed.

[0080] In the detection transformer 120A, the magnitudes of first magnetic flux densities B11 and B12 induced by first currents I11 and I12 in a first frequency band (e.g., a band having a range of 150 KHz to 30 MHz) may be configured to be greater than the magnitudes of second magnetic flux densities B21 and B22 induced by second currents I21 and I22 in a second frequency band (e.g., a band having a range of 50 Hz to 60 Hz).

[0081] In the present invention, when component A is "configured" to do B, it may mean that the design parameters of component A are set to be suitable for doing B. For example, when detection transformer 120A is configured to increase the magnitude of magnetic flux induced by a current in a particular frequency band, it may mean that parameters such as the size, core diameter, number of turns, inductance magnitude, and mutual inductance magnitude of detection transformer 120A are appropriately set to increase the magnitude of magnetic flux induced by a current in a particular frequency band.

[0082] In order to supply a first induced current to the amplifier unit 130A, the secondary side 122A of the detection transformer 120A may be differentially connected to the input terminal of the amplifier unit 130A as shown in Fig. 2. Depending on the configuration of the amplifier unit 130A, the secondary side 122A of the detection transformer 120A may be disposed on a path connecting the input terminal of the amplifier unit 130A and the reference potential (reference potential 2) of the amplifier unit 130A.

[0083] Meanwhile, the above embodiment in which the detection unit 120 is realized by the detection transformer 120A is merely an example, and the concept of the present invention is not limited thereto. Therefore, any means capable of sensing only the first currents I11 and I12 input in common mode to the large current paths 111A and 112A may be used as the detection unit 120 without any limitation.

[0084] However, this is merely an example, and the concept of the present invention is not limited to this. That is, the number of windings of the large current paths 111A and 112A and the secondary side 122A wound around the core 123A may be appropriately determined according to the requirements of the system in which the current compensation device 100A is used.

[0085] According to an embodiment of the present invention, the detection transformer 120A may include a core with a through opening, which generates an output signal based on the magnetic flux density generated by the first current on the at least two or more high current paths, where the core has an openable and closable clamp structure, and in an open state, each of the at least two or more high current paths 111A and 112A may be inserted inside the core.

[0086] 5A and 5B are diagrams illustrating a sensing transformer 120A including a core 123A with an openable and closable clamp structure according to one embodiment of the present invention.

[0087] 5A, the detection unit 120 may be realized by a detection transformer 120A including a clamped core 123A. The high current paths 111A and 112A may be inserted into the openings of the detection transformer 120A as shown.

[0088] The following description is based on the assumption that the windings of the large current paths 111A and 112A and the secondary side 122A are inserted (or wound) around the core 123A of the detection transformer 120A, taking into consideration the direction in which the magnetic flux and / or magnetic flux density is generated.

[0089] When a first current I11 is input to the large current path 111A, a magnetic flux density B11 may be induced in the core 123A. Similarly, when a first current I12 is input to the large current path 112A, a magnetic flux density B12 may be induced in the core 123A. A first induced current ID1 may be induced in the winding of the secondary side 122A by the induced magnetic flux densities B11 and B12.

[0090] In this manner, the detection transformer 120A may be configured so that the first magnetic flux densities B11 and B12 induced by the first currents I11 and I12 can overlap (or reinforce each other) and generate a first induced current ID1 corresponding to the first currents I11 and I12 on the secondary side 122A that is insulated from the two or more high current paths 111A and 112A.

[0091] On the other hand, the sensing transformer 120A may be configured such that the second magnetic flux density induced by the second currents I21 and I22 flowing through the two or more large current paths 111A and 112A, respectively, satisfies a predetermined magnetic flux density condition.

[0092] FIG. 5B is a diagram illustrating second magnetic flux densities B21 and B22 induced in the detection transformer 120A by second currents I21 and I22 when the large current paths 111A and 112A are wound once around the primary side 121A of the detection transformer 120A of the present invention.

[0093] 5B, the detection unit 120 may be realized by a detection transformer 120A including a clamped core 123A. Similar to FIG. 5A, the high current paths 111A and 112A may be inserted into the openings of the detection transformer 120A as shown.

[0094] 4B, the detection transformer 120A may be configured such that the second induced current ID2 induced by the second currents I21 and I22 flowing through the two or more high current paths 111A and 112A, respectively, satisfies a predetermined second induced current condition. In this case, the predetermined second induced current condition may be a condition in which the magnitude of the second induced current ID2 is less than a predetermined critical magnitude.

[0095] In this manner, the sensing transformer 120A may be configured such that the second magnetic flux densities B21 and B22 induced by the second currents I21 and I22 cancel each other out, and only the first currents I11 and I12 are sensed. However, this is merely an example, and the concept of the present invention is not limited to this.

[0096] In the detection transformer 120A according to one embodiment of the present invention, both the high current paths 111A and 112A and the winding of the secondary side 122A may be inserted into the core 123A. In such a case, the detection transformer 120A may be configured in such a form that the high current paths 111A and 112A and the winding of the secondary side 122A simply pass through the opening of the core 123A.

[0097] According to an embodiment of the present invention disclosed in Figures 5A and 5B, the core 123A may have a clamp structure in which a portion can be opened and closed to allow the high current paths 111A and 112A to pass or be inserted into the central opening.

[0098] The clamp-type core 123A of the present invention may be configured in an open state so that the high-current paths 111A and 112A pass through the central through-hole, and the open portion of the core 123A may be closed after the high-current paths 111A and 112A are inserted. However, this is only one example, and the core 123A may be realized in various shapes that allow the high-current paths 111A and 112A to be inserted into the through-hole. For example, the core 123A may be realized in a square shape in addition to a circular shape as shown in Figures 5A and 5B.

[0099] Thus, according to one embodiment of the present invention, the high current paths 111A and 112A are configured to be simply inserted (or simply passed) through the core 123A, and the size can be dramatically reduced when compared to a detection unit 120 in which the high current paths 111A and 112A are wound several times around the core 123A.

[0100] In particular, in high power / high current systems, materials that are difficult to process, such as thick copper conductors, are used for the high current paths 111A and 112A, so by simply inserting the high current paths 111A and 112A into the core 123A, the productivity and assembly of products using the high power / high current system can be improved.

[0101] FIG. 6 is a diagram illustrating the currents IL1 and IL2 that flow through the compensation capacitor section 150A.

[0102] 6, the compensation capacitor unit 150A may be configured such that a current IL1 flowing between the two large current paths 111A and 112A through the compensation capacitor satisfies a predetermined first current condition. In this case, the predetermined first current condition may be a condition in which the magnitude of the current IL1 is less than a predetermined first critical magnitude.

[0103] The compensation capacitor section 150A may be configured so that the current Il2 flowing through the compensation capacitor between each of the two large current paths 111A and 112A and the reference potential (reference potential 1) of the current compensation device 100A satisfies a predetermined second condition. In this case, the predetermined second current condition may be a condition in which the magnitude of the current IL2 is less than a predetermined second critical magnitude.

[0104] The compensation currents IC1 and IC2 flowing in the two high current paths 111A and 112A, respectively, along the compensation capacitor portion 150A may cancel the first currents I11 and I22 on the high current paths 111A and 112A and prevent the first currents I11 and I22 from being transmitted to the second device 200A. According to one embodiment, the first currents I11 and I22 and the compensation current may be currents having the same magnitude and opposite phase to each other.

[0105] As a result, the current compensation device 100A according to one embodiment of the present invention actively compensates for the first currents I11 and I12 input in common mode to each of the two large current paths 111A and 112A connected to the first device 300A, thereby preventing malfunction or damage to the second device 200A.

[0106] Fig. 7 is a schematic diagram of an active compensation device 100A-1 according to an embodiment of the present invention. The compensation device 100A-1 shown in Fig. 7 may be an example of the compensation device 100A. The amplifier unit 130A-1 included in the compensation device 100A-1 is an example of the amplifier unit 130A of the compensation device 100A.

[0107] In the compensation device 100A-1, the amplifier 130A of the compensation device 100A is realized by an amplifier 130A-1 having a structure of a non-inverting amplifier including an Op-amp. In the amplifier 130A-1, power sources Vcc and -Vcc may be supplied from the third device 400A to the Op-amp with a reference potential 2 as a reference. R1, R2, Rf1, Cf1, Rf2, and Cf2 included in the amplifier 130A-1 are elements for adjusting the gain of the non-inverting amplifier according to the frequency. Specifically, the values ​​of R1, R2, Rf1, Cf1, Rf2, and Cf2 may be determined to meet the limit standard of conducted emissions (CE) within a first frequency band (e.g., 150 KHz to 30 MHz). For example, the values ​​of R1, R2, Rf1, Cf1, Rf2, and Cf2 may be determined so that the first currents I11 and I12 and the compensation currents IC1 and IC2 have similar magnitudes and opposite phases to each other.

[0108] For example, in the detection transformer 120A, the winding ratio between the primary side 121A and the secondary side 122A is 1:N. sen In the compensation transformer 140A, the winding ratio of the primary side 141A to the secondary side 142A is 1:N. inj Then, the values ​​of R1, R2, Rf1, Cf1, Rf2, and Cf2 are set so that the current gain of the amplifier unit 130A-1 is N sen N inj It may be designed to be.

[0109] The amplifier unit 130A-1 may include a high pass filter 401. Elements R0 and C0 included in the high pass filter 401 can block the amplifier unit 130A-1 from operating at low frequencies below a first frequency band that is the target of noise reduction. According to one embodiment, a decoupling capacitor section 170A (see FIG. 15) may be disposed on the output side of the compensation device 100A-1 (ie, on the side of the second device 200A).

[0110] Fig. 8 illustrates an active compensation device 100A-2 according to an embodiment of the present invention. The compensation device 100A-2 illustrated in Fig. 8 is an example of the compensation device 100A. The amplifier section 130A-2 of the compensation device 100A-2 is an example of the amplifier section 130A of the compensation device 100A.

[0111] In the compensation device 100A-2, the amplifier section 130A of the compensation device 100A is realized by an amplifier section 130A-2 having a push-pull amplifier structure including an npn BJT and a pnp BJT.

[0112] The input terminal of the amplifier 130A-2 is connected to the secondary side 122A via a resistor R in may be connected in parallel. Rin may adjust the input impedance of the amplifier unit 130A-2. Cb and Ce are capable of selectively coupling only AC signals.

[0113] The third device 400A provides a DC low voltage (VDC) referenced to a reference potential 2 to drive the amplifier section 130A-2. The CDC is a DC decoupling capacitor and may be connected in parallel with the third device 400A. The CDC may selectively couple only AC signals between the collectors of both the npn BJT and the pnp BJT.

[0114] In the amplifier unit 130A-2, Rnpn, Rpnp, Rbb, and Re may adjust the operating point of the BJT. Rnpn, Rpnp, Rbb, and Re may be designed according to the operating point of the BJT. Rnpn may be the collector end of the npn BJT and may connect the third device 400A end and the base end of the npn BJT. Rbb may connect the base end of the npn BJT and the base end of the pnp BJT. Rpnp may be the collector end of the pnp BJT and may connect the reference potential 2 and the base end of the pnp BJT.

[0115] On the other hand, in the detection transformer 120A, the winding ratio between the primary side 121A and the secondary side 122A is 1:N. senIn the compensation transformer 140A, the winding ratio of the primary side 141A to the secondary side 142A is 1:N. inj Then, the current gain of the amplifier 130A-2 is N sen N inj It may be designed so that

[0116] Meanwhile, the current flowing from the collector to the emitter of the BJT changes depending on the voltage applied between the base and emitter. When the input voltage of the noise-based amplifier 130A-2 is a positive swing greater than 0, an npn BJT can operate. The operating current at this time may flow through the first path 501. When the input voltage of the noise-based amplifier 130A-2 is a negative swing less than 0, a pnp BJT can operate. The operating current at this time may flow through the second path 502.

[0117] On the other hand, the transconductance of a BJT element (the ratio of the output current to the input voltage of the BJT) is g m、BJT Then, the total transconductance g of the amplifier unit 130A-2 is m、BJT can be expressed as in Equation 1. JPEG2025016641000002.jpg18170

[0118] In Equation 1, Iout is the current flowing through the primary side 141A of the compensation transformer 140A as the output current of the amplifier unit 130A-2. sen is the potential difference between both ends of the differential input terminal of the amplifier 130A-2 as the input voltage of the amplifier 130A-2, that is, the voltage induced on the secondary side 122A of the detection transformer 120A. m、BJT As mentioned above, represents the transconductance (the ratio of output current to input voltage) that a BJT has by itself without a feedback loop.

[0119] Therefore, the current gain A of the amplifier 130A-2 i、amp can be expressed as in Equation 2. JPEG2025016641000003.jpg19170

[0120] In formula 2, I sen is the current induced in the secondary side 122A by the sensing transformer 120A as the input current of the amplifier 130A-2. out is a current flowing through primary side 141A of compensation transformer 140A as an output current of amplifier 130A-2.

[0121] From this, the current gain of the amplifier unit 130A-2 can be approximated as shown in Equation 3. JPEG2025016641000004.jpg18170

[0122] On the other hand, as described above, the current gain A i、amp is N sen N inj By designing the compensation currents IC1 and IC2 to be equal in magnitude to the first currents I11 and I12, the compensation currents IC1 and IC2 may cancel out the first currents I11 and I12.

[0123] JPEG2025016641000005.jpg20170

[0124] According to one embodiment, a decoupling capacitor section 170A (see FIG. 15) may be optionally disposed on the output side of the compensation device 100A-2 (ie, on the side of the second device 200A).

[0125] 9A is a schematic diagram of a compensation device 100A-3 according to an embodiment of the present invention. The compensation device 100A-3 is an example of the current compensation device 100A, and the amplifier unit 130A-3 may be an example of the amplifier unit 130A.

[0126] In the compensation device 100A-3, the amplifier section 130A of the compensation device 100A is realized by an amplifier section 130A-3 having a push-pull amplifier structure including an npn BJT and a pnp BJT. Only AC signals can be selectively coupled to Cb and Ce of amplifier 130A-3.

[0127] The third device 400A generates a DC low voltage V DC Supply. C DC is the above V DC , which may be connected in parallel with the third device 400A. DC may selectively couple only an AC signal between the collectors of both the npn BJT and the pnp BJT.

[0128] In the amplifier section 130A-3, Rnpn, Rpnp, Rbb, and Re may adjust the operating point of the BJT. Rnpn may be the collector terminal of the npn BJT and may connect the third device 400A terminal and the base terminal of the npn BJT. Rbb may connect the base terminal of the npn BJT and the base terminal of the pnp BJT. Rpnp may be the collector terminal of the pnp BJT and may connect the reference potential 2 and the base terminal of the pnp BJT.

[0129] Meanwhile, in one embodiment, the secondary side 122A of the detection transformer 120A may be connected to the base and emitter terminals of both BJTs, and the primary side 141A of the compensation transformer 140A may be connected to the collector and base of both BJTs. The amplifier unit 130A-3 may have a recurrent structure that reinjects the output current into the base of the BJT. Due to the recurrent structure, the amplifier unit 130A-3 can stably obtain a constant current gain for the operation of the compensation device 100A-3.

[0130] When the input voltage of the noise-induced amplifier 130A-3 is a positive swing greater than 0, the npn BJT can operate. The operating current at this time may flow through the first path 601. When the input voltage of the noise-induced amplifier 130A-3 is a negative swing less than 0, the pnp BJT can operate. The operating current at this time may flow through the second path 602.

[0131] FIG. 9B is a simplified diagram of the amplifier of FIG. 9A. Referring to FIG. 9B, an induced current I generated on the secondary side 122A of the detection transformer 120A i (or I sen ) may be the first induced current input to the amplifier 130A-3, or an output signal including the first induced current. OBJT (or I out、BJT ) is the I passing through the primary side 141A of the compensation transformer 140A. OBJT may be the amplified current or amplified signal output from the amplifier 130A-3.

[0132] JPEG2025016641000006.jpg25170

[0133] JPEG2025016641000007.jpg21170JPEG2025016641000008.jpg18170

[0134] Therefore, the current gain A of the amplifier 130A-3 i、amp can be expressed as in Equation 6. JPEG2025016641000009.jpg18170

[0135] JPEG2025016641000010.jpg20170

[0136] Unlike the amplifier section 130A-2 of the compensation device 100A-2, the amplifier section 130A-3 of the compensation device 100A-3 has an R in does not exist, and the compensating output current I out、BJTTherefore, the amplifying unit 130A-3 is not limited in current gain, but can obtain a more stable current gain than the amplifying unit 130A-2.

[0137] According to an embodiment, a decoupling capacitor section 170A (see FIG. 15) may be disposed on the output side (ie, on the second device 200A side) of the compensation device 100A-3.

[0138] 10A and 10B are diagrams illustrating an amplifier unit 130A-4 of a compensation device 100A-4 according to an embodiment of the present invention.

[0139] Referring to FIG. 10A, an amplifier unit 130A-4 according to an embodiment of the present invention may include at least one impedance Z1 and Z2 that adjusts the amplification ratio of an amplifying element.

[0140] For example, the amplifier 130A-4 may include an npn-type BJT, a pnp-type BJT, a capacitor Ce at the emitter end of each BJT, a capacitor Cb at the base end of each BJT, resistors Rnpn and Rpnp at the collector end of each BJT, resistors Re at the emitter ends of the two BJTs, and resistors Rbb at the base ends of the two BJTs. A first end of the capacitor Ce at the emitter end of each of the two BJTs may be connected to the secondary side 122A of the detection transformer 120A, and a second end may be connected to the emitter end of each BJT. Resistors Rnpn and Rpnp at the collector ends of the BJTs, resistors Re at the emitter ends of the two BJTs, and resistors Rbb at the base ends of the two BJTs may each be configured to design the DC operating points of the BJTs.

[0141] 10A may include at least one impedance Z1 and Z2 that adjusts the amplification ratio of the amplifying element. The first impedance Z1 and the second impedance Z2 may be realized by using one or more resistors R, capacitors C, or inductors L in combination.

[0142] For example, the first impedance Z1 and the second impedance Z2 may be realized in RC series or RLC series, respectively, and may be designed to more finely compensate the phase and magnitude of the current compensation according to frequency.

[0143] A first end of the first impedance Z1 may be connected to the primary side 141A of the compensation transformer 140A, and a second end may be connected to the emitter ends of the two BJTs. Also, a first end of the second impedance may be connected to the primary side 141A of the compensation transformer 140A, and a second end may be connected to a capacitor Cb at the base end of each of the BJTs.

[0144] Amplification factor A of the amplifier 130A-4 according to another embodiment of the present invention i、amp may be adjusted according to the value of at least one of the impedances Z1 and Z2 described above. For example, if the first impedance Z1 is R1 and the second impedance Z2 is (n-1)R1, the amplification degree A i、amp can be designed as -n (n>1). In this case, the design value of n can be tuned taking into account the characteristic error of the element.

[0145] FIG. 10B is a simplified diagram of the amplifier of FIG. 10A. Referring to FIG. 10B, a first induced current I generated on the secondary side 122A of the detection transformer 120A is i may be an input current input to the amplifier 130A-4. Also, the amplified current I passing through the primary side 141A of the compensation transformer 140A may be OBJT may be the output current output from the amplifier 130A. Amplification degree A of the amplifier 130A i、amp can be expressed as in Equation 7. JPEG2025016641000011.jpg31170

[0146] As shown in Equation 7, the amplifier of the present invention has a current amplification factor A i、amp =-n (n>1). In the above example, the amplification factor A i、amp N sen *N inj By setting Z1 and Z2 above while taking the error into consideration, the current amplification degree can be accurately tuned.

[0147] In particular, when the current compensation device includes a detection unit 120A having a clamp structure as described in Figures 5A and 5B, the detection gain of the first current is not large, so that the reduction in gain due to the detection unit 120A can be compensated for by appropriately adjusting at least one of the impedances Z1 and Z2.

[0148] 11 is a diagram showing a schematic configuration of a compensation device 100B according to another embodiment of the present invention. In the following, a description of the contents that overlap with the contents of the drawings described above will be omitted.

[0149] The compensation device 100B according to another embodiment of the present invention may actively compensate for the first currents I11, I12, and I13 input in common mode to the high current paths 111B, 112B, and 113B connected to the first device 300B, respectively.

[0150] Therefore, a compensation device 100B according to another embodiment of the present invention may include three large current paths 111B, 112B, and 113B, a detection transformer 120B, an amplifier section 130B, a compensation transformer 140B, and a compensation capacitor section 150B.

[0151] In comparison with the compensation device according to the above-mentioned embodiment, the compensation device 100B includes three large current paths 111B, 112B, and 113B, which causes a difference between the detection transformer 120B and the compensation capacitor unit 150B. Therefore, the following description of the compensation device 100B will focus on the above-mentioned differences.

[0152] A compensation device 100B according to another embodiment of the present invention may include first, second, and third high current paths 111B, 112B, and 113B that are distinct from one another. According to one embodiment, the first high current path 111B may be an R-phase power line, the second high current path 112B may be an S-phase power line, and the third high current path 113B may be a T-phase power line. The first currents I11, I12, and I13 may be input in a common mode to the first high current path 111B, the second high current path 112B, and the third high current path 113B, respectively.

[0153] According to one embodiment, the primary side 121B of the sensing transformer 120B may be disposed on each of the first, second and third high current paths 111B, 112B and 113B to generate induced currents on the secondary side 122B. The magnetic flux densities generated in the sensing transformer 120B by the first currents I11, I12 and I13 on the three high current paths 111B, 112B and 113B may reinforce each other.

[0154] On the other hand, when the compensation device 100B includes three high current paths 111B, 112B, and 113B, the use of a clamp-type detection unit such as that shown in Figures 5A and 5B can maximize the effect of reducing the size of the detection unit and the size of the compensation device 100B.

[0155] Meanwhile, the compensation capacitor section 150B can provide paths through which the compensation currents IC1, IC2, and IC3 generated by the compensation transformer flow to the first large current path 111B, the second large current path 112B, and the third large current path 113B, respectively.

[0156] The active current compensation device 100B according to such an embodiment may be used to compensate (or cancel) first currents I11, I12, and I13 that occur in a common mode on three high current paths of a three-phase, three-wire power system.

[0157] 12 is a diagram showing a schematic configuration of a compensation device 100C according to still another embodiment of the present invention. In the following, a description of the contents that overlap with the contents of the above-mentioned drawings will be omitted.

[0158] The compensation device 100C may actively compensate for the first currents I11, I12, I13, and I14 input in common mode to the large current paths 111C, 112C, 113C, and 114C connected to the first device 300C, respectively.

[0159] Therefore, the compensation device 100C according to one embodiment of the present invention may include four large current paths 111C, 112C, 113C, and 114C, a detection transformer 120C, an amplifier section 130C, a compensation transformer 140C, and a compensation capacitor section 150C.

[0160] In comparison with the compensation device according to the above-mentioned embodiment, the compensation device 100C includes four large current paths 111C, 112C, 113C, and 114C, which causes differences between the detection transformer 120C and the compensation capacitor unit 150C. Therefore, the following description of the compensation device 100C will focus on the above-mentioned differences.

[0161] The compensation device 100C according to an embodiment may include first, second, third, and fourth high current paths 111C, 112C, 113C, and 114C that are distinct from one another. According to an embodiment, the first high current path 111C may be an R-phase power line, the second high current path 112C may be an S-phase power line, the third high current path 113C may be a T-phase power line, and the fourth high current path 114C may be an N-phase power line. The first currents I11, I12, I13, and I14 may be input in a common mode to the first high current path 111C, the second high current path 112C, the third high current path 113C, and the fourth high current path 114C, respectively.

[0162] According to one embodiment, the primary side 121C of the sensing transformer 120C may be disposed on each of the first, second, third, and fourth high current paths 111C, 112C, 113C, and 114C to generate induced currents on the secondary side 122C. The magnetic flux densities generated in the sensing transformer 120C by the first currents I11, I12, I13, and I14 on the four high current paths 111C, 112C, 113C, and 114C may reinforce each other.

[0163] On the other hand, when the compensation device 100C includes four high current paths 111C, 112C, 113C, and 114C, the effect of reducing the size of the detection unit and the size of the compensation device 100C can be maximized by using a clamp-type detection unit as shown in Figures 5A and 5B.

[0164] On the other hand, the compensation capacitor section 150C can provide paths through which the compensation currents IC1, IC2, IC3, and IC4 generated by the compensation transformer flow to the first high current path 111C, the second high current path 112C, the third high current path 113C, and the fourth high current path 114C, respectively.

[0165] The compensation device 100C according to such an embodiment may be used to compensate (or cancel) first currents I11, I12, I13, and I14 that are generated in common mode on four high current paths of a three-phase, four-wire power system.

[0166] FIG. 13 is a diagram illustrating a schematic configuration of a system in which the compensation device 100B according to the embodiment shown in FIG. 11 is used, according to an embodiment of the present invention.

[0167] The compensation device 100B according to the embodiment may be used together with one or more other compensation devices 500 on the high current path connecting the secondary device 200B and the primary device 300B.

[0168] For example, the compensation device 100B according to the embodiment may be used together with a first compensation device 510 that compensates for a first current input in a common mode. In this case, the first compensation device 510 may be realized by active elements like the compensation device 100B, or may be realized by only passive elements.

[0169] Furthermore, the compensation device 100B according to the embodiment may be used together with a second compensation device 520 that compensates for a third current input in a differential mode. In this case, the second compensation device 520 may also be realized with active elements, or may be realized only with passive elements.

[0170] Furthermore, the compensation device 100B according to the embodiment may be used together with an n-th compensation device 530 that compensates for a voltage. In this case, the n-th compensation device 530 may also be realized with active elements, or may be realized only with passive elements.

[0171] Meanwhile, the types, numbers, and arrangement order of the compensation devices 500 described in Fig. 13 are merely examples, and the concept of the present invention is not limited thereto. Therefore, various numbers and types of compensation devices may be included in the system depending on the design of the system. In addition, it goes without saying that the embodiment shown in Fig. 13 may be selectively applied to all other embodiments in this specification as well.

[0172] Fig. 14 is a schematic diagram showing a system configuration including an active compensation device 101 according to an embodiment of the invention. Referring to Fig. 14, the compensation device 101 may further include a decoupling capacitor section 170 in addition to the compensation device shown in Fig. 1. Detailed descriptions of components that overlap with the above-described embodiment will be omitted.

[0173] The decoupling capacitor section 170 may be a means for making the output impedance from the compensation section 160 to the second device 200 satisfy a predetermined condition. In other words, the decoupling capacitor section 170 may be a means for making the compensation current output to the second device 200 along at least two or more large current paths 111 and 112, and preventing the compensation current from returning to the compensation device 101.

[0174] For example, the compensation device 101 can improve the compensation effect of the first current input in the common mode when the output impedance from the compensation unit 160 satisfies the condition that the output impedance from the compensation unit 160 is equal to or lower than the impedance of the compensation unit 160 itself. According to the above embodiment, it is possible to satisfy the condition that the amount of at least a part of the compensation current flowing to the second device 200 side is greater than the amount of at least a part of the compensation current flowing to the inside of the compensation device 101 along each of the two or more large current paths 111 and 112.

[0175] The impedance of the second device 200 may be changed arbitrarily depending on the surrounding conditions of the power system and the filter. For example, a home appliance may have various impedance values ​​depending on its components (e.g., electric motors, electric heaters, light-emitting elements, etc.).

[0176] The decoupling capacitor section 170 prevents the output performance of the compensation current of the compensation device 101 from fluctuating significantly according to changes in the impedance value of the second device 200, making it applicable to various systems.

[0177] The compensation devices 100 and 101 according to an embodiment may be a feedforward type compensation filter that compensates for noise input from the first device 300 at the front end of the power supply side. However, the present invention is not limited thereto, and as illustrated in Figs. 23 and 47, the present invention may also include a compensation device of a type that compensates for noise detected at the front end of the power supply side at the rear end.

[0178] Fig. 15 is a schematic diagram of a specific example of the compensation device 101 according to the embodiment shown in Fig. 14. Referring to Fig. 15, the compensation device 101A may further include a decoupling capacitor section 170A in addition to the compensation device 100A shown in Fig. 3.

[0179] The decoupling capacitor section 170A may be a means for making the output impedance from the compensation section 160A to the second device 200A satisfy a predetermined condition.

[0180] Impedance Zn on the first device 300A side and / or impedance Z on the second device 200A side line may be arbitrarily changed according to the surrounding conditions of the power system and the filter. The decoupling capacitor section 170A may prevent the output performance of the compensation current of the compensation device 101A from fluctuating greatly according to the change in the impedance value of the second device 200A.

[0181] Such a decoupling capacitor section 170A may include at least two or more capacitors arranged on paths branched off from at least two or more high current paths 111A and 112A connecting the second device 200A and the compensation capacitor section 150A.

[0182] 15, one end of each of the two capacitors included in the decoupling capacitor unit 170A may be connected to a reference potential (reference potential 1) of the compensation device 101A, and the opposite ends of each of the two capacitors may be connected to the first large current path 111A and the second large current path 112A, respectively. According to an embodiment, the decoupling capacitor unit 170A may be connected to the power supply side (i.e., the second device 200A side) of the compensation device 101A, but is not limited thereto.

[0183] Impedance Z of decoupling capacitor section 170A Y may be designed to have a sufficiently small value in the first frequency band to be subjected to noise reduction. For example, the impedance Z Ycan satisfy Equation 8. JPEG2025016641000012.jpg19170

[0184] Referring to Equation 8, the impedance Z seen from the compensation device 101A to the second device 200A side is line ||Z Y The decoupling capacitor section 170A can be used to line Regardless of the value, the designed Z Y For example, the impedance Z of the decoupling capacitor section 170A can be Y may be designed to have a value less than a specified value within a specified frequency band (e.g., a first frequency band). Y has a sufficiently small value in the first frequency band that is the target of noise reduction, the current compensation device 101A reduces the impedance Z line Regardless, it may still operate normally.

[0185] By incorporating decoupling capacitor section 170A, compensation device 101A can also be used as a stand-alone module in some systems.

[0186] Meanwhile, the sensing unit 120 according to an embodiment of the present invention may include a general sensing transformer 120A or the clamp structure described in FIGS. 5A and 5B.

[0187] According to one embodiment, the detection unit 120 does not need to have a large impedance since it is intended to detect the noise first currents I11 and I12. The detection transformer 120A or the clamp structure can have an impedance that is one thousandth to one hundredth of the impedance of the passive filter (e.g., CM choke). Therefore, the size of the detection transformer 120A can be much smaller than the size of the CM choke.

[0188] Meanwhile, it goes without saying that the amplifier units 130 and 130A of the compensation devices 101 and 101A may include the amplifier units 130A-1, 130A-2, 130A-3, and 130A-4 according to the various embodiments described above.

[0189] 16 is a diagram showing a schematic configuration of a compensation device 101C according to an embodiment of the present invention. In the following, contents that overlap with the explanation of the drawings described above will be omitted.

[0190] The compensation device 101C shown in FIG. 16 may further include a decoupling capacitor section 170C on the output side (i.e., on the second device 200C side) of the compensation device 100B shown in FIG.

[0191] The decoupling capacitor section 170C may include three capacitors. One end of each of the three capacitors may be connected to the first large current path 111C, the second large current path 112C, and the third large current path 113C, respectively. The opposite ends of the three capacitors may be connected to a reference potential (reference potential 1) of the current compensation device 100C.

[0192] The impedance Z of the decoupling capacitor section 170C Y may be designed to have a value smaller than a value specified in the first frequency band targeted for noise reduction. Due to the incorporation of the decoupling capacitor section 170C, the current compensation device 100C may be used as an independent module even in some systems (e.g., three-phase three-wire systems).

[0193] Although not shown, it goes without saying that a decoupling capacitor section including four capacitors may also be coupled in a three-phase four-wire system as shown in Fig. 12. As an example, in a three-phase four-wire system, a decoupling capacitor section including four capacitors may be disposed between the compensation capacitor section and the second device, but is not limited to this.

[0194] Fig. 17 shows a schematic configuration of a system including a compensation device 102 according to an embodiment of the present invention. The current compensation device 102 may be the compensation device 100 shown in Fig. 1 to which only the disturbance protection unit 13 has been added. All of the compensation devices according to the above-mentioned embodiments may be applied to the compensation device 102. Therefore, the following description will focus on the differences due to the disturbance protection unit 13.

[0195] 17, the compensation device 102 may further include a disturbance protection unit 13 in addition to the detection unit 120, the amplification unit 130, and the compensation unit 160 as described above.

[0196] The disturbance protection unit 13 can protect the amplifier unit 130 from disturbances. For example, an active element included in the amplifier unit 130 can be protected by the disturbance protection unit 13.

[0197] The compensation device 102 may be implemented in an electric device, but generally, the condition in which the electric device operates may not be stable. That is, an interference signal such as an overvoltage or overcurrent may enter the compensation device 102 from the outside through the high-current paths 111 and 112. For example, a pulse voltage of several kV may occur in at least one of the high-current paths 111 and 112 due to lightning or a lightning surge. The above-mentioned overvoltage / overcurrent may be transmitted to the amplifier 130 through the detection unit 120 or the compensation unit 160. The amplifier 130 may include various types of active elements, is vulnerable to external interference, and may malfunction or fail due to the overvoltage / overcurrent.

[0198] In various embodiments of the present invention, the compensation device 102 has a structure that insulates the amplifier unit 130 from the large current paths 111 and 112, thereby providing primary protection for the amplifier unit 130 from the above-mentioned disturbances.

[0199] For more reliable protection from disturbances, the compensation device 102 may include a disturbance protection unit 13. In one embodiment, when a voltage equal to or greater than a predetermined critical voltage is applied to at least one of an input terminal of the amplifier unit 130 to which the detection unit 120 and the amplifier unit 130 are connected and an output terminal of the amplifier unit 130 to which the detection unit 120 and the compensation unit 160 are connected, the disturbance protection unit 13 may limit the applied voltage to a voltage equal to or less than the critical voltage. For example, the disturbance protection unit 13 may include a first disturbance protection unit 11 for blocking an overvoltage transmitted to the amplifier unit 130 through the detection unit 120, and a second disturbance protection unit 12 for blocking an overvoltage transmitted to the amplifier unit 130 through the compensation unit 160.

[0200] According to an embodiment, the first disturbance protection unit 11 may be differentially connected to an input terminal of the amplifier unit 130. The first disturbance protection unit 11 may be connected in parallel to an output terminal of the detector unit 120. The second disturbance protection unit 12 may be connected in parallel to an input terminal of the compensation unit 160. The first disturbance protection unit 11 and the second disturbance protection unit 12 may be isolated from the high current paths 111 and 112 .

[0201] According to an embodiment, the first disturbance protection unit 11 may have a first impedance when a voltage less than a predetermined critical voltage is applied to the input end of the amplifier unit 130, and may have a second impedance lower than the first impedance when a voltage equal to or greater than the predetermined critical voltage is applied to the input end of the amplifier unit 130. The first impedance may be a very large value, for example, a value close to infinity. Similarly, the second disturbance protection unit 12 may have a first impedance when a voltage less than a predetermined critical voltage is applied to the output end of the amplifier unit 130, and may have a second impedance lower than the first impedance when a voltage equal to or greater than the predetermined critical voltage is applied to the output end of the amplifier unit 130.

[0202] According to one embodiment, the disturbance protection unit 13 does not pass current through the disturbance protection unit 13 when the voltage across the disturbance protection unit 13 is less than a specified voltage, but when an external overvoltage causes the voltage across the disturbance protection unit 13 to exceed the specified voltage, the disturbance protection unit 13 can protect the amplifier unit 130 from transmitting an overvoltage by passing current (in parallel).

[0203] Fig. 18 shows a schematic diagram of a compensation device 102A according to an embodiment of the present invention. The current compensation device 102A may be obtained by adding only the first and second disturbance protection elements 11A and 12A as an example of the disturbance protection unit 13 to the compensation device 100A shown in Fig. 2. All of the various compensation devices or amplifier units according to the above-mentioned embodiments can be applied to the compensation device 102A. The following description will focus on the differences due to the first and second disturbance protection elements 11A and 12A.

[0204] Referring to FIG. 18, the compensation device 102A may include first and second disturbance protection elements 11A and 12A in addition to a detection transformer 120A, an amplifier section 130A, and a compensation section 160A (e.g., a compensation transformer 140A and a compensation capacitor section 150A).

[0205] The first disturbance protection element 11A and the second disturbance protection element 12A may be one example of the first disturbance protection section 11 and the second disturbance protection section 12 described above.

[0206] The first disturbance protection element 11A and the second disturbance protection element 12A may include a TVS (Transient Voltage Suppression) diode element, but are not limited to this.

[0207] For example, an external overvoltage S such as a lightning surge may occur in at least one of the high current paths 111A and 112A. For example, as shown in FIG. 18, when an external overvoltage S occurs in the second high current path 112A, it may be transmitted in the form of magnetic energy to the amplifier unit 130A through the first transmission path P1 or the second transmission path P2. The first transmission path P1 is a path through the detection transformer 120A, and the second transmission path P2 is a path through the compensation transformer 140A. The active elements of the amplifier unit 130A are susceptible to external disturbances and therefore require a protection device.

[0208] The first disturbance protection element 11A may be connected in parallel to the secondary side 122A of the detection transformer 120A to protect the amplifier unit 130A from an overvoltage transmitted to the first transmission path P1. The second disturbance protection element 12A may be connected in parallel to the primary side 141A of the compensation transformer 140A to protect the amplifier unit 130A from an overvoltage transmitted to the second transmission path P2.

[0209] The first and second disturbance protection elements 11A and 12A may include, for example, TVS diode elements. In this case, in order to minimize the performance reduction of the amplifier unit 130A due to the TVS diode elements, a TVS diode element having a sufficiently low diode junction capacitance (for example, a specified value or less) may be used. For example, the junction capacitance of the TVS diode may be several hundred pF or less. Even if the TVS diodes of the first and second disturbance protection elements 11A and 12A have a low junction capacitance, their durability can be ensured by the insulating structure.

[0210] The first and second disturbance protection elements 11A and 12A (e.g., TVS diodes) may have a breakdown voltage. For example, when the voltage applied to the first disturbance protection element 11A is less than the breakdown voltage, no current may flow through the first disturbance protection element 11A. However, when a voltage equal to or greater than the breakdown voltage is applied across the first disturbance protection element 11A due to an external overvoltage S, the impedance of the first disturbance protection element 11A becomes low, and a current may flow through the first disturbance protection element 11A. The second disturbance protection element 12A may also operate in the same manner as the first disturbance protection element 11A.

[0211] When a voltage equal to or greater than a predetermined critical voltage (e.g., a breakdown voltage) is applied to at least one of the input terminal and the output terminal of the amplifier unit 130A, the first and second disturbance protection elements 11A and 12A may consume at least a portion of the power due to the voltage equal to or greater than the predetermined critical voltage. At least a remaining portion of the power due to the voltage equal to or greater than the predetermined critical voltage may be consumed by the remaining elements (e.g., elements included in the amplifier unit 130A).

[0212] According to one embodiment, due to the isolated structure and the combination of the first and second disturbance protection elements 11A and 12A, the compensation device 102A can be used as an independent module in any system.

[0213] Fig. 19 illustrates a schematic diagram of a compensation device 102A-1 according to an embodiment of the present invention. The compensation device 102A-1 is an example of the compensation device 102A illustrated in Fig. 18, and the amplifier unit 130A-3 is an example of the amplifier unit 130A of the compensation device 102A.

[0214] On the other hand, the compensation device 102A-1 may be obtained by adding only the first and second disturbance protection elements 11A and 12A to the amplifier section 130A-3 described with reference to the compensation device 100A-3 shown in Fig. 9A. Therefore, the description will be omitted for the sake of brevity, and the differences due to the first and second disturbance protection elements 11A and 12A will be mainly described.

[0215] The amplifier 130A-3 may include a first amplifier element for amplifying a positive signal and a second amplifier element for amplifying a negative signal. For example, the amplifier 130A-3 may be realized by a push-pull amplifier using amplifier elements including an npn BJT and a pnp BJT.

[0216] The amplifier 130A-3 of the compensation device 102A-1 may have a feedback structure that feeds back the output current to be compensated to the input terminal again. The amplifier 130A-3 is limited in current gain, but can obtain a stable current gain.

[0217] The compensation device 102A-1 may include a first disturbance protection element 11A connected in parallel to the secondary side 122A of the detection transformer 120A to protect the amplifier unit 130A-3 from an overvoltage transmitted through the detection transformer 120A. Also, a second disturbance protection element 12A may be connected in parallel to the primary side 141A of the compensation transformer 140A to protect the amplifier unit 11A-1 from an overvoltage transmitted through the compensation transformer 140A.

[0218] The first and second disturbance protection elements 11A and 12A may be realized, for example, by TVS diode elements having a junction capacitance equal to or less than a specified value (for example, equal to or less than several hundred pF).

[0219] The first and second disturbance protection elements 11A and 12A (for example, TVS diodes) may have a breakdown voltage, and the breakdown voltage may be designed according to the operating voltage of the amplifier section 130A-3.

[0220] Fig. 20 illustrates a schematic diagram of a compensation device 102A-2 according to an embodiment of the present invention. The compensation device 102A-2 is an example of the compensation device 102A illustrated in Fig. 18, and the amplifier unit 130A-4 is an example of the amplifier unit 130A of the compensation device 102A.

[0221] On the other hand, the compensation device 102A-2 may be obtained by adding only the first and second disturbance protection elements 11A and 12A to the amplifier section 130A-4 described with reference to the compensation device 100A-4 shown in Fig. 10A. Therefore, the description overlapping with the compensation device 100A-4 in Fig. 10A will be omitted, and the description will focus on the differences due to the first and second disturbance protection elements 11A and 12A.

[0222] In one embodiment of the present invention, the amplifying section 130A-4 may further include at least one impedance Z1 and Z2 that adjusts the amplification ratio of the first amplifying element and the second amplifying element, in addition to the first amplifying element and the second amplifying element described above.

[0223] Similar to the current compensation device 102A-1, the compensation device 102A-2 may also include a first disturbance protection element 131A connected in parallel to the secondary side 122A of the detection transformer 120A in order to protect the amplifier unit 130A-4. Also, a second disturbance protection element 132A may be connected in parallel to the primary side 141A of the compensation transformer 140A in order to protect the amplifier unit 131A-2 from an overvoltage transmitted through the compensation transformer 140A.

[0224] FIG. 21 is a diagram illustrating a schematic configuration of a compensation device 102B according to an embodiment. Compensation device 102B can be said to be an embodiment of compensation device 102A shown in FIG. 18 further including a decoupling capacitor section 170B.

[0225] Alternatively, it can be said that the compensation device 120B is an embodiment in which the compensation device 101A shown in FIG. 15 further includes first and second disturbance protection elements 11A and 12A.

[0226] Alternatively, the compensation device 120B can be said to be an embodiment in which the compensation device 100A shown in Fig. 6 further includes a decoupling capacitor section 170B and first and second disturbance protection elements 11A and 12A. Therefore, a duplicated description will be omitted.

[0227] In order for the active compensation device 102B to maintain stable performance, it is sufficient that the impedance on the output side of the compensation device 102B (i.e., the second device 200A side) is sufficiently smaller than the impedance Zn on the first device 300A side (i.e., the noise source side).

[0228] The decoupling capacitor section 170B prevents the compensation current output performance of the compensation device 102B from varying significantly with changes in the impedance value of the second device 200A, allowing the compensation device to function in a variety of systems.

[0229] According to one embodiment, due to the combination of the isolated structure, the first and second disturbance protection elements 11A and 12A, and the decoupling capacitor section 170B, the compensation device 102B can be used as an independent module in any system.

[0230] FIG. 22 is a diagram illustrating a schematic configuration of a compensation device 102C according to another embodiment of the present invention. It can be said that the compensation device 102C is an embodiment in which the compensation device 101C shown in FIG. 16 further includes first and second disturbance protection elements 11C and 12C.

[0231] Also, the compensation device 102C can be said to be an embodiment in which the compensation device 100B shown in Fig. 11 further includes a decoupling capacitor section 170C and first and second disturbance protection elements 11C and 12C. Therefore, a duplicated description will be omitted.

[0232] Referring to FIG. 22, the compensation device 102C may compensate (or cancel) first currents I11, I12, and I13 that occur in a common mode on a high current path of a three-phase, three-wire power system.

[0233] The compensation device 102C may include three high current paths 111C, 112C, 113C, a detection transformer 120C, an amplifier section 130C, a compensation transformer 140C, a compensation capacitor section 150C, a first disturbance protection element 11A, a second disturbance protection element 12A, and a decoupling capacitor section 170C.

[0234] According to one embodiment, the first high current path 111C may be an R-phase power line, the second high current path 112C may be an S-phase power line, and the third high current path 113C may be a T-phase power line.

[0235] The primary side 121C of the sensing transformer 120C may be disposed in each of the first large current path 111C, the second large current path 112C, and the third large current path 113C to generate an induced current in the secondary side 122C.

[0236] The compensation capacitor unit 150C can provide paths through which the compensation currents IC1, IC2, and IC3 generated by the compensation transformer flow to the first, second, and third large current paths 111C, 112C, and 113C, respectively.

[0237] The compensation device 102C may include a decoupling capacitor section 170C including three Y-capacitors (Y-caps). One end of each of the three Y-caps may be connected to the first, second, and third high current paths 111C, 112C, and 113C, respectively. The opposite ends of the three Y-caps may be connected to a reference potential (reference potential 1) of the compensation device 102C.

[0238] The first disturbance protection element 11C may be connected in parallel to the secondary side 122C of the sensing transformer 120A. The second disturbance protection element 12C may be connected in parallel to the primary side 141C of the compensation transformer 140C.

[0239] On the other hand, although not shown, the compensator 102C including the decoupling capacitor unit 170C and the disturbance protection elements 11C and 12C may be modified to suit a three-phase, four-wire power system (see FIG. 12). The description of the compensator for the three-phase, four-wire power system may correspond to the content described with reference to FIG.

[0240] Fig. 23 is a diagram showing a schematic configuration of a compensation device 102D according to another embodiment of the present invention. At least a part of the compensation devices according to the various embodiments described above may be applied to the compensation device 102D. Also, a description of the contents that overlap with the contents described with reference to Figs. 17 to 22 will be omitted.

[0241] 23, the compensation device 102D may be a feedback type CSCC compensation device 102D that senses a common mode noise current drawn from the second device 200A side (e.g., power supply side) and compensates with a current from the first device 300A side (e.g., noise source side). That is, in the compensation device 102D, the detection transformer 120D may be disposed on the second device 200A side, and the compensation capacitor section 150D may be disposed on the first device 300A side.

[0242] FIG. 24 is a diagram illustrating a schematic configuration of a system including a compensation device 103 according to an embodiment of the present invention.

[0243] The compensation device 103 according to one embodiment of the present invention can be said to be an embodiment in which only a malfunction detection unit 60 and a connection circuit for connecting the malfunction detection unit 60 to other components are added to the compensation device 100 shown in Fig. 2. Therefore, descriptions that overlap with the compensation device according to the above embodiment will be omitted, and the description will focus on the malfunction detection unit 60, which is the difference.

[0244] According to an embodiment, the two or more high current paths 111 and 112 may be electrically connected to the malfunction detection unit 60. In this case, the malfunction detection unit 60 may check the states of the two or more high current paths 111 and 112 and generate a signal corresponding thereto. For example, the malfunction detection unit 60 may check the voltages of the two or more high current paths 111 and 112 and / or the line voltages of the two or more high current paths 111 and 112 and generate a signal indicating whether the high current paths 111 and 112 are normal or not based on the voltages.

[0245] According to an embodiment, the detection unit 120 may be electrically connected to the malfunction detection unit 60. The malfunction detection unit 60 may check the operating state of the detection unit 120 and generate a signal corresponding thereto. For example, in an example in which the detection unit 120 is realized as a detection transformer, the malfunction detection unit 60 may check whether the primary side and the secondary side of the detection transformer are insulated, and based on the result, generate a signal indicating whether the detection unit 120 is normal or not.

[0246] According to an embodiment, the amplifier 130 may be electrically connected to the malfunction detector 60. The malfunction detector 60 may check the operating state of the amplifier 130 and generate a corresponding signal. A method in which the malfunction detector 60 checks for an abnormality in the amplifier 130 will be described later. The compensation transformer unit 140 may be electrically connected to the amplifier unit 130 and generate a compensation current based on the output signal amplified by the amplifier unit 130 described above.

[0247] According to an embodiment, the compensation transformer unit 140 may be electrically connected to a malfunction detector 60, which will be described later. The malfunction detector 60 may check the operating state of the compensation transformer unit 140 and generate a signal corresponding thereto. For example, in an example in which the compensation transformer unit 140 is implemented as a compensation transformer, the malfunction detector 60 may check whether the primary side and the secondary side of the compensation transformer are insulated, and based on the result, generate a signal indicating whether the compensation transformer unit 140 is normal.

[0248] The compensation capacitor unit 150 can provide a path through which the compensation current generated by the compensation transformer unit 140 flows to each of two or more large current paths.

[0249] According to an embodiment, the compensation capacitor unit 150 may be electrically connected to the malfunction detecting unit 60. The malfunction detecting unit 60 may check the operating state of the compensation capacitor unit 150 and generate a signal corresponding thereto. For example, the malfunction detecting unit 60 may check the magnitude of current flowing through each of the two or more large current paths 111 and 112 through the compensation capacitor unit 150 and generate a signal indicating whether the compensation capacitor unit 150 is normal or not based on the magnitude of current flowing through the two or more large current paths 111 and 112.

[0250] The malfunction detection unit 60 can check the operating state of at least one of the two or more high current paths 111 and 112, the detection unit 120, the amplification unit 130, the compensation transformer unit 140, and the compensation capacitor unit 150 (hereinafter referred to as the targets of check) and generate a signal corresponding to the checked operating state.

[0251] In one embodiment, the malfunction detection unit 60 may include a malfunction detection signal output unit that outputs a signal corresponding to the operational state of the object to be checked, and a malfunction detection signal display unit that displays the signal corresponding to the operational state.

[0252] In one embodiment, the malfunction detection signal output unit may output a signal in the form of a voltage corresponding to an operating state of the object to be checked based on whether or not a voltage of at least one node inside the object to be checked is within a predetermined reference voltage range. The signal (i.e., voltage) output by the malfunction detection signal output unit may be output to an external device or to a malfunction detection signal display unit. In this case, the external device may refer to various devices including the first device 300 and the second device 200 described above.

[0253] In one embodiment, the malfunction detection signal display unit may include a light emitting element that is turned on based on the signal generated by the malfunction detection signal output unit. In this case, the light emitting element may include, for example, a light emitting diode.

[0254] In another embodiment, the malfunction detection signal display unit may include a light emitting element group including at least two light emitting elements. In this case, the malfunction detection signal display unit may control on / off of at least one light emitting element of the light emitting element group based on the signal generated by the detection signal output unit. For example, the malfunction detection signal display unit may increase the number of light emitting elements that are turned on in proportion to the magnitude of the voltage generated by the malfunction detection signal output unit.

[0255] As described above, the malfunction detection unit 60 may check the operating state of the object to be checked based on at least one node voltage inside the object to be checked, or may check the operating state of the object to be checked based on at least one path current inside the object to be checked. Of course, the malfunction detection unit 60 may check the operating state of the object to be checked based on the temperature, the amount of temperature change, and the magnitude of the magnetic field and / or the electric field of the object to be checked. However, this is merely an example, and the idea of ​​the present invention is not limited thereto.

[0256] In an example including an amplifier unit 130 composed of a first amplifier element and a second amplifier element that are arranged complementarily to each other, the malfunction detection unit 60 may check the operation state of the amplifier unit 130 and generate a signal corresponding thereto. In such a case, the malfunction detection unit 60 may generate a signal corresponding to the operation state of the amplifier unit 130 based on the voltage of a central node arranged on a path that electrically connects the first amplifier element and the second amplifier element.

[0257] The malfunction detection unit 60 may output or display a signal indicating that the operating state of the amplifier unit 130 is normal when the voltage of such a central node is a value that has a predetermined relationship with the operating voltage of the amplifier unit 130 (e.g., a value corresponding to half the operating voltage).

[0258] On the other hand, in the above-mentioned content, the amplifying elements being "arranged complementarily to each other" may mean that, as shown in Figures 26B and 26C, one of the amplifying elements is arranged to amplify a positive signal, and the remaining amplifying element is arranged to amplify a negative signal.

[0259] The compensation device 103 configured as described above may sense and actively compensate for specific conditions of current on two or more high current paths 111 and 112, and may be applied to high current, high voltage, and / or high power systems despite the miniaturization of the device 103.

[0260] Meanwhile, the compensation device 103 configured as above may be realized in the form of a module including a substrate sealed in one sealing structure. Also, each component of the compensation device 103, the first device 300, the second device 200, the third device 400, the reference potential 1, the reference potential 2, and terminals connected to other external devices may be provided in the form of pins protruding in a direction perpendicular to one surface of the substrate.

[0261] For example, the terminal for outputting the signal corresponding to the operating state generated by the malfunction detection unit 60 may have the form of a pin and be provided so as to protrude from the above-mentioned module, so that the user can easily check for an abnormality in a specific configuration of the compensation device 103 by checking the voltage of the corresponding pin without disassembling the module.

[0262] In the following, the compensation device 103 according to various embodiments will be described with reference to FIGS. 25 to 27 together with FIG.

[0263] FIG. 25 is a diagram illustrating a schematic configuration of a compensation device 103A for use in a two-wire system according to one embodiment of the present invention.

[0264] The compensation device 103A may be an example of the compensation device 103 in Fig. 24, or may be the compensation device 100A in Fig. 3 to which only the malfunction detection unit 60A is added. Therefore, the description of the compensation device 103A may correspond to the description of Figs. 24 and 3.

[0265] 26A to 26C are diagrams illustrating a malfunction detecting unit 60A according to an embodiment. The following description will be given with reference to both of FIGS. 26A to 26C.

[0266] In one embodiment, the malfunction detecting unit 60A may check the operation state of the amplifier unit 130A and generate a signal corresponding to the checked operation state. To this end, the malfunction detecting unit 60A may include a malfunction detecting signal output unit 61A and a malfunction detecting signal display unit 62A as shown in Fig. 26C. The malfunction detecting signal output unit 61A may output a signal corresponding to the operation state to be checked, and the malfunction detecting signal display unit 62A may display the signal corresponding to the operation state.

[0267] In another embodiment, the malfunction detection unit 60A may include only the malfunction detection signal output unit 61A as shown in FIG. 26B.

[0268] The malfunction detection signal output unit 61A may output a signal in the form of a voltage corresponding to the operating state of the amplifying unit 130A based on whether or not the voltage of at least one node inside the amplifying unit 130A falls within a predetermined reference voltage range.

[0269] For example, as shown in FIG. 26B, when the amplifier unit 130A is composed of a first amplifier element 31A and a second amplifier element 32A arranged complementarily to each other, the malfunction detection signal output unit 61A may generate a signal corresponding to the operating state of the amplifier unit 130A based on the voltage of a central node 33A arranged on a path electrically connecting the first amplifier element 31A and the second amplifier element 32A.

[0270] For example, the malfunction detection signal output unit 61A may output a signal indicating that the operating state of the amplifier unit 130A is normal when the voltage of the central node 33A is a value corresponding to half (e.g., 6 [V]) of the operating voltage of the amplifier unit 130A (e.g., 12 [V]), that is, a value within a certain range (e.g., 4 to 8 [V]) from half the operating voltage of the amplifier unit 130A. At this time, the operating voltage of the amplifier unit 130A and the range of the value of half the operating voltage of the amplifier unit 130A may be appropriately determined according to the design of the compensation device 103A.

[0271] The signal generated by the malfunction detection signal output unit 61A may be output to an external device and / or a malfunction detection signal display unit 62A, which will be described later.

[0272] The malfunction detection signal display unit 62A can display the signal generated by the malfunction detection signal output unit 61A in a format that can be recognized by the user. Such a malfunction detection signal display unit 62A can be realized by various display means.

[0273] For example, the malfunction detection signal display unit 62A may include a light emitting element for indicating the state of the amplifier unit 130A as normal or abnormal, as shown in Fig. 26C. In this case, the light emitting element may include, for example, a light emitting diode, which can indicate normality when lit and abnormality when unlit.

[0274] In another embodiment, the malfunction detection signal display unit 62A may include a group of light-emitting elements including at least two or more light-emitting elements to more specifically display the voltage of the central node 33A of the amplifier unit 130A. The malfunction detection signal display unit 62A may control the on and off of at least one or more light-emitting elements of the light-emitting element group based on the signal generated by the detection signal output unit 61A. For example, the malfunction detection signal display unit 62A may increase the number of light-emitting elements that are turned on in proportion to the magnitude of the voltage of the central node 33A.

[0275] The light emitting element as described above does not necessarily have to be located within the compensation device 103A, but may be located outside the compensation device 103A in an appropriate location for a user to recognize, while being electrically connected to the malfunction detection signal output unit 61A. This may be similarly applied to other embodiments of the present specification.

[0276] FIG. 27 is a diagram illustrating a schematic configuration of a compensation device 103B according to another embodiment of the present invention.

[0277] It can be said that the compensation device 103B is an embodiment in which the compensation device 100B shown in Fig. 11 further includes a malfunction detection unit 60B. The description of the malfunction detection unit 60B may correspond to the description with reference to Figs. 24 to 26. Therefore, the overlapping contents will be omitted.

[0278] The compensation device 103B according to an embodiment may compensate (or cancel) first currents I11, I12, and I13 that occur in a common mode on a high current path of a three-phase, three-wire power system.

[0279] The compensation device 103B may include three large current paths 111B, 112B, 113B, a detection transformer 120B, an amplifier section 130B, a compensation transformer 140B, a compensation capacitor section 150B, and a malfunction sensing section 60B.

[0280] According to one embodiment, the first high current path 111B may be an R-phase power line, the second high current path 112B may be an S-phase power line, and the third high current path 113B may be a T-phase power line.

[0281] The primary side 121B of the sensing transformer 120B may be disposed in each of the first large current path 111B, the second large current path 112B, and the third large current path 113B to generate an induced current in the secondary side 122B.

[0282] The compensation capacitor unit 150B can provide paths through which the compensation currents IC1, IC2, and IC3 generated by the compensation transformer flow to the first, second, and third large current paths 111B, 112B, and 113B, respectively.

[0283] On the other hand, although not shown, the compensation device 103B may of course further include at least a part of the above-mentioned decoupling capacitor section 170 and the first and second disturbance protection elements 11A and 12A.

[0284] Meanwhile, although not shown, the compensation device 103B including the malfunction detector 60B may be modified to suit a three-phase four-wire power system (see FIG. 12). The description of the compensation device for the three-phase four-wire power system may correspond to the content described with reference to FIG.

[0285] FIG. 28 is a diagram illustrating a schematic configuration of a system including a compensation device 104 according to an embodiment of the present invention.

[0286] The compensator 104 may be an embodiment in which first and second balancing units 70 and 80 are added to the three-phase, four-wire system of the compensator 100 of FIG.

[0287] Also, the compensation device 104 may be an embodiment in which the first and second balance units 70 and 80 are added to the three-phase four-wire system shown in Fig. 12, for example. Therefore, a duplicated description will be omitted. On the other hand, the balance may indicate noise balance.

[0288] Meanwhile, the compensator 104 according to the embodiment of the present invention is not limited to being applicable to a three-phase four-wire system, and may of course be modified to suit a three-phase three-wire system or a single-phase two-wire system.

[0289] In one embodiment, the compensation device 104 may include two or more high current paths 111, 112, 113, 114, a detection section 120, an amplification section 130, a compensation transformer section 140, a compensation capacitor section 150, a first balance section 70, and a second balance section 80.

[0290] According to an embodiment, the two or more high current paths 111, 112, 113, 114 may be the R line, the S line, the T line, and the N line, respectively, in a three-phase four-wire power system. Of course, the two or more high current paths 111, 112, 113, 114 may be the R line, the S line, and the T line, respectively, in a three-phase three-wire power system as shown in Fig. 32, or may be the L line and the N line, respectively, in a single-phase two-wire power system as shown in Fig. 33. Thus, in the present invention, the number of the two or more high current paths 111, 112, 113, 114 may be variously set.

[0291] As described above, each of the two or more high current paths 111, 112, 113, 114 may be a path for transmitting the power supplied by the second device 200, i.e., the second currents I21, I22, I23, I24, to the first device 300. According to an embodiment, the second currents I21, I22, I23, I24 may be alternating currents having a frequency in a second frequency band. For example, the second frequency band may be a band having a range of 50 Hz to 60 Hz.

[0292] Furthermore, each of the two or more large current paths 111, 112, 113, 114 may be a path through which the first currents I11, I12, I13, I14, which are common mode noise, flow. The first currents I11, I12, I13, I14 may be generated by various causes (for example, from the first device 300). The first currents I11, I12, I13, I14 may be currents having a frequency in a first frequency band. In this case, the first frequency band may be a frequency band higher than the above-mentioned second frequency band, and may be, for example, a band having a range of 150 KHz to 30 MHz.

[0293] The first balance section 70 may adjust the balance of the first currents I11, I12, I13, and I14 among the large current paths 111, 112, 113, and 114.

[0294] In the present invention, "adjusting the balance" may mean adjusting the physical quantity of each adjustment target so that the difference in the physical quantity between the balance adjustment targets is reduced. Therefore, the first balance unit 70 can reduce the difference in the magnitude of the first currents I11, I12, I13, and I14 flowing through the high current paths 111, 112, 113, and 114, respectively. For example, assume that the magnitude of the first current I11 of the first high current path 111 is 1, the magnitude of the first current I12 of the second high current path 112 is 3, the magnitude of the first current I13 of the third high current path 113 is 1.5, and the magnitude of the first current I14 of the fourth high current path 114 is 2.5. In accordance with the above assumptions, the first balance section 70 may adjust the magnitude of the first current I11 to 2.01, the magnitude of the first current I12 to 2.02, the magnitude of the first current I13 to 1.99, and the magnitude of the first current I14 to 1.98.

[0295] In this way, the present invention evens out the distribution of the first currents I11, I12, I13, I14, which are noise currents on each high current path, allowing the remaining components of the compensation device 104 to better reject the noise.

[0296] According to an embodiment, the first balance unit 70 may be configured to include a large current path connection unit that allows only a current of the first frequency band to flow between the large current paths 111, 112, 113, and 114. In this case, the large current path connection unit may be realized by, for example, a capacitor having a capacity that allows only a current of the first frequency band to flow.

[0297] The detection unit 120 may be electrically connected to the high current paths 111, 112, 113, and 114, sense a first current balanced on two or more of the high current paths 111, 112, 113, and 114, and generate an output signal corresponding to the sensing result.

[0298] The amplifier section 130 may be electrically connected to the detector section 120, and may amplify the output signal output by the detector section 120 to generate an amplified output signal.

[0299] The compensation device 104 may, for example, generate compensation currents IC1, IC2, IC3, and IC4 having the same magnitude and opposite phase as the balance-adjusted first current to compensate for the balance-adjusted first current on the high current paths 111, 112, 113, and 114.

[0300] The compensation transformer unit 140 may be electrically connected to the amplifier unit 130 and generate a compensation current based on the output signal amplified by the amplifier unit 130 described above.

[0301] The compensation capacitor section 150 can provide a path for the compensation current generated by the compensation transformer section 140 to flow to each of the two or more high current paths 111 , 112 , 113 , and 114 .

[0302] The second balance section 80 may adjust the balance of a composite current obtained by adding the compensation currents IC1, IC2, IC3, and IC4 provided by the compensation capacitor section 150 to the first current whose balance has been adjusted on the large current paths 111, 112, 113, and 114.

[0303] As described above, in the present invention, "adjusting the balance" may mean adjusting the physical quantity of each adjustment target so that the difference in physical quantity between the balance adjustment targets is reduced. Therefore, the second balance unit 80 can reduce the difference in magnitude between the composite currents flowing through each of the high current paths 111, 112, 113, and 114. For example, assume that the magnitude of the composite current of the first high current path 111 is 0.01, the magnitude of the composite current of the second high current path 112 is 0.02, the magnitude of the composite current of the third high current path 113 is -0.01, and the magnitude of the composite current of the fourth high current path 114 is -0.02. Under the above assumption, the second balance unit 80 may adjust the magnitude of the composite current in all of the high current paths 111, 112, 113, and 114 to 0.

[0304] In this way, the present invention can more completely block the first current transmitted to the second device 200 by re-evening and reducing the remaining minute distribution of the first current after current compensation by the compensation transformer section 140 and the compensation capacitor section 150.

[0305] According to an embodiment, the second balance unit 80 may be configured to include a large current path connection unit that allows only a current of the first frequency band to flow between the large current paths 111, 112, 113, and 114. In this case, the large current path connection unit may be realized by, for example, a capacitor having a capacity that allows only a current of the first frequency band to flow.

[0306] The compensation device 104 configured as described above may sense and actively compensate for specific conditions of current on two or more high current paths 111, 112, 113, 114, and may be applied to high current, high voltage, and / or high power systems despite the miniaturization of the device 104.

[0307] In the following, the compensation device 104 according to various embodiments will be described with reference to FIGS. 29 to 34 in addition to FIG.

[0308] FIG. 29 is a diagram illustrating a schematic configuration of a compensation device 104A used in a three-phase, four-wire system according to one embodiment of the present invention.

[0309] A compensation device 104A according to one embodiment of the present invention may actively compensate for first currents I11, I12, I13, and I14 input in common mode to four large current paths 111A, 112A, 113A, and 114A connected to a first device (the first device is connected to P4 to P7).

[0310] Therefore, the compensation device 104A according to one embodiment of the present invention may include four high current paths 111A, 112A, 113A, 114A, a detection transformer 120A, an amplifier section 130A, a compensation transformer 140A, a compensation capacitor section 150A, a first balance section 70A, and a second balance section 80A.

[0311] Furthermore, the compensation device 104A may include terminals P1 to P11 connected to external devices. In this case, the terminal P1 may be a terminal connected to a reference potential 1, the terminal P2 may be a terminal connected to a reference potential 2, the terminal P3 may be a terminal connected to a third device that supplies power to the amplifier unit 130A, the terminals P4 to P7 may be terminals connected to a first device, and the terminals P8 to P11 may be terminals connected to a second device.

[0312] FIG. 30 is a diagram illustrating the configuration and operation of a first balance section 70A according to one embodiment.

[0313] The first balance section 70A may adjust the balance of the first currents I11, I12, I13, and I14 between the large current paths 111A, 112A, 113A, and 114A, and generate balanced first currents I11', I12', I13', and I14'.

[0314] In one embodiment, the first balance section 70A may be realized to include capacitors 71A, 72A, and 73A connecting the high current paths 111A, 112A, and 113A corresponding to the R line, S line, and T line, respectively, to the high current path 114A corresponding to the N line, as shown in FIG. 30.

[0315] The capacitances of the capacitors 71A, 72A, and 73A constituting the first balance unit 70A may be determined so that only a current in a first frequency band to which the frequency of the first current belongs flows selectively. For example, when the first frequency band is 150 khz to 30 MHz, the capacitances of the capacitors 71A, 72A, and 73A constituting the balance unit 70A may be determined to be 30 uF, respectively, so that the capacitors 71A, 72A, and 73A operate like short circuits in that frequency band. This allows the balance of the first current between the large current paths 111A, 112A, 113A, and 114A to be adjusted through the capacitors 71A, 72A, and 73A.

[0316] For example, if the magnitude of the first current I11 on the first high current path 111A is relatively larger than the magnitudes of the first currents I12, I13, I14 on the remaining high current paths 112A, 113A, 114A, the first current may be transmitted to the fourth high current path 114A through capacitor 71A, and then transmitted to the remaining high current paths 112A and 113A through capacitors 72A and 73A.

[0317] On the other hand, since the first current is distributed (or balanced) with equal magnitude among the high current paths 111A, 112A, 113A, and 114A, the difference between the impedances Zeq11, Zeq12, Zeq13, and Zeq14 when looking at the first balance section 70A for each of the high current paths 111A, 112A, 113A, and 114A may be less than a predetermined critical impedance difference.

[0318] In one embodiment, the first balance unit 70A may reduce the difference between the voltages of the high current paths 111A, 112A, 113A, and 114A in the first frequency band to a predetermined critical voltage difference or less. As described above, the capacitors 71A, 72A, and 73A operate like short circuits in the first frequency band, so that the first balance unit 70A can reduce the difference between the voltages of the high current paths 111A, 112A, 113A, and 114A to a predetermined critical voltage difference or less. In other words, the difference between the voltages of the nodes N1, N2, N3, and N4 on the high current paths 111A, 112A, 113A, and 114A can be reduced to a predetermined critical voltage difference or less.

[0319] In this manner, the present invention may generate balanced first currents I11', I12', I13', I14' and transmit them to other components of the compensation device 104A, thereby providing effective noise cancellation.

[0320] 29 again, the above-mentioned detection unit 120 may be realized by a detection transformer 120A. The detection transformer 120A may sense the first currents I11', I12', I13', and I14' whose balance is adjusted on the high current paths 111A, 112A, 113A, and 114A while being insulated from the high current paths 111A, 112A, 113A, and 114A.

[0321] The detection transformer 120A may generate a first induced current on the secondary side 122A based on a first magnetic flux density induced by the balanced first currents I11', I12', I13', and I14' on the primary side 121A arranged on the high current paths 111A, 112A, 113A, and 114A.

[0322] Meanwhile, the number of windings of the high current paths 111A, 112A, 113A, 114A (or primary side 121A) and secondary side 122A may be appropriately determined according to the requirements of the system in which the compensation device 104A is used. For example, both the windings of the high current paths 111A, 112A, 113A, 114A (or primary side 121A) and the windings of the secondary side 122A may be wound only once on the transformer core. In such a case, the detection transformer 120A may be configured in such a form that the windings of the high current paths 111A, 112A, 113A, 114A (or primary side 121A) and the windings of the secondary side 122A simply pass through the center hole of the core. However, this is merely an example, and the idea of ​​the present invention is not limited thereto. Moreover, the detection unit 120 being realized by the detection transformer 120A is merely an example, and the concept of the present invention is not limited thereto.

[0323] The detection transformer 120A may be configured so that the second magnetic flux densities induced by the second currents I21, I22, I23, I24 can cancel each other out, and may sense only the first currents I11', I12', I13', I14' in which the balance is adjusted.

[0324] The amplifier unit 130 (e.g., amplifier 130A) may amplify the output signal output by the detection unit 120 described above to generate an amplified output signal. The amplifier unit may be realized by the amplifier units according to the various embodiments described above.

[0325] The compensation transformer section 140 (eg, compensation transformer 140A) may generate a compensation current based on the output signal amplified by the amplifier section 130 described above.

[0326] The compensation capacitor section 150 may be implemented as a compensation capacitor section 150A that provides a path for the current generated by the compensation transformer 140A to flow to each of the four high current paths 111A, 112A, 113A, 114A, as described above.

[0327] The compensation capacitor unit 150A may be configured such that the current flowing through the compensation capacitor among the four large current paths 111A, 112A, 113A, and 114A satisfies a predetermined first current condition. In this case, the predetermined first current condition may be a condition in which the magnitude of the current is less than a predetermined first critical magnitude.

[0328] Furthermore, the compensation capacitor section 150A may be configured so that a current flowing through the compensation capacitor between each of the four large current paths 111A, 112A, 113A, and 114A and the reference potential (reference potential 1) of the compensation device 104A satisfies a predetermined second condition. In this case, the predetermined second current condition may be a condition in which the magnitude of the current is less than a predetermined second critical magnitude.

[0329] The compensation currents flowing through the compensation capacitor section 150A in each of the four high current paths 111A, 112A, 113A, 114A may offset the balanced first currents I11', I12', I13', I14' on the high current paths 111A, 112A, 113A, 114A, and prevent the balanced first currents I11', I12', I13', I14' from being transmitted to the second device 200A.

[0330] According to the above-mentioned process, the compensation device 104A may, for example, generate compensation currents IC1, IC2, IC3, and IC4 having the same magnitude and opposite phase as the balance-adjusted first currents I11', I12', I13', and I14' to compensate for the balance-adjusted first currents I11', I12', I13', and I14' on the high current paths 111A, 112A, 113A, and 114A.

[0331] FIG. 31 is a diagram illustrating the configuration and operation of a second balance section 80A according to one embodiment.

[0332] The second balance section 80 may adjust the balance of composite currents I31, I32, I33, I34 obtained by adding compensation currents IC1, IC2, IC3, IC4 provided by the compensation capacitor section 150A to the first currents I11', I12', I13', I14' whose balance has been adjusted on the high current paths 111A, 112A, 113A, 114A, to generate balanced composite currents I31', I32', I33', I34'.

[0333] In one embodiment, the second balance section 80A may be realized by capacitors 81A, 82A, and 83A that connect the high current paths 111A, 112A, and 113A corresponding to the R line, S line, and T line, respectively, to the high current path 114A corresponding to the N line.

[0334] The capacitances of the capacitors 81A, 82A, and 83A constituting the second balancing unit 80A may be determined so that only current of a first frequency band to which the frequency of the composite current belongs flows selectively, and a detailed explanation of this is provided in the explanation of the first balancing unit 70A.

[0335] In one embodiment, when the magnitude of the composite current I31 on the first high current path 111A is relatively larger than the magnitudes of the composite currents I32, I33, and I34 on the remaining high current paths 112A, 113A, and 114A, the composite current I31 may be transmitted to the fourth high current path 114A through capacitor 81A and then transmitted to the remaining high current paths 112A and 113A again through capacitors 82A and 83A.

[0336] On the other hand, since the composite current is distributed (or balanced) with equal magnitude among the high current paths 111A, 112A, 113A, and 114A, the difference between the impedances Zeq21, Zeq22, Zeq23, and Zeq24 when looking at the first balance section 80A for each of the high current paths 111A, 112A, 113A, and 114A may be less than a predetermined critical impedance difference.

[0337] In one embodiment, the second balance unit 80A may reduce the difference between the voltages of the high current paths 111A, 112A, 113A, and 114A (e.g., nodes N5, N6, N7, and N8) in the first frequency band to a predetermined critical voltage difference or less. Since the capacitors 81A, 82A, and 83A behave like short circuits in the first frequency band, the second balance unit 80A may reduce the difference between the voltages of the high current paths 111A, 112A, 113A, and 114A to a predetermined critical voltage difference or less.

[0338] In this way, the present invention can more completely block the first current transmitted to the second device side by re-evening and reducing the remaining minute distribution of the first current after current compensation by the compensation transformer unit 140A.

[0339] As a result, the compensation device 104A according to one embodiment of the present invention may actively compensate for the first currents I11, I12, I13, and I14 input in common mode to each of the four high current paths 111A, 112A, 113A, and 114A connected to the first device, thereby preventing malfunction or damage to the second device.

[0340] Fig. 32 is a diagram showing a schematic configuration of a compensation device 104B used in a three-phase three-wire system according to another embodiment of the present invention. In the following, reference will be made to Figs. 28 to 31, and descriptions of contents that overlap with those already described will be omitted.

[0341] Further, the description of the detection transformer 120B, the amplifier section 130B, the compensation transformer 140B, and the compensation capacitor section 150B may correspond to the description of each component of the three-phase three-wire system described in FIG. 11, and therefore will be omitted.

[0342] The compensation device 104B includes three large current paths 111B, 112B, and 113B. The compensation device 104B will be described below, focusing on the first balance section 70B and the second balance section 80B where differences occur.

[0343] According to one embodiment, the first high current path 111B may be an R-line power line, the second high current path 112B may be an S-line power line, and the third high current path 113B may be a T-line power line. The first currents I11, I12, and I13 may be input in a common mode to each of the first high current path 111B, the second high current path 112B, and the third high current path 113B.

[0344] The first balance section 70B may adjust the balance of the first currents I11, I12, and I13 between the large current paths 111B, 112B, and 113B, and generate first currents I11', I12', and I13' whose balance has been adjusted.

[0345] In one embodiment, the first balance unit 70B may be realized by a capacitor having one end connected to each of the high current paths 111B, 112B, and 113B corresponding to the R line, S line, and T line, and the other end connected in common, as shown in Fig. 32. For example, when the magnitude of the first current I11 on the first high current path 111B is relatively larger than the magnitudes of the first currents I12 and I13 on the remaining high current paths 112B and 113B, the first current I11 may be transmitted to the remaining high current paths 112B and 113B through the capacitor 71B and the capacitors 72B and 73B.

[0346] The primary side 121B of the detection transformer 120B may be disposed in each of the first high current path 111B, the second high current path 112B, and the third high current path 113B to detect the balanced first currents I11', I12', I13'.

[0347] The compensation capacitor section 150B can provide paths through which the compensation currents IC1, IC2, and IC3 generated by the compensation transformer flow to the first high current path 111B, the second high current path 112B, and the third high current path 113B, respectively.

[0348] The second balance unit 80B may adjust the balance of composite currents I31, I32, I33 obtained by adding compensation currents IC1, IC2, IC3 provided by the compensation capacitor unit 150B to the first currents I11', I12', I13' whose balance has been adjusted on the large current paths 111B, 112B, 113B, to generate composite currents I31', I32', I33' whose balance has been adjusted. The configuration and operation principle of the second balance unit 80B are substantially the same as the configuration and operation principle of the first balance unit 70B, and therefore a detailed description thereof will be omitted.

[0349] Fig. 33 is a diagram illustrating a schematic configuration of a compensation device 104C according to still another embodiment of the present invention. In the following, with reference to Figs. 28 to 31, description of contents that overlap with those already described will be omitted.

[0350] Further, the explanations of the detection transformer 120C, the amplifier section 130C, the compensation transformer 140C, and the compensation capacitor section 150C may correspond to the explanations of each component of the single-phase two-wire system described in Figures 3 and 6 (i.e., the detection transformer 120A, the amplifier section 130A, the compensation transformer 140A, and the compensation capacitor section 150A), and therefore will be omitted.

[0351] The compensation device 104C includes two large current paths 111C and 112C, and the compensation device 104C will be described focusing on the first balance section 70C and the second balance section 80C where differences occur.

[0352] According to one embodiment, the first high current path 111C may be an L-line power line, and the second high current path 112C may be an N-line power line.

[0353] The first balance section 70C may adjust the balance of the first currents I11 and I12 between the large current paths 111C and 112C, and generate first currents I11' and I12' whose balance has been adjusted.

[0354] In one embodiment, the first balance unit 70C may be realized by a capacitor 71C that connects the high current paths 111C and 112C corresponding to the L line and the N line to each other as shown in Fig. 33. As described above, for example, when the magnitude of the first current I11 on the first high current path 111C is relatively larger than the magnitude of the first current I12 on the remaining high current path 112C, the first current I11 may be transmitted to the second high current path 112C through the capacitor 71C.

[0355] The second balance unit 80C may adjust the balance of composite currents I31, I32 in which the compensation currents IC1, IC2 provided by the compensation capacitor unit 150C are added to the first currents I11', I12', the balance of which is adjusted on the large current paths 111C, 112C, to generate composite currents I31', I32' whose balance is adjusted. The configuration and operation principle of the second balance unit 80C are substantially the same as the configuration and operation principle of the first balance unit 70C, and therefore a detailed description thereof will be omitted.

[0356] Such an embodiment of the compensator 104C may be used to cancel (or compensate) first currents I11 and I12 input to or generated in a single-phase, two-wire power system.

[0357] FIG. 34 is a diagram illustrating a schematic configuration of a compensation device 104D used in a three-phase four-wire system according to still another embodiment of the present invention.

[0358] A compensation device 104D according to an embodiment may be configured to further include a phase adjuster 90 in addition to the compensation device similar to the compensation device 104A described with reference to Fig. 28 to Fig. 31. Therefore, the following description will be centered on the role of the phase adjuster 90.

[0359] The phase adjustment unit 90 according to an embodiment may electrically connect at least two or more high current paths between the second device 200D and the compensation device 104D, and the electrically connected at least two or more high current paths may be used as one high current path. In this case, "electrically connecting" two or more high current paths may mean electrically shorting two or more high current paths.

[0360] For example, the phase adjustment unit 90 may utilize only the R line (S line) and the N line depending on the operation of the switching element 91 between the first high current path and the second high current path, and a compensation device designed to be compatible with three-phase four-wire may be used for a single-phase two-wire system.

[0361] Of course, the phase adjustment unit 90 may operate both the switching element 91 between the first and second high current paths and the switching element 92 between the second and third high current paths, and may utilize the R line (the S line and the T line) and the N line, and a compensation device designed to be compatible with a three-phase four-wire system may be used in a single-phase two-wire system.

[0362] This allows the present invention to be used in a variety of power systems without modifying or replacing the compensation device 104D.

[0363] FIG. 35 is a diagram illustrating a schematic configuration of a system including a compensation device 105 according to an embodiment of the present invention.

[0364] Compensation device 105 in Fig. 35 is different from compensation device 104 in Fig. 28 in that compensation capacitor section 150 is provided, and may further include output impedance adjustment section 50. Therefore, explanations of components that overlap with those of compensation device 104 in Fig. 28 will be omitted, and the explanation will focus on compensation capacitor section 150 and output impedance adjustment section 50.

[0365] The compensation capacitor unit 150 can provide a path through which the compensation current IC generated by the compensation transformer unit 140 flows to the reference high current path 114. At this time, the reference high current path 114 means any one of the high current paths 111, 112, 113, and 114, and any one of the remaining high current paths 111, 112, and 113 may also correspond to the reference high current path depending on the selection.

[0366] According to an embodiment, the compensation capacitor unit 150 may be realized by a capacitor that provides a path through which the compensation current IC generated by the compensation transformer unit 140 flows to the reference large current path 114. In this case, the compensation capacitor unit 150 may include a capacitor that connects a reference potential (reference potential 1) of the compensation device 105 and the reference large current path 114.

[0367] The second balancing unit 80 may distribute the compensation current IC provided to the reference high current path 114 to two or more high current paths 111, 112, 113, and 114. For example, when the magnitude of the compensation current IC provided to the high current path 114 is 8, the second balancing unit 80 may distribute the compensation current IC such that a compensation current with a magnitude of 2 flows through each of the four high current paths 111, 112, 113, and 114.

[0368] Meanwhile, the second balancing unit 80 may adjust the balance of the composite current on the large current paths 111, 112, 113, and 114. In this case, the composite current may mean a current obtained by adding a distributed compensation current to the first current whose balance has been adjusted by the first balancing unit. For example, the second balancing unit 80 may reduce the difference in magnitude between the composite currents flowing through the large current paths 111, 112, 113, and 114.

[0369] According to an embodiment, the second balance unit 80 may be configured to include a large current path connection unit that allows only a current of the first frequency band to flow between the large current paths 111, 112, 113, and 114. In this case, the large current path connection unit may be realized by, for example, a capacitor having a capacity that allows only a current of the first frequency band to flow.

[0370] The second balancing section 80 may adjust the output impedance from the compensation transformer section 140 to the second device 200 side together with the output impedance adjusting section 50 described later.

[0371] The output impedance adjustment unit 50 may adjust the output impedance from the compensation transformer unit 140 to the second device 200 side together with the second balance unit 80. For example, the impedance adjustment unit 50 may reduce the output impedance seen from the compensation transformer unit 140 to the second device 200 side, and prevent the compensation current IC from flowing in the reverse direction (e.g., in the direction of the compensation transformer unit 140). In one embodiment, the output impedance adjustment unit 50 may be realized by a capacitor having a predetermined capacitance.

[0372] In the following, the compensation device 105 according to various embodiments will be described with reference to FIGS. 36 to 39 together with FIG.

[0373] FIG. 36 is a diagram illustrating a schematic configuration of a compensation device 105A used in a three-phase four-wire system according to one embodiment of the present invention.

[0374] Compensation device 105A in Fig. 35 differs from compensation device 104A described with reference to Fig. 29 to Fig. 31 in that compensation capacitor section 150A and output impedance adjustment section 50A may be added. Therefore, explanations of components that overlap with those of compensation devices 104 and 104A will be omitted, and the compensation capacitor section 150A and output impedance adjustment section 50A will be mainly described. Below, compensation device 105A will be described with reference to Figs. 36 to 38, focusing on compensation capacitor section 150A and output impedance adjustment section 50A.

[0375] Furthermore, the compensation device 105A may include terminals P1 to P11 connected to external devices. In this case, the terminal P1 may be a terminal connected to a reference potential 1, the terminal P2 may be a terminal connected to a reference potential 2, the terminal P3 may be a terminal connected to a third device that supplies power to the amplifier unit 130A, the terminals P4 to P7 may be terminals connected to a first device, and the terminals P8 to P11 may be terminals connected to a second device.

[0376] On the other hand, the configuration and operation of the first balance section 70A according to one embodiment may correspond to the description with reference to FIG.

[0377] FIG. 37 is a diagram illustrating a process in which the compensation current IC generated by the compensation transformer section 140A is distributed to the large current paths 111A, 112A, 113A, and 114A through the compensation capacitor section 150A and the second balance section 80A.

[0378] The compensation capacitor unit 150A can provide a path through which the compensation current generated by the compensation transformer unit 140A flows to the reference high current path 114A. Meanwhile, the compensation current transmitted to the reference high current path 114A may be distributed to each of the high current paths 111A, 112A, 113A, and 114A through the second balance unit 80A.

[0379] For example, the compensation current transmitted to the reference high current path 114A may be transmitted to the first high current path 111A through the first capacitor 81A of the second balance section 80A (path W1). Similarly, the compensation current may be transmitted to the second high current path 112A and the third high current path 113A through the second capacitor 82A and the third capacitor 83A, respectively (see paths W2 and W3). On the other hand, the remaining compensation current transmitted to the high current paths 111A, 112A, and 113A may remain in the fourth high current path (or the reference high current path 114A) (see path W4).

[0380] The compensation currents provided to the four high current paths 111A, 112A, 113A, 114A, respectively, can cancel the first currents I11', I12', I13', I14' whose balance is adjusted on each of the high current paths 111A, 112A, 113A, 114A, and prevent the first currents I11', I12', I13', I14' whose balance is adjusted from being transmitted to the second device 200A. At this time, the first currents I11', I12', I13', I14' whose balance is adjusted and the compensation currents can be, for example, currents having the same (or that can be considered to be the same) magnitude and having opposite phases (or phases corresponding to opposite phases) to each other.

[0381] In one embodiment, the compensation capacitor unit 150A may be configured so that a current flowing through the compensation capacitor between the reference large current path 114A and the reference potential (reference potential 1) of the compensation device 105A satisfies a predetermined second condition. In this case, the predetermined second current condition may be a condition in which the magnitude of the current is less than a predetermined second critical magnitude.

[0382] As described above, the second balancing unit 80 distributes the compensation current provided by the compensation capacitor unit 150A to each of the large current paths 111A, 112A, 113A, and 114A, and may also adjust the balance of the composite current to generate a balanced composite current. In this case, the composite current may refer to a current obtained by adding the distributed compensation current to the first currents I11', I12', I13', and I14' whose balance has been adjusted by the first balancing unit 70A.

[0383] The configuration and operation of the second balance section 80A according to one embodiment may correspond to the description with reference to FIG. 31, and therefore will not be repeated.

[0384] FIG. 38 is a diagram for explaining the process in which the output impedances Zeq31, Zeq32, Zeq33, and Zeq34 are adjusted by the second balance section 80A and the output impedance adjuster 50A.

[0385] In one embodiment, the output impedance adjustment section 50A may include a capacitor 51A that provides a path for current to flow between the reference large current path 114A and the reference potential of the compensation transformer section 140A, as shown in FIG.

[0386] As described above, the second balancing section 80A may also include capacitors 81A, 82A, and 83A that provide paths through which current flows between the reference large current path 114A and each of the remaining large current paths 111A, 112A, and 113A.

[0387] In one embodiment, the output impedances Zeq31, Zeq32, Zeq33, and Zeq34 from the compensation transformer unit 140A to the second device side may be a composite impedance obtained by connecting the impedance of the capacitor 51A and the capacitors 81A, 82A, and 83A in series and the impedances Zeq41, Zeq42, Zeq43, and Zeq44 of the second device in parallel. For example, in the first large current path 111A, the output impedance Zeq31 may be a composite impedance obtained by connecting the impedance of the capacitor 51A and the capacitor 81A in series and the impedance Zeq41 of the second device in parallel.

[0388] In this way, the second balance unit 80A and the output impedance adjustment unit 50A act as impedances connected in parallel with the impedances Zeq41, Zeq42, Zeq43, and Zeq44 of the second device, and the compensation transformer unit 140A reduces the output impedances Zeq31, Zeq32, Zeq33, and Zeq34 seen from the second device side, so that current compensation using the compensation current can be performed smoothly even for second device impedances Zeq41, Zeq42, Zeq43, and Zeq44 of various sizes.

[0389] FIG. 39 is a diagram showing a schematic configuration of a compensation device 105B used in a three-phase three-wire system according to another embodiment of the present invention.

[0390] The compensation device 105B in Fig. 39 may differ from the compensation device 104B described with reference to Fig. 32 in the compensation capacitor section 150B and the output impedance adjustment section 50B. Therefore, explanations of components that overlap with those of the compensation device 104B in Fig. 32 (e.g., detection transformer 120B, amplifier section 130B, compensation transformer 140B, first and second balance sections 70B and 80B, etc.) will be omitted, and the following explanation will focus on the compensation capacitor section 150B and the output impedance adjustment section 50B.

[0391] The compensation capacitor unit 150B can provide a path through which the compensation current IC generated by the compensation transformer flows to the third high current path 113B, which is a reference high current path. At this time, the reference high current path 113B means any one of the high current paths 111B, 112B, and 113B, and the remaining high current paths 111B and 112B may also be reference high current paths according to selection.

[0392] In one embodiment, compensation capacitor portion 150B may be implemented with capacitor 151B. The second balancing section 80B may distribute the compensation current transmitted to the reference large current path 113B to each of the large current paths 111B, 112B, and 113B.

[0393] In one embodiment, the second balance section 80B may be realized by capacitors 81B, 82B, and 83B having one end connected to each of the large current paths 111B, 112B, and 113B corresponding to the R line, S line, and T line, and the other end connected in common.

[0394] In one embodiment, the compensation current sent to the reference high current path 113B may be sent to the first high current path 111B through the first capacitor 81B of the second balance unit 80B. Similarly, the compensation current may be sent to the second high current path 112B and the third high current path 113B through the second capacitor 82B and the third capacitor 83B, respectively.

[0395] The compensation current provided to each of the three high current paths 111B, 112B, 113B can offset (or compensate) the balanced first currents I11', I12', I13 on each high current path 111B, 112B, 113B.

[0396] In one embodiment, the compensation capacitor section 150B may be in a condition where the magnitude of the current flowing through the compensation capacitor between the reference large current path 113B and the reference potential (reference potential 1) of the compensation device 105B is less than a predetermined second critical magnitude.

[0397] As described above, the second balance section 80B not only distributes the compensation current provided by the compensation capacitor section 150B to each of the large current paths 111B, 112B, and 113B, but may also adjust the balance of the composite current and generate a balanced composite current.

[0398] The capacitances of the capacitors 81B, 82B, and 83B constituting the second balance section 80B may be determined so that only a current in a first frequency band to which the frequency of the composite current belongs flows selectively.

[0399] In one embodiment, the second balance section 80B may adjust the output impedance from the compensation section 140B to the second device side together with the output impedance adjustment section 50B.

[0400] In one embodiment, the output impedance adjustment unit 50B may include a capacitor 51B that provides a path for current to flow between the reference large current path 113B and the reference potential of the compensation unit 140B.

[0401] The principle of adjusting the output impedance from the compensator 140B to the second device by the second balance unit 80B and the output impedance adjuster 50B will be described in detail with reference to FIG. 38, and therefore will not be described in detail here.

[0402] Such an embodiment of the compensator 105B may be used to cancel (or compensate) common mode first currents I11, I12, I13 occurring in a three-phase, three-wire power system.

[0403] 40 illustrates a schematic configuration of a system including an active compensation device 106 according to an embodiment of the present invention. The active compensation device 106 may actively compensate for a noise current In (e.g., an EMI noise current) and / or a noise voltage (e.g., an EMI noise voltage) generated in a common mode (CM) on two or more large current paths 111 and 112 from a first device 300.

[0404] The active compensation device 106 may include a detection unit 120, a first amplification unit 131, a second amplification unit 132, an Nth amplification unit 133, and a compensation unit 160, where N is a natural number equal to or greater than 2. That is, the active compensation device 106 according to various embodiments of the present invention may include two or more parallel amplification units.

[0405] 1, the amplifying section 130 is configured with a parallel structure of a first amplifying section 131, a second amplifying section 132, and an Nth amplifying section 133. Therefore, the contents overlapping with the components (e.g., the detecting section 120 and the compensating section 160, etc.) described in the compensation device 100 described above will be omitted, and the first amplifying section 131, the second amplifying section 132, and the Nth amplifying section 133 will be mainly described.

[0406] For example, a common mode noise current In may be input to the large current paths 111 and 112 by a switching operation of a power conversion device on the first device 300 side. Alternatively, for example, a noise current leaking from the first device 300 side passes through a ground (for example, reference potential 1) and flows into the large current paths 111 and 112 via the second device 200, thereby generating the noise current In.

[0407] The noise current In generated in the same direction on the high current paths 111 and 112 can be regarded as a common mode noise current. In addition, the common mode noise voltage (not shown) may be a voltage generated between the ground (for example, reference potential 1) and the high current paths 111 and 112, instead of a voltage generated between the high current paths 111 and 112.

[0408] For example, the noise current In may be a noise current due to a parasitic capacitance between the first device 300 and the surrounding environment. The noise current In may correspond to the first current (e.g., I11, I12, I13, I14, etc.) described above. For example, the first device 300 side may correspond to a noise source, and the second device 200 side may correspond to a noise receiver.

[0409] The detection unit 120 may sense the noise current In on two or more large current paths 111 and 112, and generate an output signal corresponding to the noise current In on the first, second, and Nth amplification units 131, 132, and 133 sides.

[0410] For example, the detection unit 120 may be in a form in which the electric wires on the amplifier units 131 and 132 side are wound around a CM choke around which the power lines corresponding to the high current paths 111 and 112 are wound. The detection unit 120 may induce output signals (e.g., induced voltage or induced current) based on the noise currents In on the high current paths 111 and 112 to the electric wires on the first, second, and Nth amplifier units 131, 132, and 133 sides, respectively, while being insulated from the high current paths 111 and 112. That is, the detection unit 120 can generate a plurality of output signals. The output signals (e.g., induced voltage or induced current) may be input signals to the first, second, and Nth amplifier units 131, 132, and 133. However, this is merely one example.

[0411] According to various embodiments of the present invention, the active compensation device may include a plurality of amplifiers. For example, the detector 120 may generate output signals corresponding to the plurality of amplifiers based on the noise currents In on the large current paths 111 and 112. The output signals from the detector 120 may be input to the plurality of amplifiers, respectively.

[0412] 40 shows first, second and Nth amplifying units 131, 132 and 133, however, since N is a natural number of 2 or more, the amplifying units of the active compensation devices according to various embodiments may of course be composed of only the first and second amplifying units 131 and 132. In the following, the first, second and Nth amplifying units 131, 132 and 133 will be described as an example.

[0413] According to an embodiment, the detection unit 120 may be differentially connected to the input terminals of the first, second and Nth amplification units 131 and 132, respectively.

[0414] The first, second, and Nth amplifiers 131, 132, and 133 may be electrically connected to the detector 120 and may amplify the output signal output by the detector 120 to generate an amplified output signal. The amplifiers 131, 132, and 133 may be realized by various means and may include active elements. In one embodiment, each of the amplifiers 131, 132, and 133 may include at least one of an OP-AMP or a BJT (Bipolar Junction Transistor).

[0415] The amplifier units 131, 132, 133 may receive power from a third device 400 that is distinct from the first device 300 and / or the second device 200, amplify the output signal output by the detection unit 120, and generate an amplified current or an amplified voltage.

[0416] Each of the multiple amplifiers 131, 132, 133 may be realized by the various amplifiers described above.

[0417] The output signals (e.g., currents or voltages) amplified by the amplifiers 131, 132, and 133 may be input to the compensation unit 160. For example, the first amplifier 131 may output a first amplified current (or a first amplified voltage) to the compensation unit 160 side, the second amplifier 132 may output a second amplified current (or a second amplified voltage) to the compensation unit 160 side, and the Nth amplifier 133 may output an Nth amplified current (or an Nth amplified voltage) to the compensation unit 160 side.

[0418] The compensation section 160 may generate a compensation current or a compensation voltage based on the amplified signals output from the first, second, and Nth amplifiers 131, 132, and 133, respectively.

[0419] According to an embodiment, the compensation unit 160 may generate a compensation current based on the first amplified current output from the first amplifier unit 131, the second amplified current output from the second amplifier unit 132, and the Nth amplified current output from the Nth amplifier unit 133. The compensation current may be injected onto the high current paths 111 and 112 or extracted from the high current paths 111 and 112 to cancel or reduce the noise current In on the high current paths 111 and 112.

[0420] The compensation current may be injected into the large current paths 111 and 112 to cancel the noise current In, or may flow at least a part of the noise current In to the ground (for example, the reference potential 1) to reduce the noise current In. In this case, the compensation unit 160 may correspond to current compensation. A detailed description of the current compensation will be given later with reference to FIGS. 41 and 42, and FIGS. 48 and 49.

[0421] According to another embodiment, the compensation unit 160 may generate a compensation voltage in series on the large current paths 111 and 112 based on the first amplified voltage output from the first amplifier unit 131 and the second amplified voltage output from the second amplifier unit 132. The output side of the compensation unit 160 may generate a compensation voltage in series on the large current paths 111 and 112, but may be insulated from the amplifier units 131 and 132. For example, the compensation unit 160 may be composed of a compensation transformer for the above insulation. The above compensation voltage may have an effect of suppressing the noise current In flowing on the large current paths 111 and 112. In this case, the compensation unit 160 may correspond to voltage compensation. A detailed description of the voltage compensation will be described later with reference to Figs. 43 to 45.

[0422] The compensator 160 may be of a feedforward type that compensates for noise input from the first device 300 at the front end, which is the power supply side. However, the present invention is not limited thereto, and the active compensator 106 may include a compensator that returns noise to the rear end for compensation.

[0423] FIG. 41 shows a more specific example of the embodiment shown in FIG. 40 that uses two amplifying sections, and generally illustrates a system including an active compensation device 106A1 according to an embodiment of the present invention. FIG. 42 generally illustrates a specific example of the active compensation device 106A1.

[0424] 41 and 42, an active compensation device 106A1 according to an embodiment of the present invention may include a detection transformer 120A1, a first amplifier unit 131A, a second amplifier unit 132A, a compensation transformer 140A1, and a compensation capacitor unit 150A. The compensation unit 160 described above may be realized by, for example, the compensation transformer 140A1 and the compensation capacitor unit 150A.

[0425] According to one embodiment, the detection transformer 120A1 is an example of the above-mentioned detection unit 120, and the first and second amplifiers 131A and 132A are an example of the above-mentioned first and second amplifiers 131 and 132. Therefore, the description of the above-mentioned detection unit 120 and the first and second amplifiers 131 and 132 may correspond to the description of the detection transformer 120A1 and the first and second amplifiers 131A and 132A. Therefore, the contents that overlap with the contents described in FIG. 40 will be omitted.

[0426] In one embodiment, the sensing transformer 120A1 can detect a voltage induced across the sensing transformer 120A1 due to a noise current In input to the high current paths 111 and 112 (eg, power lines).

[0427] The detection transformer 120A1 may include a core C1, a primary side (e.g., a primary winding) corresponding to the large current paths 111 and 112 (e.g., a power line), and a secondary side (e.g., a secondary winding) connected to the input terminals of the amplifiers 131A and 132A. As an example, the large current paths 111 and 112 corresponding to the primary side may pass through the core C1, and the electric wire on the amplifier side corresponding to the secondary side may be wound around the core C1. However, this is not limited to the above.

[0428] According to one embodiment, the primary side of the sensing transformer 120A1 may have a first high current path 111 and a second high current path 112 passing through or wound around a core C1, respectively.

[0429] According to one embodiment, the secondary side of the detection transformer 120A1 may be in a form in which a first electric wire L1 differentially connected to an input terminal of the first amplifier unit 131A and a second electric wire L2 differentially connected to an input terminal of the second amplifier unit 132A are each wound around the above-mentioned core C1.

[0430] The detection transformer 120A1 may generate an induced current or an induced voltage on the secondary side based on the magnetic flux density induced by the noise current In from the primary side through the large current paths 111 and 112 passing through the core C1.

[0431] According to an embodiment of the present invention, the detection transformer 120A1 may output a signal to be input to the first amplifier 131A and a signal to be input to the second amplifier 132A based on the above-mentioned noise current In. That is, the detection transformer 120A1 may output a plurality of output signals in parallel on the secondary side.

[0432] When two parallel amplifiers are used, for example, a first induced current generated in a first wire L1 on the secondary side of the detection transformer 120A1 may be differentially input to the first amplifier 131A, and a second induced current generated in a second wire L2 on the secondary side of the detection transformer 120A1 may be differentially input to the second amplifier 132A.

[0433] Alternatively, for example, depending on the configuration of the amplifiers 131A and 132A, the first electric wire L1 on the secondary side of the detection transformer 120A1 may be disposed on a path connecting the input terminal of the first amplifier 131A and the reference potential (reference potential 2) of the first amplifier 131A. That is, one end of the first electric wire L1 on the secondary side may be connected to the input terminal of the first amplifier 131A, and the other end of the first electric wire L1 on the secondary side may be connected to the reference potential (reference potential 2) of the first amplifier 131A. Similarly, the second electric wire L2 on the secondary side of the detection transformer 120A1 may be disposed on a path connecting the input terminal of the second amplifier 132A and the reference potential (reference potential 2) of the second amplifier 132A.

[0434] For example, in the detection transformer 120A1, the winding ratio of the first electric wire L1 on the primary side and the secondary side is 1:N. sen1 Then, the current induced in the first electric wire L1, that is, the current input to the first amplifier 131A, is I n / 2N sen1 In addition, in the detection transformer 120A1, the winding ratio of the second electric wire L2 on the primary side and the secondary side is 1:N. sen2 Then, the current induced in the second electric wire L2, that is, the current input to the second amplifier 132A, is I n / 2N sen2 That is, the first and second amplifiers 131A and 132A receive the noise current I ncan be separated into two amplification sections and detected in parallel.

[0435] Therefore, according to one embodiment, when the first electric wire L1 and the second electric wire L2 have the same number of windings, the input currents of the first amplifier 131A and the second amplifier 132A may be the same or correspond to each other. That is, when the first electric wire L1 and the second electric wire L2 have the same number of windings, the output current by the detection of the noise current In may be divided into halves and input to the first amplifier 131A and the second amplifier 132A, respectively. However, the present invention is not limited to this, and according to another embodiment, the first electric wire L1 and the second electric wire L2 may have different number of windings. In this case, the input current of the first amplifier 131A and the input current of the second amplifier 132A may also be different from each other.

[0436] The first amplifier 131A can amplify the first induced current induced in the first electric wire L1 on the secondary side based on a gain (e.g., F1) of the first amplifier 131A. Similarly, the second amplifier 132A can amplify the second induced current induced in the second electric wire L2 on the secondary side based on a gain (e.g., F2) of the second amplifier 132A.

[0437] According to an embodiment, the gain F1 of the first amplifying unit 131A and the gain F2 of the second amplifying unit 132A may be designed to have the same magnitude. For example, they may be designed to satisfy F1=-F2. In this case, the first amplifying unit 131A and the second amplifying unit 132A may operate in a complementary manner. For example, the first amplifying unit 131A and the second amplifying unit 132A may operate in a full-bridge configuration.

[0438] However, the present invention is not limited to this, and according to one embodiment, the gain F1 of the first amplifying unit 131A and the gain F2 of the second amplifying unit 132A may be different from each other.

[0439] Compensation transformer 140A1 and compensation capacitor section 150A may correspond to the above-mentioned compensation section 160. The current amplified by first amplifier section 131A and the current amplified by second amplifier section 132A each flow through the primary side of compensation transformer 140A1.

[0440] The compensation transformer 140A1 may include a core C2, a primary side (e.g., a primary winding) connected to the output terminals of the amplifiers 131A and 132A, and a secondary side (e.g., a secondary winding) connected to the large current paths 111 and 112. The compensation transformer 140A1 may have a configuration in which the primary side electric wires L3 and L4 and the secondary side electric wires are wound around one core C2. The primary side of the compensation transformer 140A1 may have a configuration in which the electric wire L3 through which the output current of the first amplifier 131A flows and the electric wire L4 through which the output current of the second amplifier 132A flows are each wound around the core C2.

[0441] Compensation transformer 140A1 may generate an induced current in a secondary wire based on a magnetic flux density induced by a current flowing in the primary wire.

[0442] On the other hand, a third electric wire L3 through which the current output from the first amplifier unit 131A flows and a fourth electric wire L4 through which the current output from the second amplifier unit 132A flows may be wound on the primary side of the compensation transformer 140A1.

[0443] According to one embodiment, the third wire L3 is connected to the output current F1*I n / 2N sen1 In addition, the fourth electric wire L4 can carry the output current F2*I n / 2N sen2 can flow.

[0444] For example, in the compensation transformer 140A1, the third electric wire L3 on the primary side and the winding ratio on the secondary side are set to 1:N. inj1 , the fourth wire L4 on the primary side and the winding ratio on the secondary side are 1:N inj2Then, the current induced on the secondary side of the compensation transformer 140A1 is "F1*In / 2(N sen1 *N inj1 )+F2*I n / 2(N sen2 *N inj2 )" may be used.

[0445] According to one embodiment, the first amplifier unit 131A and its input / output terminals and the second amplifier unit 132A and its input / output terminals may be symmetrical to each other (F1=F2, N sen1 =N sen2 , N inj1 =N inj2 ), however, the present invention is not limited thereto.

[0446] The current transformed through compensation transformer 140A1 (ie, the secondary current) may be injected or drawn as compensation current IC into large current paths 111 and 112 (eg, power lines) through compensation capacitor section 150A.

[0447] In one embodiment, when the compensation current IC is injected into the high current paths 111 and 112, the compensation current IC may be in opposite phase to the noise current In to cancel the noise current In. In another embodiment, when the compensation current IC is drawn from the high current paths 111 and 112, the compensation current IC may be proportional to the noise current In. This allows the active compensation device 106A1 to reduce noise.

[0448] In one embodiment of the present invention, the first and second amplifier sections 131A and 132A of the active compensation device 106A1 can accommodate and generate twice the current swing for the same DC voltage supply (e.g., the voltage supply of the third device 400) by utilizing a full-bridge circuit.

[0449] 42, the active compensation device 106A1 according to an embodiment of the present invention may further include a decoupling capacitor section 170A. The description of the decoupling capacitor section 170A corresponds to the description of the decoupling capacitor sections 170 and 170A in FIGS. 14 and 15, and therefore will not be provided.

[0450] On the other hand, the amplification section of the present invention is not limited to being composed of a first amplification section 131A and a second amplification section 132A, but may include a plurality of amplification sections including a first amplification section 131A, a second amplification section 132A, and an Nth amplification section (not shown), as shown in FIG. 40.

[0451] According to an embodiment, the plurality of amplifiers may be connected in parallel to the detection transformer 120A1 and the compensation transformer 140A1, respectively, as shown in Fig. 42. The manner in which the Nth amplifier (not shown) is connected to the detection transformer 120A1 and the compensation transformer 140A1 may correspond to the manner in which the first and second amplifiers 131A and 132A are connected to the detection transformer 120A1 and the compensation transformer 140A1.

[0452] 42, an Nth electric wire (not shown) that corresponds to the secondary side and is differentially connected to an input terminal of an Nth amplifier (not shown) may be additionally wound around core C1 of detection transformer 120A1. For example, an Nth induced current generated in an Nth electric wire (not shown) on the secondary side of detection transformer 120A1 may be differentially input to the Nth amplifier.

[0453] Furthermore, the Nth amplifier (not shown) may output an output current of the Nth amplifier (not shown) based on the input Nth induced current and the current gain of the Nth amplifier. An electric wire through which the output current of the Nth amplifier flows may be additionally wound on the core C2 of the compensation transformer 140A1. In this case, the compensation transformer 140A1 may generate a compensation current with a winding ratio between the output currents of the first, second, and Nth amplifiers and the output ends of each.

[0454] FIG. 43 shows a more specific example of the embodiment shown in FIG. 40, and shows a schematic diagram of a system including an active compensation device 106B according to an embodiment of the present invention.

[0455] FIG. 44 generally illustrates a compensation device 106B1 as one example of the compensation device 106B shown in FIG. 43, and FIG. 45 generally illustrates an active compensation device 106B2 as another example of the active compensation device 106B shown in FIG. 43.

[0456] 43, compensation device 106B may include detection unit 120B, first amplifier unit 131B, second amplifier unit 132B, and compensation transformer 190B. Detection unit 120B, first and second amplifier units 131B and 132B, and compensation transformer 190B are examples of detection unit 120, first and second amplifier units 131 and 132, and compensation unit 160, respectively. Content common to the above content will be omitted.

[0457] The detection unit 120B may output a first output signal and a second output signal based on the noise current In, and the first output signal may be input to the first amplifier 131B, and the second output signal may be input to the second amplifier 132B. For example, the first output signal may be input to an input terminal of the first amplifier 131B as a differential voltage, and the second output signal may be input to an input terminal of the second amplifier 132B as a differential voltage. Depending on the configuration of the detection unit 120B, the first output signal and the second output signal may be the same as or different from each other.

[0458] The first amplifier 131B may output a first output voltage V1 corresponding to the product of the voltage input to the first amplifier 131B and the voltage gain of the first amplifier 131B. The second amplifier 132B may output a second output voltage V2 corresponding to the product of the voltage input to the second amplifier 132B and the voltage gain of the second amplifier 132B. The first and second output voltages V1 and V2 may indicate potentials of the amplifiers 131B and 132B with respect to a reference potential 2, respectively.

[0459] In the compensation device 106B according to an embodiment of the present invention, the difference between the first output voltage V1 and the second output voltage V2 may be input to the compensation transformer 190B. That is, the difference between the first output voltage V1 and the second output voltage V2 may correspond to the input voltage of the compensation transformer 190B.

[0460] The compensation transformer 190B may be an example of the above-described compensation unit 160. In other words, the above-described compensation unit 160 may be realized by the compensation transformer 190B in the compensation device 106B according to one embodiment.

[0461] The voltage across the primary side of compensation transformer 190B may correspond to the difference between the output voltage V1 of first amplifier section 131B and the output voltage of second amplifier section 131B described above.

[0462] The compensation transformer 190B may induce a compensation voltage in series on the secondary side of the large current paths 111 and 112 based on the voltage applied to the primary side. The compensation voltage generated in series on the large current paths 111 and 112 can have the effect of suppressing the noise current In flowing through the large current paths 111 and 112.

[0463] 43, the compensation transformer 190B is illustrated as generating a compensation voltage at the front end, which is the power supply side (i.e., between the detection unit 120B and the second device 200), but the present invention is not limited thereto. As an example, the compensation transformer 190B may generate a compensation voltage on the high current paths 111 and 112 between the detection unit 120B and the first device 300.

[0464] Compensators 106B1 and 106B2, which are examples of the compensation device 106B, will be described with reference to FIGS. 44 and 45 below.

[0465] The amplifier units 131B and 132B of the compensation device 106B1 and the compensation device 106B2 and the compensation transformer 190B may correspond to each other. According to an embodiment, the detection unit 120B1 of the compensation device 106B1 and the detection unit 120B2 of the compensation device 106B2 may be different from each other.

[0466] The detectors 120B1 and 120B2 of the compensation devices 106B1 and 106B2 according to an embodiment may have a configuration in which a secondary wire is wound in an overlapping manner around a CM choke around which the first large current path 111 and the second large current path 112 are wound. When the detectors 120B1 and 120B2 are formed using a CM choke in this manner, the detectors 120B1 and 120B2 can function as a passive filter as a CM choke in addition to the functions of detection and transformation.

[0467] That is, when detection units 120B1 and 120B2 are formed by overlapping and winding a secondary electric wire around a CM choke, detection units 120B1 and 120B2 may simultaneously perform the role of suppressing or blocking the noise current In as well as detecting and transforming the noise current In.

[0468] The primary sides of the detection units 120B1 and 120B2 may be windings in which the first large current path 111 and the second large current path 112 are wound around a CM choke.

[0469] On the other hand, in one embodiment (see FIG. 44), a single electric wire may be wound around the CM choke on the secondary side of the detection unit 120B1. The single electric wire may be connected in parallel to the input terminal of the first amplification unit 131B and at the same time connected in parallel to the input terminal of the second amplification unit 132B. For example, the voltage Vsen induced on the secondary side of the detection unit 120B1 may be differentially input to the input terminal of the first amplification unit 131B and at the same time differentially input to the input terminal of the second amplification unit 132B.

[0470] In the embodiment of FIG. 44, for example, the voltage Vsen induced on the secondary side of the detection unit 120B1 can be input equally to the first amplification unit 131B and the second amplification unit 132B.

[0471] The first amplifier 131B may output a first output voltage V1 corresponding to a value obtained by multiplying the differential input voltage Vsen of the first amplifier 131B by the voltage gain G1 of the first amplifier 131B. The second amplifier 132B may output a second output voltage V2 corresponding to a value obtained by multiplying the differential input voltage Vsen of the second amplifier 132B by the voltage gain G2 of the second amplifier 132B. The first output voltage V1 and the second output voltage V2 may be potentials based on the reference potential 2 of the amplifiers 131B and 132B. The difference between the first output voltage V1 and the second output voltage V2 may be the input voltage of the compensation transformer 190B. According to an embodiment of FIG. 44, G1=-G2 may be satisfied.

[0472] Meanwhile, in another embodiment (see FIG. 45), the secondary side of the detection unit 120B2 may have electric wires corresponding to the first amplifier unit 131B and the second amplifier unit 132B wound around the CM choke in an overlapping manner. For example, the secondary side of the detection unit 120B2 may have a configuration in which the first electric wire L11 differentially connected to the input terminal of the first amplifier unit 131B and the second electric wire L12 differentially connected to the input terminal of the second amplifier unit 132A are wound around the CM choke in an overlapping manner.

[0473] For example, the voltage Vsen1 induced in the first wire L11 in the secondary side of the detection unit 120B2 may be differentially input to the first amplifier 131B, and the voltage Vsen2 induced in the second wire L12 in the secondary side of the detection unit 120B2 may be differentially input to the second amplifier 132B.

[0474] In the embodiment of FIG. 45, the differential input voltage Vsen1 of the first amplifier 131B and the differential input voltage Vsen2 of the second amplifier 132B may be generated based on the number of turns of the first wire L11 on the secondary side and the number of turns of the second wire L12 on the secondary side. According to one embodiment, the first wire L11 and the second wire L12 may be wound to generate input voltages of opposite phases in each amplifier 131B and 132B. For example, when the number of turns of the first wire L11 and the second wire L12 on the secondary side are similar, the differential input voltages Vsen1 and Vsen2 of each amplifier 131B and 132B may have similar magnitudes and opposite phases. That is, Vsen1=-Vsen2. For example, the input voltage Vsen1 of the first amplifier 131B may correspond to a value obtained by multiplying the voltage induced on the primary side of the detector 120B2 (i.e., across the CM choke) by the winding ratio of the first wire L11 on the primary side and the secondary side. The input voltage Vsen2 of the second amplifier 132B may correspond to a value obtained by multiplying the voltage induced on the primary side of the detector 120B2 by the winding ratio of the second wire L12 on the primary side and the secondary side. According to the embodiment of FIG. 45, G1=+G2 can be satisfied.

[0475] The first amplifier 131B may output a first output voltage V1 corresponding to a value obtained by multiplying the input voltage Vsen1 of the first amplifier 131B by the voltage gain G1 of the first amplifier 131B. The second amplifier 132B may output a second output voltage V2 corresponding to a value obtained by multiplying the differential input voltage Vsen2 of the second amplifier 132B by the voltage gain G2 of the second amplifier 132B. The first output voltage V1 and the second output voltage V2 are potentials based on the reference potential 2 of the amplifiers 131B and 132B. The difference between the first output voltage V1 and the second output voltage V2 may be the input voltage of the compensation transformer 190B.

[0476] 44 and 45, the compensation transformer 190B may have a structure in which a primary side electric wire and a secondary side electric wire pass through one core or are wound at least once. The primary side electric wire may be an electric wire connecting the output end of the first amplifier 131B and the output end of the second amplifier 132B. The secondary side electric wire may correspond to the large current paths 111 and 112.

[0477] The potential difference between the output of the first amplifier 131B and the output of the second amplifier 132B becomes the voltage on the primary side of the compensation transformer 190B, and the compensation transformer 190B supplies a compensation voltage V inj1 can be generated.

[0478] The compensating voltage V induced on the secondary side of the compensating transformer 190B inj1 may correspond to a value obtained by multiplying the potential difference between the output of the first amplifier unit 131B and the output of the second amplifier unit 132B by the winding ratio of the primary side and the secondary side.

[0479] The compensation devices 106B1 and 106B2 according to an embodiment provide voltage compensation V inj1 This provides an effect equivalent to the effect of increasing the inductance of the CM chokes of the detection units 120B1 and 120B2, and can provide an effect of suppressing the noise current In (L boost type).

[0480] Meanwhile, the compensation devices 106B1 and 106B2 according to an embodiment may further include a decoupling capacitor section 170B.

[0481] According to one embodiment, the decoupling capacitor section 170B may be disposed between the detection sections 120B1 and 120B2 and the first device 300. The decoupling capacitor section 170B may be composed of two Y-capacitors, one end of which is connected to the reference potential 1 and the other end of which is connected to the large current paths 111 and 112, respectively.

[0482] Fig. 46 is a schematic diagram showing a system configuration including an active compensation device 106D according to another embodiment of the present invention. Fig. 46 is a schematic diagram showing a configuration in which various compensation devices (e.g., 106) as described above are used in a three-phase, three-wire system.

[0483] Compensator 106D in Fig. 46 differs from compensator 106 for a single-phase two-wire system described with reference to Fig. 40 in that it is used in a three-phase three-wire system. Therefore, overlapping points will be omitted and the following description will focus on the differences.

[0484] In comparison with the above-described compensation device 106 (see FIG. 40), the compensation device 106D includes three large current paths 111D, 112D, and 113D, which results in a difference in the primary side of the detection unit 120D and the secondary side of the compensation unit 160D.

[0485] According to an embodiment, the first high current path 111D may be an R-phase power line, the second high current path 112D may be an S-phase power line, and the third high current path 113D may be a T-phase power line. The noise current In may be input in a common mode to each of the first high current path 111D, the second high current path 112D, and the third high current path 113D.

[0486] The primary side of the detector 120D may be disposed on the first large current path 111D, the second large current path 112D, and the third large current path 113D, respectively.

[0487] The secondary side of the detection unit 120D may output in parallel a first output corresponding to the input of the first amplification unit 131D, a second output corresponding to the input of the second amplification unit 132D, and a third output corresponding to the input of the Nth amplification unit 133D.

[0488] The input signal to the primary side of the compensation unit 160D may be based on the output signals output from the above-mentioned first, second and Nth amplifier units 131D, 132D and 133D, respectively.

[0489] Compensation section 160D may correspond to compensation transformer 140A and compensation capacitor section 150A, which perform current compensation as described above, or compensation section 160D may correspond to compensation transformer 190B, which performs voltage compensation as described above.

[0490] The secondary side of compensation unit 160D may be disposed in each of first large current path 111D, second large current path 112D, and third large current path 113D.

[0491] According to an embodiment, the compensation unit 160D may generate compensation voltages (i.e., secondary voltages) in series for each of the three large current paths 111D, 112D, and 113D based on the voltages (i.e., primary voltages) output from the first and second amplifier units 131D and 132D, respectively. In this case, for example, the compensation unit 160D may include a compensation transformer (e.g., 190B).

[0492] According to another embodiment, the compensation unit 160D may inject a compensation current into each of the first large current path 111D, the second large current path 112D, and the third large current path 113D based on an induced current generated based on the currents output from the first, second, and Nth amplifier units 131D, 132D, and 133D, respectively, or may extract a compensation current to the reference potential 1. In this case, for example, the compensation unit 160D may include a compensation transformer (e.g., 140A1) and a compensation capacitor unit (e.g., 150A).

[0493] Such an embodiment of the active compensation device 106D may compensate for common mode noise on the power lines of a three-phase, three-wire power system.

[0494] The compensation device 106D including multiple parallel amplifiers may be adapted or modified for a three-phase, four-wire power system (see FIG. 12). The description of the compensation device for the three-phase, four-wire power system may correspond to the description with reference to FIG.

[0495] Fig. 47 shows a schematic configuration of a system including an active compensation device 106F according to an embodiment of the present invention. As mentioned above as another example in the explanation of Fig. 40, the active compensation device 106F is an embodiment of a type that detects noise at the front end on the power supply side and returns to the rear end to perform compensation.

[0496] FIG. 48 generally illustrates a compensation device 106F1 as one example of the active compensation device 106F shown in FIG. 47, and FIG. 49 generally illustrates a compensation device 106F2 as another example of the active compensation device 106F shown in FIG. 47.

[0497] 47, the compensation device 106F may include a detection unit 120F, a first amplification unit 135F, a second amplification unit 136F, and a compensation unit 160F. With reference to FIGS. 48 and 49, the compensation unit 160F may include a compensation transformer 140F and a compensation capacitor unit 150F.

[0498] The detection unit 120F may detect the noise current In on the large current paths 111 and 112, and output an output signal based on the noise current In to the first and second amplification units 135F and 136F, respectively. The detection unit 120F may output a first output signal and a second output signal based on the noise current In, and the first output signal may be input to the first amplification unit 135F, and the second output signal may be input to the second amplification unit 136F.

[0499] 48 and 49, the detection unit 120F may have a configuration in which a secondary electric wire is wound in an overlapping manner around a CM choke around which the first large current path 111 and the second large current path 112 are wound. The primary sides of the detection units 120F1 and 120F2 may be windings in which the first large current path 111 and the second large current path 112 are wound around a CM choke, respectively.

[0500] On the other hand, in one embodiment (see FIG. 48), a single electric wire may be wound around the CM choke on the secondary side of the detection unit 120F1. The single electric wire may be connected in parallel to the input terminal of the first amplifier unit 135F and the input terminal of the second amplifier unit 136F.

[0501] In this case, for example, the voltage Vsen induced on the secondary side of the detection unit 120F1 may be input equally to the first amplifier unit 135F and the second amplifier unit 136F. According to an embodiment, when the voltage gain of the first amplifier unit 135F is G5 and the voltage gain of the second amplifier unit 136F is G6, G5=-G6 may be satisfied. The difference between the output voltage of the first amplifier unit 135F and the output voltage of the second amplifier unit 136F may be the input voltage of the compensation unit 160F. That is, it may be the input voltage of the compensation transformer 140F.

[0502] On the other hand, in another embodiment (see FIG. 49), on the secondary side of the detection unit 120F2, a first electric wire L31 connected in parallel to the input terminal of the first amplifier unit 135F and a second electric wire L32 connected in parallel to the input terminal of the second amplifier unit 136F may be wound in a layered manner around the above-mentioned CM choke.

[0503] For example, the voltage Vsen1 induced in the first electric wire L31 on the secondary side of the detection unit 120F2 may be differentially input to the first amplification unit 135F, and the voltage Vsen2 induced in the second electric wire L32 in the secondary side of the detection unit 120F2 may be differentially input to the second amplification unit 136F.

[0504] According to an embodiment, the first wire L31 and the second wire L32 may be wound to generate input voltages having similar magnitudes and opposite phases to the first amplifier unit 135F and the second amplifier unit 136F. For example, when the number of turns of the first wire L21 and the second wire L22 on the secondary side are similar, Vsen1=-Vsen2 may be satisfied. Also, when the voltage gain of the first amplifier unit 135F is G5 and the voltage gain of the second amplifier unit 136F is G6, G5=+G6 may be satisfied. The difference between the output voltage of the first amplifier unit 135F and the output voltage of the second amplifier unit 136F may be the input voltage of the compensation unit 160F. That is, it may be the input voltage of the compensation transformer 140F.

[0505] On the other hand, referring again to both Figures 48 and 49, the compensating transformer 140F generates an induced voltage V inj2 The voltage V converted through the compensation transformer 140F can be generated. inj2 may draw the compensation current Ic from the large current paths 111 and 112 (for example, power lines) through the compensation capacitor unit 150F.

[0506] On the other hand, the compensation devices 106F, 106F1, 106F2 shown in FIGS. 47, 48, and 49 can of course also be applied to the three-phase three-wire system as shown in FIG. 46, and the three-phase four-wire system.

[0507] According to an embodiment of the present invention, the noise that can be accommodated and compensated for by the compensation device (e.g., 106, 106A1, 106B, 106D, 106F, etc.) may be increased. For example, for the same DC voltage supply (e.g., the voltage supply of the third device 400), the noise current that can be accommodated and compensated for by the active compensation device may be increased by utilizing parallel amplifiers.

[0508] According to an embodiment of the present invention, when detecting and compensating for the same noise, the stress on the amplifier unit can be reduced. Specifically, multiple parallel amplifier units can be used to increase the maximum noise tolerance within a limited DC voltage (e.g., the supply voltage of the third device 400).

[0509] Furthermore, the compensation devices according to various embodiments (e.g., 106, 106A1, 106B, 106D, 106F, etc.) may have a very small increase in size and cost when used for high power applications, unlike when a CM choke is used alone.

[0510] 50 is a schematic diagram showing a configuration of a system including a compensation device 107 according to an embodiment of the present invention. The compensation device 107 may actively compensate for a current In (e.g., an EMI noise current) and a voltage Vn (e.g., an EMI noise voltage) that are generated in a common mode (CM) on two or more large current paths 111 and 112 from a first device 300.

[0511] 50, the compensation device 107 may include a detection unit 120, an amplification unit 139, a first compensation unit 190, and a second compensation unit 160. The amplification unit 139 may include a first amplification unit 137 and a second amplification unit 138.

[0512] For example, the detection unit 120 may correspond to the detection unit described above (e.g., 120, 120A, etc.), the first compensation unit 190 may correspond to the compensation transformer 190B described in Figures 43 to 45, and the second compensation unit 160 may also correspond to the compensation unit described above (e.g., 160, 160A, etc.), but duplicate explanations will be omitted as much as possible.

[0513] The explanation of the noise current In and the noise voltage Vn replaces the explanation of the noise current and the noise voltage explained in FIG.

[0514] The two or more large current paths 111 and 112 may be paths along which a noise current In from the first device 300 is transmitted to the second device 200. Alternatively, the two or more large current paths 111 and 112 may be paths along which a noise voltage Vn is generated relative to the ground (for example, the reference potential 1).

[0515] The noise current In or the noise voltage Vn may be input to each of the two or more large current paths 111 and 112 in a common mode.

[0516] In the drawings, the noise current In and noise voltage Vn are illustrated between the node where the second compensation section 160 and the high current paths 111 and 112 meet and the detection section 120, however, in this specification the terms “noise current” and “noise voltage” are not limited to this and can refer to voltages and currents that have a first frequency and can be generated in common mode throughout the high current paths 111 and 112.

[0517] On the other hand, the two or more high current paths 111 and 112 may include two paths as shown in FIG. 1, or may include three paths (e.g., a three-phase three-wire power system) or four paths (e.g., a three-phase four-wire power system).

[0518] The detection unit 120 may detect the noise current In on two or more large current paths 111 and 112, and generate an output signal corresponding to the noise current In on the amplification unit 139 side.

[0519] At least a part of the large current paths 111 and 112 may pass through the detection unit 120 in order to detect the noise current In, but a portion of the detection unit 120 where an output signal is generated by detection may be insulated from the large current paths 111 and 112. For example, the detection unit 120 may have a form in which an electric wire on the amplifier unit 139 side is wound around a CM choke around which a power line corresponding to the large current paths 111 and 112 is wound. However, the present invention is not limited to this.

[0520] According to one embodiment, the detection unit 120 may detect the noise current In on the high current paths 111 and 112, and generate an output signal to the first amplifier unit 137 and the second amplifier unit 138. The output signal may correspond to a voltage between nodes a and b. The nodes a and b may be differentially connected to the input terminal of the first amplifier unit 137 and may also be differentially connected to the input terminal of the second amplifier unit 138. Thus, the voltage between nodes a and b may be input as an input voltage to the first amplifier unit 137 and the second amplifier unit 138.

[0521] The first amplifier 137 and the second amplifier 138 may each amplify the above-mentioned input voltage and output a different output signal (e.g., output voltage). In this case, the gain (e.g., voltage gain) of the first amplifier 137 and the gain (e.g., voltage gain) of the second amplifier 138 may be different.

[0522] The amplified voltage V1 output from the first amplifier section 137 becomes an input signal to the first compensation section 190, and the first compensation section 190 may generate compensation voltages in series on the large current paths 111 and 112 based on the above V1.

[0523] The amplified voltage V2 output from the second amplifier 138 becomes an input signal to the second compensation unit 160. The second compensation unit 160 may flow a compensation current from the large current paths 111 and 112 to the reference potential 1 based on the above V2, thereby reducing the noise current In.

[0524] Although the first amplifier unit 137 and the second amplifier unit 138 are expressed separately according to their functions, according to one embodiment, the first amplifier unit 137 and the second amplifier unit 138 may be realized in a single IC.

[0525] Meanwhile, the first compensation section 190 and the second compensation section 160 may each include a compensation transformer to insulate the high current paths 111 and 112, the first amplifier section 137, and the second amplifier section 138.

[0526] The first compensating unit 190 is a type of compensating unit that compensates for the voltage before or after the CM choke in response to the noise input from the first device 300. The second compensating unit 160 is a type of compensating unit that returns the noise to the rear end.

[0527] The first compensation unit 190 may generate a compensation voltage in series on the large current paths 111 and 112 based on the amplified voltage output from the amplifier 139. For example, the first compensation unit 190 may be composed of a compensation transformer for insulation. The compensation voltage can have the effect of suppressing the noise current In flowing on the large current paths 111 and 112.

[0528] The second compensation unit 160 may generate a compensation current based on the output signal amplified by the amplifier unit 139 and output to the second compensation unit 160 side. The second compensation unit 160 may be connected to the large current paths 111 and 112, respectively, so that the compensation current flows from the large current paths 111 and 112 to the reference potential 1. For example, the second compensation unit 160 may branch the above compensation current from the large current paths 111 and 112. This may compensate for the noise current In flowing on the large current paths 111 and 112. For example, the second compensation unit 160 may include a compensation transformer for insulation. The above compensation current may flow at least a part of the noise current In to ground (for example, the reference potential 1) to reduce the noise current In.

[0529] The compensation device 107 according to various embodiments of the present invention as described above may be a combined voltage compensation and current compensation structure. For example, the first compensation unit 190 may perform voltage compensation, and at the same time, the second compensation unit 160 may perform current compensation.

[0530] FIG. 51 shows a more specific example of the embodiment shown in FIG. 50, and shows a schematic diagram of a compensation device 107B according to an embodiment of the present invention.

[0531] Referring to FIG. 51, the compensation device 107B includes a detection transformer 120B, a first amplifier section 137B, and a second amplifier section 138B, which may correspond to the detection section 120, the first amplifier section 137, and the second amplifier section 138, respectively, described above.

[0532] Additionally, the compensation device 107B includes a first compensation transformer 190B disposed on the output side of the first amplifier section 137B, which may correspond to the first compensation section 190 described above.

[0533] Moreover, the compensation device 107B includes a second compensation transformer 140B and a compensation capacitor section 150B arranged on the output side of the second amplifier section 138B, and these two components are combined and correspond to the above-mentioned second compensation section 160. Therefore, an attempt is made to omit a description of common contents as much as possible.

[0534] The detection transformer 120B may include a primary side 121 disposed on the large current paths 111 and 112, and a secondary side 122 differentially connected to the input terminals of the amplifier parts 137B and 138B.

[0535] According to an embodiment of the present invention, the detection transformer 120B may be formed by overlapping and winding the electric wire of the secondary side 122 around the CM choke around which the first high current path 111 and the second high current path 112 are wound. When the detection transformer 120B is formed using the CM choke in this manner, the detection transformer 120B can function not only as a detection and a transformation but also as a passive filter as a CM choke. That is, when the detection transformer 120B is formed by overlapping and winding the electric wire of the secondary side 122 around the CM choke, the detection transformer 120B may simultaneously perform the role of suppressing or blocking the noise current In as well as detecting and transforming the noise current In. Meanwhile, the compensation devices 107, 107B, 107C1, and 107C2 according to various embodiments of the present invention are added together with the above-mentioned CM choke, and the common mode noise voltage and current can be effectively reduced even in a high-power system without increasing the size or number of the CM choke.

[0536] For example, in the detection transformer 120B, the winding ratio of the primary side 121 and the secondary side 122 is 1:N. sen and the noise current I n The voltage induced across the primary side 121 of the detection transformer 120B is V choke That is, the voltage V induced on the secondary side 122 is sen V choke N sen It is double. JPEG2025016641000013.jpg12170

[0537] For example, the secondary side 122 of the detection transformer 120B is differentially connected in parallel to the input terminal of the first amplifier unit 137B and the input terminal of the second amplifier unit 138B, and an induced voltage V sen may be supplied.

[0538] Each of the first amplifier 137B and the second amplifier 138B detects an induced voltage V induced on the secondary side 122 of the detection transformer 120B. sen may each be amplified (eg, adjusted in magnitude and / or phase).

[0539] The voltage gain G1 of the first amplifying unit 137B and the voltage gain G2 of the second amplifying unit 138B may be different from each other. According to an embodiment of the present invention, the voltage gain G2 of the second amplifying unit 138B may be designed to be larger than the voltage gain G1 of the first amplifying unit 137B. A detailed description of this will be given later. However, this is not limited thereto, and G1 and G2 may be determined based on various embodiments.

[0540] The output voltage V1 of the first amplifier unit 137B can be expressed as in Equation 10 below. JPEG2025016641000014.jpg10170

[0541] The output voltage V1 of the first amplifier 137B becomes the input voltage of the first compensation transformer 190B (i.e., the voltage of the primary side 191). The first compensation transformer 190B outputs a compensation voltage V inj1 may be generated.

[0542] First compensation transformer 190B may have a structure in which, for example, an electric wire of primary side 191 and an electric wire of secondary side 192 pass through one core or are wound at least once around one core. The electric wire of primary side 191 is an electric wire through which an output signal of first amplifier 137B flows, and the electric wire of secondary side 192 may correspond to large current paths 111 and 112.

[0543] For example, in the first compensation transformer 190B, the winding ratio of the primary side 191 and the secondary side 192 is 1:N. inj1 Then, the voltage V induced on the secondary side 192 is inj1 is the N of V1 inj1 Therefore, the compensation voltage V inj1 can be expressed as in Equation 11. JPEG2025016641000015.jpg19170

[0544] On the other hand, if the voltage gain of the second amplifier unit 138B is G2, the output voltage V2 of the second amplifier unit 138B can be expressed as in the following formula 12. JPEG2025016641000016.jpg10170 The output voltage V2 of the second amplifier section 138B becomes the input voltage of the second compensation section 160, i.e., the input voltage of the second compensation transformer 140B.

[0545] A configuration in which the second compensation transformer 140B and the compensation capacitor unit 150B are combined may correspond to the above-mentioned second compensation unit 160. The second compensation transformer 140B may be a means for generating, on the secondary side of the second compensation transformer 140B, a compensation current Icy to be branched from the high current paths 111 and 112 while being insulated from the high current paths 111 and 112.

[0546] The second compensation transformer 140B may induce an induced voltage V3 on the secondary side based on the amplified voltage V2 generated on the primary side. For example, in the second compensation transformer 140B, the winding ratio of the primary side and the secondary side is 1:N. inj2 Then, the voltage V3 induced on the secondary side is N of V2. inj2 Therefore, the induced voltage V3 can be expressed as in Equation 13. JPEG2025016641000017.jpg19170

[0547] The secondary side of second compensation transformer 140B may be disposed on a path connecting compensation capacitor section 150B, which will be described later, and a reference potential (reference potential 1) of compensation device 107B.

[0548] The compensation capacitor unit 150B may draw a compensation current Icy from the power line based on the voltage V3 induced by the second compensation transformer 140B. The compensation current Icy compensates (or cancels) the noise current on the large current paths 111 and 112, thereby allowing the compensation device 107B to reduce noise.

[0549] On the other hand, the common mode noise voltage at the node where the compensation capacitor unit 150B and the large current paths 111 and 112 are connected is V n and the voltage between the first compensation transformer 190B and the second device 200 is V LISN And V n and V LISN Solving the circuit equation between V and V gives the following equation 14. n and V LISN may denote a potential relative to a reference potential 1 (eg, ground). JPEG2025016641000018.jpg6170JPEG2025016641000019.jpg24170

[0550] On the other hand, the noise radiated to the second device 200 side by the operation of the compensation device 107B must be approximately equal to 0. Therefore, V LISN should be equal to 0, and the following Equation 15 can be derived: JPEG2025016641000020.jpg30170

[0551] Using this, the effective impedance of the large current paths 111 and 112 between the detection transformer 120B and the compensation capacitor unit 150B can be calculated as shown in Equation 16. JPEG2025016641000021.jpg25170

[0552] JPEG2025016641000022.jpg22170

[0553] This may be an effect of the first amplifier 137 (e.g., the first amplifier 137B) and the first compensation unit 190 (e.g., the first compensation transformer 190B). The first amplifier 137 and the first compensation unit 190 may perform voltage compensation Vinj1 on the large current path, which has an effect equivalent to the effect of increasing inductance, and can suppress noise current from flowing (L boost type).

[0554] JPEG2025016641000023.jpg23170JPEG2025016641000024.jpg10170

[0555] For example, the above noise suppression effect can be achieved by adjusting the voltage gain G1 of the first amplifier 137B, the turns ratio N sen , and the turns ratio N inj1 can be adjusted accordingly.

[0556] On the other hand, the node V n Solving the circuit equation between the reference potential 1 gives us equation 18. JPEG2025016641000025.jpg6170JPEG2025016641000026.jpg19170

[0557] Here, C yis the capacitance of the Y-capacitor included in the compensation capacitor unit 150B. On the other hand, by utilizing this, the node V n The effective Y-impedance Z seen toward the compensation capacitor section 150B is cy、eff can be calculated as in Equation 19. JPEG2025016641000027.jpg31170

[0558] The above formula 19 is V choke In Equation 19, 1 / (s*Cy) represents the impedance of the Y-capacitor included in the compensation capacitor section 150B. Z cy、eff indicates the effective Y− impedance seen toward compensation capacitor section 150B at the node where compensation capacitor section 150B and large current paths 111 and 112 meet.

[0559] JPEG2025016641000028.jpg19170

[0560] This may be an effect of the second amplifier unit 138 (e.g., the second amplifier unit 138B) and the second compensation unit 160 (e.g., the first compensation transformer 140B and the compensation capacitor unit 150B). The second amplifier unit 138 and the second compensation unit 160 are of a feedback type and can perform current compensation Icy so that the noise current is diverted from the large current path, which has an effect equivalent to the effect of increasing the Y-capacitance, and can effectively draw out the noise to the ground (i.e., reference potential 1) (C boost type).

[0561] JPEG2025016641000029.jpg24170JPEG2025016641000030.jpg17170

[0562] For example, the above noise extraction effect is caused by the voltage gain G1 of the first amplifier 137B, the voltage gain G2 of the second amplifier 138B, the turns ratio N inj1, and the turns ratio N inj2 It may be adjusted accordingly.

[0563] For example, in the first compensation transformer 190B, the wires of the primary side 191 may pass through a core, and the wires of the secondary side 192 (i.e., the high current paths 111 and 112) may pass through the core or be formed into a single turn.

[0564] 52 and 53 show schematic diagrams of compensation devices 107C1 and 107C2 according to an embodiment of the present invention, as a specific example of the compensation device shown in FIG.

[0565] The compensation device 107C1 according to one embodiment shown in FIG. 52 may include a detection transformer 120C, a first amplifier 137C, a second amplifier 138C, a first compensation transformer 190C1, a second compensation transformer 140C, and a compensation capacitor section 150C.

[0566] The compensation device 107C1 is an embodiment in which the primary wire and the secondary large current paths 111 and 112 of the first compensation transformer 190C1 pass through a core, and the winding ratio N inj1 The winding ratio N may be about 1. However, the present invention is not limited to this. For example, the secondary large current paths 111 and 112 may be wound around the core once. In this case, the winding ratio N inj1 can be about 2.

[0567] The detection transformer 120C, first amplifier 137C, second amplifier 138C, first compensation transformer 190C1, second compensation transformer 140C, and compensation capacitor section 150C in Figure 52 correspond to the detection transformer 120B, first amplifier 137B, second amplifier 138B, first compensation transformer 190B, second compensation transformer 140B, and compensation capacitor section 150B described in Figure 51, so duplicated content will be omitted.

[0568] Referring to FIG. 52, in a compensation device 107C1 according to an embodiment of the present invention, the detection transformer 120C may be a different type of element from the first compensation transformer 190C1 and the second compensation transformer 140C.

[0569] For example, unlike the first compensation transformer 190C1 and the second compensation transformer 140C which only function as a transformer, the detection transformer 120C may be configured in such a manner that the electric wires on the amplifier units 137C and 138C side are wound in an overlapping manner around a CM choke around which the power lines corresponding to the large current paths 111 and 112 are wound. The CM choke may be a passive filter that uses inductance to suppress noise currents, and the detection transformer 120C may detect noise by simply winding the secondary side electric wires in an overlapping manner around the above-mentioned CM choke.

[0570] On the other hand, the compensation device 107C2 of one embodiment shown in FIG. 53 may include a detection transformer 120C, a first amplifier 137C, a second amplifier 138C, a first compensation transformer 190C2, a second compensation transformer 140C, and a compensation capacitor section 150C.

[0571] The compensation device 107C2 according to an embodiment may actively compensate for the noise current In or noise voltage Vn generated in the large current paths 111 and 112 in common mode.

[0572] The detection transformer 120C, first amplifier 137C, second amplifier 138C, first compensation transformer 190C2, second compensation transformer 140C, and compensation capacitor section 150C included in compensation device 107C2 may correspond to the descriptions of the detection transformer 120B, first amplifier 137B, second amplifier 138B, first compensation transformer 190B, second compensation transformer 140B, and compensation capacitor section 150B described in FIG. 51.

[0573] In one embodiment of the compensation device 107C2, the first compensation transformer 190C2 may be placed after the detection transformer 120C (e.g., the CM choke) on the first device 300 side relative to the detection transformer 120C. The first compensation transformer 190C2 applies a compensation voltage V inj1 may occur.

[0574] FIG. 54 shows a schematic configuration of a system including a compensation device 107D according to another embodiment of the present invention. FIG. 54 is a schematic diagram showing a configuration in which various compensation devices such as those described above (eg, 107, 107B, 107C1, etc.) are used in a three-phase, three-wire system.

[0575] Compensation device 107D in Fig. 54 differs from compensator 107B for a single-phase two-wire system described with reference to Fig. 51 in that it is used in a three-phase three-wire system. Therefore, overlapping points will be omitted and the following description will focus on the differences.

[0576] Referring to FIG. 54, the compensation device 107D may actively compensate for the noise current In input in common mode to each of the large current paths 111D, 112D, and 113D connected to the first device 300D.

[0577] The compensation device 107D may include a first large current path 111D, a second large current path 112D, and a third large current path 113D that are distinct from one another. According to an embodiment, the first large current path 111D may be an R-phase power line, the second large current path 112D may be an S-phase power line, and the third large current path 113D may be a T-phase power line. The noise current In may be input in a common mode to each of the first large current path 111D, the second large current path 112D, and the third large current path 113D.

[0578] The primary side 121D of the sensing transformer 120D may be disposed in each of the first large current path 111D, the second large current path 112D, and the third large current path 113D, and may generate an induced voltage Vsen on the secondary side 122D.

[0579] On the other hand, in the compensation device 107D, the first and second amplifier units 137D and 138D correspond to the amplifier units 137B and 138B.

[0580] The first amplifying section 137D may output an amplified voltage V1 based on an input voltage, and the second amplifying section 138D may output an amplified voltage V2 based on the above-mentioned input voltage.

[0581] V1 may be the input voltage of the first compensation transformer 190D, i.e., the voltage on the primary side 191D of the first compensation transformer 190D. V2 may be the input voltage of the second compensation transformer 140D, i.e., the voltage on the primary side of the second compensation transformer 140D.

[0582] On the other hand, the secondary side 192D of the first compensation transformer 190D may be disposed in each of the first large current path 111D, the second large current path 112D, and the third large current path 113D. The first compensation transformer 190D outputs a compensation voltage V in series to each of the three large current paths 111D, 112D, and 113D that are the secondary side 192D based on the voltage V1 of the primary side 191D output by the first amplifier unit 137D. inj1 may be generated.

[0583] Meanwhile, the second compensation transformer 140D and the compensation capacitor unit 150D are included in the second compensation unit 160D, and the output voltage V2 of the second amplifier unit 138D may become the input voltage of the second compensation unit 160D, i.e., the voltage of the primary side 191D of the second compensation transformer 140D. The second compensation transformer 140D may generate an induced voltage V3 on the secondary side based on the voltage V2 on the primary side.

[0584] The compensation capacitor section 150D ensures that the compensation current Ic from each of the first large current path 111D, the second large current path 112D, and the third large current path 113D is drawn to the reference potential 1 based on the induced voltage V3 on the secondary side of the second compensation transformer 140D.

[0585] Compensation device 107D according to such an embodiment may simultaneously perform voltage compensation and current compensation for common mode noise on the power lines of a three-phase, three-wire power system.

[0586] The compensation device 107D including the first and second amplifiers 137D and 138D and the first and second compensation units 190D and 160D may be adapted or modified for a three-phase, four-wire power system (see FIG. 12). The description of the compensation device for the three-phase, four-wire power system may correspond to the description with reference to FIG. 12. FIG. 55 illustrates an outline of the functional configuration of an active compensation device 106E according to another embodiment of the present invention.

[0587] FIG. 56 generally illustrates an active compensation device 106E1 as one example of the active compensation device 106E shown in FIG. 55, and FIG. 57 generally illustrates an active compensation device 106E2 as another example of the active compensation device 106E shown in FIG. 55.

[0588] Furthermore, each component of the compensation devices 106E, 106E1, and 106E2 may at least partially correspond to each component of the compensation device described above, so that details that are obvious in light of the above-described embodiment will be omitted.

[0589] Referring to FIG. 55, the active compensation device 106E may include a detection section 120E, first, second, third and fourth amplification sections 131E, 132E, 133E and 134E, a first compensation section 190E and a second compensation section 160E.

[0590] The detection unit 120E may correspond to the description of the detection unit 120 as an example of the detection unit 120 described above. The detection unit 120E may output an output signal based on the noise current In to the first, second, third, and fourth amplifiers 131E, 132E, 133E, and 134E. For example, the detection unit 120E may output four output signals corresponding to the amplifiers 131E, 132E, 133E, and 134E based on the noise current In. Each of the four output signals may be input to the first, second, third, and fourth amplifiers 131E, 132E, 133E, and 134E, respectively.

[0591] For example, the first and second amplifier units 131E and 132E are configured to generate an input signal for the first compensation unit 190E, and the third and fourth amplifier units 133E and 134E are configured to generate an input signal for the second compensation unit 160E.

[0592] According to an embodiment, the input terminal of the first amplifying unit 131E and the input terminal of the third amplifying unit 133E may be connected in parallel with each other. For example, the differential input voltage of the first amplifying unit 131E and the differential input voltage of the third amplifying unit 133E may be the same with each other. Meanwhile, the output signal (e.g., current or voltage) of the first amplifying unit 131E and the output signal (e.g., current or voltage) of the third amplifying unit 133E may be different depending on the respective gains of the first amplifying unit 131E and the third amplifying unit 133E. Meanwhile, the output signal of the first amplifying unit 131E may be connected to the input side of the first compensating unit 190E, and the output signal of the third amplifying unit 133E may be connected to the input side of the second compensating unit 160E.

[0593] According to an embodiment, the input terminal of the second amplifying unit 132E and the input terminal of the fourth amplifying unit 134E may be connected in parallel with each other. For example, the differential input voltage of the second amplifying unit 132E and the differential input voltage of the fourth amplifying unit 134E may be the same as each other. Meanwhile, the output signal (e.g., current or voltage) of the second amplifying unit 132E and the output signal (e.g., current or voltage) of the fourth amplifying unit 134E may be different depending on the respective gains of the second amplifying unit 132E and the fourth amplifying unit 134E. Meanwhile, the output signal of the second amplifying unit 132E may be connected to the input side of the first compensating unit 190E, and the output signal of the fourth amplifying unit 134E may be connected to the input side of the second compensating unit 160E.

[0594] According to one embodiment, the difference between the output voltage V11 of the first amplifier unit 131E and the output voltage V12 of the second amplifier unit 132E may correspond to the input voltage of the first compensation unit 190E. According to one embodiment, the difference between the output voltage V13 of the second amplifier unit 133E and the output voltage V14 of the fourth amplifier unit 134E may correspond to the input voltage of the second compensation unit 160E.

[0595] On the other hand, the output voltages V11, V12, V13, and V14 of the amplifiers 131E, 132E, 133E, and 134E may indicate voltages based on the reference potential 2 of the amplifiers 131E, 132E, 133E, and 134E.

[0596] According to an embodiment, the first compensation unit 190E may induce a compensation voltage in series on the large current paths 111 and 112 based on a difference between the output voltage V11 of the first amplifier unit 131E and the output voltage V12 of the second amplifier unit 132E. The compensation voltage generated in series on the large current paths 111 and 112 can have an effect of suppressing the noise current In flowing on the large current paths 111 and 112.

[0597] According to one embodiment, the second compensation unit 160E may draw a compensation current at ground (e.g., reference potential 1) from the high current paths 111 and 112 based on the difference between the output voltage V13 of the third amplifier unit 133E and the output voltage V14 of the fourth amplifier unit 134E. The compensation current may have the effect of reducing the magnitude of the noise current In flowing on the high current paths 111 and 112. A detailed description of the second compensation unit 160E will be provided later through Figures 56 and 57.

[0598] Active compensation devices 106E1 and 106E2, which are examples of the active compensation device 106E, will be described below with reference to FIGS. 56 and 57.

[0599] The amplifier units 131E, 132E, 133E, 134E, the first compensation transformer 190E1, the second compensation transformer 140E, and the compensation capacitor unit 150E of the compensation device 106E1 and the compensation device 106E2 may correspond to each other. Meanwhile, the above-mentioned first compensation unit 190E includes the first compensation transformer 190E1, and the second compensation unit 160E includes the second compensation transformer 140E and the compensation capacitor unit 150E.

[0600] According to one embodiment, the detector 120E1 of the compensation device 106E1 and the detector 120E2 of the compensation device 106E2 may be different from each other.

[0601] The detectors 120E1 and 120E2 of the compensation devices 106E1 and 106E2 according to an embodiment may have a configuration in which a secondary-side electric wire is wound in an overlapping manner around a CM choke around which the first large current path 111 and the second large current path 112 are wound.

[0602] The primary sides of the detection units 120E1 and 120E2 may be windings in which the first large current path 111 and the second large current path 112 are wound around a CM choke.

[0603] On the other hand, in one embodiment (see FIG. 56), a single electric wire may be wound around the CM choke on the secondary side of the detection unit 120E1. Any of the electric wires may be connected in parallel to the input terminals of the first, second, third, and fourth amplifier units 131E, 132E, 133E, and 134E. For example, the voltage V induced on the secondary side of the detection unit 120E1 may be sen may be input differentially to both input terminals of the first, second, third and fourth amplifier parts 131E, 132E, 133E and 134E, respectively.

[0604] In the embodiment of FIG. 56, for example, the voltage V induced on the secondary side of the detection unit 120E1 is sen may be input in the same manner to the first and third amplifier units 131E and 133E, and the second and fourth amplifier units 132E and 134E.

[0605] The first amplifier 131E receives a differential input voltage V sen The second amplifier 132E may output a first output voltage V11 corresponding to a value obtained by multiplying the differential input voltage V sen may be multiplied by the voltage gain G2 of the second amplifier unit 132E to output a second output voltage V12. The first output voltage V11 and the second output voltage V12 may be potentials based on a reference potential (reference potential 2) of the amplifier units 131E and 132E. The difference between the first output voltage V11 and the second output voltage V12 may be the input voltage of the first compensation transformer 190E1. According to one embodiment of FIG. 56, G1=-G2 can be satisfied.

[0606] The third amplifier 133E may output a third output voltage V13 corresponding to a value obtained by multiplying the differential input voltage Vsen of the third amplifier 133E by a voltage gain G3 of the third amplifier 133E. The fourth amplifier 134E may output a fourth output voltage V14 corresponding to a value obtained by multiplying the differential input voltage Vsen of the fourth amplifier 134E by a voltage gain G4 of the fourth amplifier 134E. The third output voltage V13 and the fourth output voltage V14 may be potentials based on a reference potential (reference potential 2) of the amplifiers 133E and 134E. The difference between the third output voltage V13 and the fourth output voltage V14 may be the input voltage of the second compensation transformer 140E. According to an embodiment of FIG. 56, G3=-G4 can be satisfied.

[0607] On the other hand, in another embodiment (see FIG. 57), on the secondary side of the detection unit 120E2, a first electric wire L21 connected in parallel to the input terminals of the first and third amplifier units 131E and 133E and a second electric wire L22 connected in parallel to the input terminals of the second and fourth amplifier units 132E and 134E may be wound in a lap around the above-mentioned CM choke.

[0608] For example, the voltage V induced in the first electric wire L21 in the secondary side of the detection unit 120E2 is sen1 may be differentially input to the first amplifier 131E and the third amplifier 133E, respectively. sen2 may be differentially input to the second amplifying section 132E and the fourth amplifying section 134E.

[0609] In the embodiment of FIG. 57, the input voltage V sen1 and V sen2 may be generated based on the number of turns of the first electric wire L21 on the secondary side of the detection unit 120E2 and the number of turns of the second electric wire L22 on the secondary side. According to one embodiment, the first electric wire L21 and the second electric wire L22 may be wound so as to generate input voltages of opposite phases to the first and third amplifier units 131E and 133E and the second and fourth amplifier units 132E and 134E.

[0610] For example, when the number of windings of the first electric wire L21 and the second electric wire L22 on the secondary side are the same, the differential input voltage V sen1 and V sen2 The input voltages V sen1 and V sen2 of the first and third amplifier units 131E and 133E may have similar magnitudes and opposite phases. That is, Vsen1=-Vsen2. For example, the input voltages V sen1 and V sen2 of the first and third amplifier units 131E and 133E may have similar magnitudes and opposite phases. sen1 may correspond to the voltage induced on the primary side of the detection unit 120E2 (i.e., across the CM choke) multiplied by the turns ratio of the first wire L21 to the primary side. sen2 may correspond to a value obtained by multiplying the voltage induced on the primary side of the detection unit 120E2 by the turns ratio of the second electric wire L12 to the primary side.

[0611] The first amplifier 131E receives the input voltage V sen1 The second amplifier 132E may output a first output voltage V11 corresponding to a value obtained by multiplying the differential input voltage Vsen2 of the second amplifier 132E by the voltage gain G1 of the second amplifier 132E. The third amplifier 133E may output a third output voltage V13 corresponding to a value obtained by multiplying the input voltage Vsen1 of the third amplifier 133E by the voltage gain G3 of the third amplifier 133E. The fourth amplifier 134E may output a fourth output voltage V14 corresponding to a value obtained by multiplying the differential input voltage Vsen2 of the fourth amplifier 134E by the voltage gain G4 of the fourth amplifier 134E. According to an embodiment of FIG. 57, G1=+G2 and G3=+G4 can be satisfied.

[0612] The output voltages V11, V12, V13, and V14 are potentials based on the reference potential 2 of the amplifiers 131E, 132E, 133E, and 134E. The difference between the first output voltage V11 and the second output voltage V12 may be the input voltage of the first compensation transformer 190E1. The difference between the third output voltage V13 and the fourth output voltage V14 may be the input voltage of the second compensation transformer 140E.

[0613] On the other hand, referring again to both Fig. 56 and Fig. 57, the first compensation transformer 190E1 may have a structure in which a primary side electric wire and a secondary side electric wire pass through one core or are wound at least once. The primary side electric wire may be an electric wire connecting the output terminal of the first amplifier unit 131E and the output terminal of the second amplifier unit 132E. The secondary side electric wire may correspond to the large current paths 111 and 112.

[0614] A potential difference (e.g., V11-V12) between the output of the first amplifying unit 131E and the output of the second amplifying unit 132E becomes a voltage on the primary side of the first compensating transformer 190E1, and the first compensating transformer 190E1 may generate a compensation voltage Vinj1 in series on the secondary side high current paths 111 and 112 based on the potential difference. The compensation voltage Vinj1 may correspond to a value obtained by multiplying the primary side voltage of the first compensating transformer 190E1 by a winding ratio of the primary side and the secondary side.

[0615] The active compensation devices 106E1 and 106E2 according to one embodiment can perform voltage compensation Vinj1 on the large current paths 111 and 112, which has an effect equivalent to the effect of increasing the inductance of the CM chokes of the detection units 120E1 and 120E2, and can suppress the noise current In (L boost type).

[0616] On the other hand, the second compensation transformer 140E and the compensation capacitor section 150E may correspond to the second compensation section 160E described above.

[0617] According to an embodiment, the second compensation transformer 140E may include a primary side (e.g., a primary winding) connected to the output terminals of the second and fourth amplifier units 132E and 134E, and a secondary side (e.g., a secondary winding) connected to the large current paths 111 and 112. For example, an electric wire connecting the output end of the second amplifier unit 132E and the output end of the fourth amplifier unit 134E may be wound on the primary side of the second compensation transformer 140E.

[0618] The second compensation transformer 140E may have a structure in which the primary wire and the secondary wire pass through one core or are wound at least one time around one core.

[0619] The secondary side of the second compensation transformer 140E may be disposed on a path connecting the compensation capacitor section 150E and the reference potential (reference potential 1) of the compensation devices 106E1 and 106E2.

[0620] The voltage on the primary side of the second compensation transformer 140E may be a potential difference (e.g., V13-V14) between the output of the third amplifier 133E and the output of the fourth amplifier 134E. The second compensation transformer 140E may generate an induced voltage Vinj2 on the secondary side based on the above-mentioned primary side voltage (e.g., V13-V14) and a winding ratio. The induced voltage Vinj2 may correspond to the product of the above-mentioned primary side voltage (e.g., V13-V14) and a winding ratio.

[0621] The voltage Vinj2 transformed through the second compensation transformer 140E may draw a compensation current Ic from the large current paths 111 and 112 (eg, power lines) through a compensation capacitor section 150E.

[0622] The compensation capacitor unit 150E may draw a compensation current Ic from the power line based on the voltage Vinj2 induced by the second compensation transformer 140E. The compensation current Ic compensates (or cancels) the noise current on the large current paths 111 and 112, so that the compensation devices 106E1 and 106E2 can reduce noise.

[0623] FIG. 58 is a diagram showing a schematic configuration of a system including a compensation device 108 according to an embodiment of the present invention.

[0624] The remaining configuration of the compensation device 108 may correspond to the configuration described in the embodiments described in FIG. 2 or above, but the specific configuration of the detection unit 820 of the compensation device 108 is different from the detection unit 120 described in the embodiments described in FIG. 2 or above, and therefore a different reference number is given. Therefore, the configuration corresponding to the above-mentioned embodiment will be described briefly.

[0625] The compensation device 108 according to one embodiment of the present invention may actively reduce the first currents I11 and I12, or noise currents, input in common mode to at least two or more high current paths 111 and 112 connected to the first device 300.

[0626] On the other hand, the two or more high current paths 111 and 112 may include two paths as shown in FIG. 58, may include three paths (e.g., three-phase three-wire) as shown in FIG. 64, or may include four paths (e.g., three-phase four-wire).

[0627] The detection unit 820 may generate a detection voltage based on a noise voltage corresponding to the first currents I11 and I12 on the high current paths. To this end, the detection unit 820 may be electrically connected to each of the high current paths 111 and 112. In other words, the detection unit 820 may mean a means for sensing the first currents I11 and I12 on the high current paths 111 and 112.

[0628] According to an embodiment, the detection unit 820 may be differentially connected to an input terminal of the amplification unit 130, which will be described later.

[0629] The amplifier 130 may be electrically connected to the detector 820, and may amplify the detection signal output by the detector 820 to generate an amplified signal.

[0630] By the amplification of the amplifier unit 130, the compensation device 108 may amplify the noise voltage corresponding to the first currents I11 and I12 and adjust the magnitude of the first current absorbed from the compensation capacitor unit. In other words, the compensation device 108 may reduce the effective impedance of the capacitor of the compensation capacitor unit based on the amplified voltage generated by the amplifier unit 130, so that at least a part of the first currents I11 and I12 flows into the compensation device 108.

[0631] The amplifier section 130 may be realized in various ways, such as in the various embodiments described above. The amplifier unit 130 may receive power from a third device 400 that is distinct from the first device 300 and / or the second device 200, and may amplify the detection voltage output by the detector 820 to generate an amplified voltage.

[0632] In one embodiment, the compensation transformer unit 140 may include a compensation transformer including a primary side electrically connected to the amplifier unit 130 and a secondary side electrically connected to the compensation capacitor unit 150 described below.

[0633] The compensation capacitor section 150 can absorb at least a part of the first currents I11 and I12 from the large current paths 111 and 112 based on the compensation voltage generated by the compensation transformer section 140 described above.

[0634] The compensation capacitor section 150 may include at least two compensation capacitors that connect the reference potential (reference potential 1) of the compensation device 108 to the two or more large current paths 111 and 112, respectively.

[0635] In the following, the compensation device 108 according to various embodiments will be described with reference to FIGS. 59 to 64 together with FIG.

[0636] FIG. 59 is a diagram illustrating a schematic configuration of a compensation device 108A for use in a second wire system according to one embodiment of the present invention.

[0637] The description of each component of the compensation device 108A may correspond to the amplifier unit 130A, the compensation transformer 140A, and the compensation capacitor unit 150A of the compensation device according to the above-mentioned embodiment, respectively. However, since the detection unit 820A of the compensation device 108A has differences from the detection unit 120 or the detection transformer 120A of the compensation device described above, the following description will focus on these differences.

[0638] The detection unit 820A according to an embodiment of the present invention may generate a detection voltage based on a noise voltage corresponding to the first currents I11 and I12 on the two or more large current paths 111 and 112.

[0639] According to an embodiment of the present invention, the above-mentioned detection unit 820A may include a detection capacitor 821A and a detection transformer 822A. Specifically, the detection unit 820A may include a detection transformer 822A that generates a detection voltage on the secondary side based on a noise voltage applied to the primary side, and a detection capacitor unit 821A that is connected to the primary side of the detection transformer and generates a noise voltage corresponding to the first current. In this case, the detection transformer 822A may include a primary side 823A connected to the detection capacitor 821A and a secondary side 824A connected to the amplifier unit 130A.

[0640] The detection capacitor 821A may be a means for detecting the first currents I11 and I12 or a noise voltage corresponding to the noise current. In this case, the detection capacitor 821A may include as many capacitors as the large current paths. In this embodiment, the detection capacitor 821A may include a first capacitor C1 and a second capacitor C2.

[0641] At this time, the first capacitor C1 of the detection capacitor 821A may be connected to the first large current path 111A, and the second capacitor C2 of the detection capacitor 821A may be connected to the second large current path 112A. Specifically, the first ends of the first capacitor C1 and the second capacitor C2 may be connected to the first large current path 111A and the second large current path 112A, respectively, and the second ends of the first capacitor C1 and the second capacitor C2 may be connected to one node and connected to the primary side 823A of the detection transformer 822A. That is, the first capacitor C1 and the second capacitor C2 can connect each of the at least two or more large current paths 111A and 112A to the primary side 823A of the detection transformer 822A. At this time, the detection capacitor 821A may be a means for sensing a noise voltage corresponding to the first currents I11 and I12 on the large current paths 111A and 112A while being insulated from the large current paths 111A and 112A.

[0642] Meanwhile, a minute current corresponding to the impedance of the compensation device 108A of the first currents I11 and I12 flowing through the two large current paths 111A and 112A may flow through the first capacitor C1 and the second capacitor C2. According to an embodiment of the present invention, the detection capacitor 821A may further include a sensor for sensing the minute current flowing through the first capacitor C1 and the second capacitor C2.

[0643] A noise voltage corresponding to the first currents I11 and I12 may be applied to a node between the second end of the detection capacitor 821A and the detection transformer 822A. Thereafter, the detection transformer 822A may generate and output a detection voltage based on the noise voltage. That is, the detection voltage may be applied between the secondary side 824A of the detection transformer 822A and the amplifier 130A. At this time, the secondary side 824A of the detection transformer 822A may be differentially connected to an input end of the amplifier 130A, which will be described later.

[0644] The amplifier 130A of the present invention may amplify the detection voltage output by the detector 820A described above to generate an amplified voltage.

[0645] The amplifier unit 130A may generate an amplified voltage in consideration of a transformation ratio of the detection transformer 820A and a transformation ratio of the compensation transformer unit 140. At this time, the amplifier unit 130A may be realized by various means.

[0646] The compensation transformer unit 140 according to an embodiment may be realized by a compensation transformer 140A. In this case, the compensation transformer 140A may be a means for outputting a compensation voltage to the high current paths 111A and 112A side (or to a secondary side 142A described later) based on the amplified voltage while being insulated from the high current paths 111A and 112A described above.

[0647] A compensation voltage may be applied to the secondary side 142A of the compensation transformer 140A. In this case, the secondary side 142A may be disposed on a path connecting the compensation capacitor section 150A and the reference potential (reference potential 1) of the compensation device.

[0648] On the other hand, the primary side 141A of the compensation transformer 140A, the amplifier section 130A, and the secondary side 822A of the detection transformer 820A may be connected to a reference potential (Reference Potential 2) that is distinct from the remaining components of the compensation device 108A.

[0649] As described above, the compensation capacitor section 150 can absorb some of the first currents I11 and I12 flowing through the two high current paths 111A and 112A, which correspond to the compensation voltage generated by the compensation transformer 140A, from each of the two high current paths 111A and 112A using the compensation device 108A.

[0650] FIG. 60 is a diagram for explaining a specific operation of compensation device 108A according to one embodiment of the present invention.

[0651] JPEG2025016641000031.jpg25170

[0652] That is, when a noise voltage Vn is applied to the node a of the compensation device 108A or the primary side of the detection transformer 822A, the detection transformer 822A may generate a detection voltage based on the noise voltage Vn. Specifically, when the transformation ratio of the detection transformer 822A is 1:Nsen, the noise voltage Vn passing through the detection transformer 822A can be converted into a detection voltage, and the detection voltage can be Nsen*Vn. That is, the detection voltage (Nsen*Vn) may be applied to the node b between the secondary side 824A and the amplifier unit 130A.

[0653] In one embodiment, the amplifier 130A may be an inverting amplifier using an OP-amp. According to one embodiment of the present invention, an isolated VSCC (voltage-sense current-compensation) topology AEF may be realized using an OP-amp powered by a DC power source through the third device 400.

[0654] JPEG2025016641000032.jpg15170JPEG2025016641000033.jpg15170

[0655] JPEG2025016641000034.jpg11170

[0656] According to one embodiment of the present invention, the amplifier 130A is o C o may be a high-pass filter for blocking the amplifier included in the amplifying unit 130A from operating at low frequencies below the band targeted for noise reduction.

[0657] Meanwhile, when the detection voltage (Nsen*Vn) is amplified through the amplifier 130A, an amplified voltage may be applied to a node c between the amplifier 130A and the primary side 141A of the compensation transformer 140A. In this case, the amplified voltage may be -Nsen*Av and amp*Vn.

[0658] When the amplified voltage (-Nsen*Av and amp*Vn) is applied to the node c of the compensation device 108A, the compensation transformer 140A may generate a compensation voltage based on the amplified voltage (-Nsen*Av and amp*Vn). Specifically, it is assumed that the transformation ratio of the compensation transformer 140A is 1:Ninj.

[0659] At this time, the amplified voltage (-Nsen*Av and amp*Vn) passing through the compensation transformer 822A may be converted into a compensation voltage, and the compensation voltage may be -Nsen*Ninj*Av and amp*Vn. That is, the compensation voltage (-Nsen*Ninj*Av and amp*Vn) may be applied to a node d between the secondary side 142A of the compensation transformer and the compensation capacitor unit 150A.

[0660] In at least two or more compensation capacitors in the compensation capacitor section 150A, first ends may be connected to the large current paths 111A and 112A, respectively, and second ends of the compensation capacitors may be connected to the compensation transformer 140A at one node d. The effective impedance value of each capacitor included in the compensation capacitor section 150A is reduced by the voltages applied to the large current paths 111A and 112A and the voltage applied to the node d.

[0661] This allows the compensation capacitor section 150A to absorb at least a part of the first currents I11 and I12 flowing through the large current paths 111A and 112A. That is, a part of the noise current is absorbed or flows into the compensation device 108A, so that the noise current transmitted to the second device 200A can be reduced or compensated for. This will be described in detail with reference to Figs. 61 and 62.

[0662] FIG. 61 is a diagram illustrating a reduction in impedance of the compensation capacitor section in compensation device 108A according to one embodiment of the present invention.

[0663] 61, the first impedance-frequency graph (thin line) shows the change in impedance according to frequency for a typical capacitor, while the second graph (thick line) shows the change in impedance according to frequency for the compensation capacitor section included in the compensation device 108A of the present invention.

[0664] The impedance of a capacitor (Cinj-) in a typical compensation capacitor section can be calculated based on the following Equation 22. JPEG2025016641000035.jpg29170

[0665] That is, the change in impedance of a typical capacitor according to frequency can be illustrated as in the first graph (thin straight line).

[0666] On the other hand, the impedance of the capacitor Cinj of the compensation capacitor section included in the compensation device 108A of the present invention can be calculated based on the following Equation 23. JPEG2025016641000036.jpg33170

[0667] That is, the effective impedance of the capacitor Cinj in Equation 23 can be expressed as Equation 24. JPEG2025016641000037.jpg11170

[0668] Based on Equation 23 or 24, the change in impedance according to the frequency of capacitor Cinj included in compensation capacitor section 150A of compensation device 108A may be illustrated as shown in the second graph (thick line).

[0669] Specifically, looking at Equation 24, N sen N inj A v、ampThe value of may be increased or decreased depending on the design of the sense transformer 822A, the compensation transformer 140A, and the amplifier section 130A of the compensation device 108A, and may have other characteristics depending on the frequency. For example, referring to FIG. 4, the frequency has the lowest effective impedance at 6 MHz.

[0670] That is, the capacitor C included in the compensation capacitor section 150A inj By designing the effective impedance of the large current paths 111A and 112A to be reduced, the first current or the noise current can be absorbed from the large current paths 111A and 112A to the compensation capacitor section 150A. This will be further described in relation to FIG.

[0671] FIG. 62 is a diagram illustrating the flow of the first currents I11 and I12 in the compensation device 108A according to one embodiment of the present invention.

[0672] 5, the compensation capacitor unit 150A may be configured such that a current IL1 flowing between the two large current paths 111A and 112A through the compensation capacitor satisfies a predetermined first current condition. In this case, the predetermined first current condition may be a condition in which the magnitude of the current IL1 is less than a predetermined first critical magnitude.

[0673] On the other hand, the compensation capacitor section 150A may also be configured so that the current IL2 flowing through the compensation capacitor between each of the two large current paths 111A and 112A and the reference potential (reference potential 1) of the current compensation device 108A satisfies a predetermined second condition.

[0674] Specifically, the compensation voltage applied to node d is -N sen N inj A v、amp V n This results in an effective impedance of the compensation capacitor Cinj of 1 / (1+N sen N inj A v、amp ) times.

[0675] The first currents I11 and I12 (or noise currents) flowing along the two large current paths 111A and 112A may be absorbed or flowed into the capacitor Cinj so as to flow to the reference potential (reference potential 1) of the compensation device 108A. inj As the effective impedance of the resistor R decreases, the current IL2 can increase in response to the decreased effective impedance.

[0676] According to an embodiment of the present invention, the above-mentioned predetermined second current condition may be a condition in which the magnitude of the current IL2 is equal to or greater than a predetermined second critical magnitude. inj That is, in the compensation device 108A according to an embodiment of the present invention, the detection transformer 822A, the compensation transformer 140A, and the amplifier unit 130A may be designed so that the current IL2 is equal to or greater than the second critical magnitude.

[0677] According to the above-described embodiment, the first currents I11 and I22 flow from the two large current paths 111A and 112A in response to the compensation capacitor section 150A, thereby reducing the transmission of the first currents I11 and I22 to the second device 200A.

[0678] FIG. 63 is a simulation graph comparing the noise reduction performance of a VSCC compensator 108A according to one embodiment of the present invention and a passive EMI filter (or passive compensator) having a capacitance value similar to that of the VSCC compensator 108A.

[0679] Referring to Figure 63, the horizontal axis of the graph indicates frequency, and the vertical axis indicates the noise level of common mode (CM) conducted emissions (CE). The solid line indicates the EMI noise standard. In other words, if the solid line (EMI noise standard) is exceeded, the product cannot be shipped.

[0680] As can be seen from the above graph, the noise level when using the VSCC active EMI filter unit 108A of the present invention is stably lower than the EMI noise standard compared to when using a passive EMI filter. Specifically, it has been confirmed by simulation that when the VSCC active EMI filter unit 108A of the present invention is operating, an additional noise reduction of 10 to 30 dB is achieved.

[0681] Therefore, the VSCC active EMI filter section 108A can reduce area and weight while having better noise reduction performance compared to a passive EMI filter.

[0682] FIG. 64 is a diagram showing a schematic configuration of a compensation device 108B according to another embodiment of the present invention.

[0683] Compensation device 108B in Fig. 64 differs from compensation device 108A for a single-phase two-wire system described with reference to Fig. 59 in that it is used in a three-phase three-wire system. Therefore, in the following, with reference to Figs. 58 to 63, description of contents that overlap with the contents described above will be omitted, and the differences will be mainly described.

[0684] Compensation device 108B includes three large current paths 111B, 112B, 113B (eg, R phase, S phase, T phase), which results in a difference in detection capacitor 821B and compensation capacitor section 150B.

[0685] The detection capacitor 821B according to an embodiment is connected to each of the first large current path 111B, the second large current path 112B, and the third large current path 113B, and can sense a noise voltage corresponding to the first current. The process of sensing the noise voltage corresponding to the first currents I11, I12, and I13 has already been described, so a detailed description thereof will be omitted.

[0686] Meanwhile, the compensation capacitor unit 150B according to one embodiment may provide a path through which at least a portion of the first currents I11, I12, and I13 corresponding to the compensation voltage generated by the compensation transformer 140B is absorbed and flows.

[0687] Such an embodiment of the compensation device 108B may be used to reduce (or block) a first current I11, I12, I13 traveling from a load to a power source in a three-phase, three-wire power system.

[0688] The compensation device 108B including the sensing capacitor 821B and the sensing transformer 822B may be adapted or modified for a three-phase, four-wire power system (see FIG. 12). The description of the compensation device for the three-phase, four-wire power system may correspond to the description with reference to FIG.

[0689] Meanwhile, the compensation devices according to all the above-mentioned embodiments (100, 101, 102, 103, 104, 105, 106, 107, 108, and their sub-embodiments) are mutually compatible in at least some of their components, i.e., one component of the compensation device described through any embodiment may be combined as one component of the compensation device according to another embodiment.

[0690] The specific implementation described in the present invention is an example and does not limit the scope of the present invention in any manner. For the sake of brevity, descriptions of conventional electronic configurations, control systems, software, and other functional aspects of the above system may be omitted. In addition, the wire connections or connecting members between components shown in the drawings are illustrative of functional connections and / or physical or circuit connections, and may be replaced or further shown as various functional connections, physical connections, or circuit connections in an actual device. In addition, unless specifically mentioned as "essential" or "important", it can be said that the components are not necessary components for applying the present invention.

[0691] Therefore, the concept of the present invention should not be limited to the embodiments described above, and all scopes equivalent to or substantially modified from the scope of the claims described below, as well as the scope of the claims, belong to the category of the concept of the present invention.

Claims

1. An active compensation device that actively compensates for noise generated in a common mode in each of at least two or more high current paths connected to a first device, At least two or more high current paths for transmitting high current supplied by a second device to the first device; a detection unit that detects a common mode noise current on the large current path and generates a plurality of output signals in parallel based on the noise current; a plurality of amplifiers corresponding to the plurality of output signals, each of which amplifies the plurality of output signals to generate a plurality of amplified signals in parallel; a compensation unit that draws out a compensation current from the large current path or generates a compensation voltage on the large current path based on the plurality of amplified signals.

2. The detection unit includes a detection transformer including a primary side disposed on the high current path and a secondary side on which the multiple output signals are generated in parallel, 2. The active compensation device according to claim 1, wherein a first electric wire connected to an input end of a first amplifier unit among the plurality of amplifier units, and a second electric wire connected to an input end of a second amplifier unit among the plurality of amplifier units are wound around the secondary side of the detection unit.

3. The compensation unit includes a transformer including a primary side connected to an output terminal of each of the plurality of amplifier units and a secondary side connected to the large current path, 2. The active compensation device according to claim 1, wherein a third electric wire through which a current output from a first amplifier unit among the plurality of amplifier units flows, and a fourth electric wire through which a current output from a second amplifier unit among the plurality of amplifier units flows are wound on a primary side of the compensation unit.

4. The plurality of amplifiers include a first amplifier and a second amplifier, 2. The active compensation device according to claim 1, wherein the compensation unit has a structure in which an electric wire connecting the output end of the first amplifier unit and the output end of the second amplifier unit passes through or is wound around a core as a primary side electric wire, and the large current path passes through or is wound around the core as a secondary side electric wire.

5. The plurality of amplification units are composed of a first amplification unit, a second amplification unit, a third amplification unit, and a fourth amplification unit; The detection unit generates a first output voltage and a second output voltage based on the noise current, the first output voltage is differentially input to the first amplifier unit and the third amplifier unit, and the second output voltage is differentially input to the second amplifier unit and the fourth amplifier unit, the compensation unit generates a compensation voltage on the large current path based on a first amplified voltage output from the first amplifier unit and a second amplified voltage output from the second amplifier unit; 2. The active compensation device according to claim 1, further comprising: another compensation section that draws out a compensation current from the large current path based on a third amplified voltage output from the third amplification section and a fourth amplified voltage output from the fourth amplification section.

Images