Charging control method, medium, program product, controller and vehicle

Abstract

The present disclosure relates to a charging control method, medium, program product, controller and vehicle. The method includes: the charging control method includes: when the on-board charger is in the first working mode, the power factor correction circuit is subjected to dual-loop control of the power outer loop and the AC current inner loop, the resonant circuit is subjected to fixed-frequency open-loop control, and the secondary drive signal of the resonant circuit follows the primary drive signal of the resonant circuit. In this way, even when the output power of the main circuit is small or unloaded, a relatively high bus voltage of the power factor correction circuit can be maintained to ensure the power supply capacity of the auxiliary circuit under different load conditions. Fixed-frequency control of the resonant circuit can avoid the problem of insufficient auxiliary circuit power supply capacity caused by frequent operation of the primary side due to variable frequency control. In addition, only the current of the power factor correction circuit is controlled without voltage control, and the resonant circuit is subjected to fixed-frequency open-loop control, which can simplify the control logic and reduce vehicle costs.

Description

Technical Field

[0001] The present disclosure relates to the field of vehicle technology, and in particular, to a charging control method, a medium, a program product, a controller and a vehicle. Background Art

[0002] With the demand for energy conservation and emission reduction, as well as the control of air pollution, new energy vehicles are gradually being promoted and applied in the market, among which electric vehicles are the main force of new energy vehicles. The on-board charger of electric vehicles is an important part of electric processing. The on-board charger generally has an AC input terminal and two DC output terminals. The AC input terminal is connected to the AC side. The first DC output terminal charges the high-voltage battery, which is equivalent to the main output; the second DC output terminal supplies power to the low-voltage system, which is equivalent to the auxiliary output. Among them, the output power of the main road will also affect the output power of the auxiliary road. For example, when the output power of the main road is small or unloaded (equivalent to the high-voltage battery at the first DC output terminal is about to be fully charged or has been fully charged), the main control will issue a very small duty cycle, or even enter the intermittent working mode, resulting in a small or even zero voltage on the auxiliary road, which may cause the problem of insufficient power supply capacity of the auxiliary road. Summary of the invention

[0003] The purpose of the present disclosure is to provide a charging control method, a medium, a program product, a controller and a vehicle.

[0004] In order to achieve the above-mentioned object, in a first aspect, the present disclosure provides a charging control method, which is applied to an on-board charger, wherein the on-board charger comprises a power factor correction circuit, a bus capacitor, a resonant circuit and a low-voltage side conversion circuit connected in sequence, wherein the power factor correction circuit is used to be connected to an AC side, the resonant circuit is used to be connected to a power battery, and the low-voltage side conversion circuit is used to be connected to a low-voltage system;

[0005] The charging control method comprises:

[0006] When the on-board charger is in the first working mode, the power factor correction circuit is subjected to dual-loop control of the power outer loop and the AC current inner loop, the resonant circuit is subjected to fixed-frequency open-loop control, and the secondary side drive signal of the resonant circuit follows the primary side drive signal of the resonant circuit, wherein the first working mode refers to a mode in which the AC side simultaneously supplies power to the power battery and the low-voltage system.

[0007] Optionally, the charging control method further includes:

[0008] Determining a charging voltage of the power battery;

[0009] The performing fixed-frequency open-loop control on the resonant circuit comprises:

[0010] If the charging voltage is less than a preset voltage threshold, determining the primary duty cycle of the resonant circuit according to a deviation between a bus voltage reference value and an AC peak voltage and a first preset duty cycle;

[0011] The primary side of the resonant circuit is controlled to operate according to a first preset frequency and the primary side duty cycle, and the secondary side of the resonant circuit is controlled to operate according to the first preset frequency and the first preset duty cycle.

[0012] Optionally, determining the primary duty cycle of the resonant circuit according to a deviation between a bus voltage reference value and an AC peak voltage and a first preset duty cycle includes:

[0013] Determine an adjustment amount of the primary duty cycle of the resonant circuit according to a deviation between a bus voltage reference value and an AC peak voltage, wherein the adjustment amount is greater than or equal to zero and less than or equal to a preset adjustment amount threshold;

[0014] The difference between the first preset duty cycle and the adjustment amount is determined as the primary duty cycle.

[0015] Optionally, the performing fixed-frequency open-loop control on the resonant circuit further includes:

[0016] If the charging voltage is greater than or equal to the preset voltage threshold, the primary side and the secondary side of the resonant circuit are controlled to operate according to a second preset frequency and a second preset duty cycle.

[0017] Optionally, the performing dual-loop control of a power outer loop and an AC current inner loop on the power factor correction circuit includes:

[0018] Obtaining the rated charging power of the power battery, the effective value of the voltage on the AC side, and the actual current on the AC side;

[0019] Determining a reference current according to the rated charging power and the effective value of the voltage;

[0020] The action of the switch tube of the power factor correction circuit is controlled according to the deviation between the reference current and the actual current.

[0021] Optionally, the low-voltage side conversion circuit comprises a current doubler circuit, a first capacitor and a step-down circuit connected in sequence, wherein the current doubler circuit is connected to the resonant circuit, and the step-down circuit is used to be connected to the low-voltage system;

[0022] The determining of the reference current according to the rated charging power and the effective value of the voltage includes:

[0023] Determining a reference charging power according to the rated charging power, wherein the reference charging power is less than the rated charging power;

[0024] The ratio of the reference charging power to the effective value of the voltage is determined as a reference current.

[0025] Optionally, the low-voltage side conversion circuit comprises a current doubler circuit and a voltage step-down circuit connected in series, wherein the current doubler circuit is connected to the resonant circuit, and the voltage step-down circuit is used to be connected to the low-voltage system;

[0026] The determining of the reference current according to the rated charging power and the effective value of the voltage includes:

[0027] The ratio of the rated charging power to the effective value of the voltage is determined as a reference current.

[0028] Optionally, the charging control method further includes:

[0029] When the on-board charger is in the second working mode, the resonant circuit is controlled in a fixed-frequency open-loop manner, and the primary drive signal follows the secondary drive signal. The second working mode refers to a mode in which the power battery only supplies power to the low-voltage system.

[0030] Optionally, the charging control method further includes:

[0031] When the on-board charger is in the third working mode, the power factor correction circuit is subjected to dual-loop control of the bus voltage outer loop and the AC current inner loop, the resonant circuit is subjected to fixed-frequency open-loop control, and the primary drive signal follows the secondary drive signal. The third working mode refers to a mode in which the power battery supplies power to the AC side and the low-voltage system at the same time.

[0032] Optionally, the frequency of the switch tube of the low-voltage side conversion circuit is an integer multiple of the frequency of the switch tube of the resonant circuit.

[0033] Optionally, the low-voltage side conversion circuit includes:

[0034] A current doubler circuit and a voltage step-down circuit connected in series; or

[0035] A current doubler circuit, a first capacitor and a voltage step-down circuit connected in sequence;

[0036] Among them, when the on-board charger is in the first working mode, the driving rising edge of the switch tube of the buck circuit lags behind the driving rising edge of the primary side of the resonant circuit by a target time length, and the driving rising edge of the switch tube of the buck circuit is synchronized with the driving rising edge of the secondary side of the resonant circuit. The target time length is the time length from the driving rising edge of the primary side to the zero crossing point of the resonant current.

[0037] Optionally, the bus capacitor is a film capacitor or a ceramic capacitor.

[0038] In a second aspect, the present disclosure provides a computer-readable storage medium having a computer program stored thereon, which, when executed by a processor, implements the steps of the charging control method provided in the first aspect of the present disclosure.

[0039] In a third aspect, the present disclosure provides a computer program product, including a computer program, which, when executed by a processor, implements the steps of the charging control method provided in the first aspect of the present disclosure.

[0040] In a fourth aspect, the present disclosure provides a controller, comprising:

[0041] a first memory having a computer program stored thereon;

[0042] The first processor is used to execute the computer program in the first memory to implement the steps of the charging control method provided in the first aspect of the present disclosure.

[0043] In a fifth aspect, the present disclosure provides a vehicle, comprising:

[0044] Power battery;

[0045] Low pressure system;

[0046] An on-board charger, wherein the on-board charger comprises a power factor correction circuit, a bus capacitor, a resonant circuit and a low-voltage side conversion circuit connected in sequence, the power factor correction circuit is used to connect to the AC side, the resonant circuit is used to connect to the power battery, and the low-voltage side conversion circuit is used to connect to the low-voltage system; and

[0047] The controller provided in the fourth aspect of the present disclosure.

[0048] In the above technical solution, when the AC side simultaneously supplies power to the power battery and the low-voltage system (i.e., the on-board charger is in the first working mode), the power factor correction circuit of the on-board charger is controlled by the dual loop of the power outer loop and the AC current inner loop, and the resonant circuit is controlled by the fixed frequency open loop, and the secondary side drive signal of the resonant circuit follows the primary side drive signal of the resonant circuit. Since the secondary side drive signal of the resonant circuit follows the primary side drive signal of the resonant circuit, that is, when the on-board charger is in the first working mode, the secondary side of the resonant circuit is turned on, therefore, when the resonant current passes through the zero point, the power battery can reversely supplement the power factor correction circuit through the turned-on secondary side, so that even when the output power of the main circuit is small or unloaded, a high bus voltage of the power factor correction circuit can be maintained, thereby ensuring the power supply capacity of the auxiliary circuit under different load conditions (e.g., full load). The fixed frequency control of the resonant circuit can avoid the problem of insufficient power supply capacity of the auxiliary circuit caused by frequent operation of the primary side due to variable frequency control. In addition, only the current of the power factor correction circuit is controlled without voltage control, and the resonant circuit is open-loop controlled at a fixed frequency, which can simplify the control logic and eliminate the need for complex control hardware or software, thereby reducing vehicle costs. In addition, when the resonant current passes through the zero point, the power battery can reversely supplement the power factor correction circuit through the turned-on secondary side, thereby reducing the capacity requirements of the bus capacitor at the output end of the power factor correction circuit, reducing the capacitance of the bus capacitor, and achieving the purpose of using a smaller bus capacitor such as a film capacitor to replace the electrolytic capacitor.

[0049] Other features and advantages of the present disclosure will be described in detail in the following detailed description. BRIEF DESCRIPTION OF THE DRAWINGS

[0050] The accompanying drawings are used to provide a further understanding of the present disclosure and constitute a part of the specification. Together with the following specific embodiments, they are used to explain the present disclosure but do not constitute a limitation of the present disclosure. In the accompanying drawings:

[0051] Figure 1 The figure is a structural block diagram of a vehicle charger according to an exemplary embodiment.

[0052] Figure 2 is a structural block diagram of a vehicle charger according to another exemplary embodiment.

[0053] Figure 3 is a structural block diagram of a vehicle charger according to yet another exemplary embodiment.

[0054] Figure 4 The topology diagram of a vehicle charger is shown according to an exemplary embodiment.

[0055] Figure 5is a topological diagram of a vehicle charger according to another exemplary embodiment.

[0056] Figure 6 The figure is a flow chart of a charging control method according to an exemplary embodiment.

[0057] Figure 7 The figure is a schematic diagram showing energy transfer of an on-board charger in a first working mode according to an exemplary embodiment.

[0058] Figure 8 The figure is a schematic diagram showing energy transfer of a vehicle charger in a second working mode according to an exemplary embodiment.

[0059] Fig. 9 The figure is a schematic diagram showing energy transfer of an on-board charger in a third working mode according to an exemplary embodiment.

[0060] Fig.10 The invention is a schematic diagram showing a control method of a power factor correction circuit according to an exemplary embodiment.

[0061] Fig.11 is a schematic diagram showing a control method of a power factor correction circuit according to another exemplary embodiment.

[0062] Fig.12 is a schematic diagram showing a method for controlling a resonant circuit according to an exemplary embodiment.

[0063] Fig.13 The figure is a control timing diagram of a vehicle charger in a first working mode according to an exemplary embodiment.

[0064] Fig.14 It is a waveform diagram showing a case where the secondary side of the resonant circuit is not turned on according to an exemplary embodiment.

[0065] Fig.15 The figure is a waveform diagram showing a waveform when a secondary side of a resonant circuit is turned on according to an exemplary embodiment.

[0066] Fig.16 is a schematic diagram showing a method for controlling a resonant circuit according to another exemplary embodiment.

[0067] Fig.17 is a control timing diagram of a vehicle charger in a first working mode according to another exemplary embodiment.

[0068] Fig.18 is a waveform diagram showing a case where the secondary side of the resonant circuit is not turned on according to another exemplary embodiment.

[0069] Fig.19 is a waveform diagram showing a waveform when a secondary side of a resonant circuit is turned on according to another exemplary embodiment.

[0070] Fig. 20 is a control timing diagram of a vehicle charger in a second working mode according to an exemplary embodiment.

[0071] Fig.21 is a control timing diagram of a vehicle charger in a third working mode according to an exemplary embodiment.

[0072] Fig. 22 is a schematic diagram showing a control method of a power factor correction circuit according to yet another exemplary embodiment.

[0073] Fig.23 is a block diagram of a charging control device according to an exemplary embodiment.

[0074] Fig.24 is a block diagram of a vehicle according to an exemplary embodiment. DETAILED DESCRIPTION

[0075] The specific implementation of the present disclosure is described in detail below in conjunction with the accompanying drawings. It should be understood that the specific implementation described herein is only used to illustrate and explain the present disclosure, and is not used to limit the present disclosure.

[0076] Figure 1 FIG. 1 is a structural block diagram of a vehicle charger according to an exemplary embodiment. Figure 1 As shown, the on-board charger includes a power factor correction circuit 1, a bus capacitor C1, a resonant circuit 2 and a low-voltage side conversion circuit 3 connected in sequence, wherein the power factor correction circuit 1 is used to connect to the AC side AC, the resonant circuit 2 is used to connect to the power battery 4, and the low-voltage side conversion circuit 3 is used to connect to the low-voltage system 5.

[0077] In the present disclosure, the low voltage system 5 may include a low voltage battery and low voltage electrical appliances (e.g., an in-vehicle entertainment system, a lamp, an in-vehicle controller, etc.) of the vehicle. The AC side AC may be a cosine AC or a sine AC. The bus capacitor C1 may be an electrolytic capacitor, a film capacitor, a ceramic capacitor, etc. The bus capacitor C1 is a filter capacitor for filtering high frequency current to reduce voltage fluctuations at the output end of the power factor correction circuit 1.

[0078] like Figure 2 and Figure 3As shown, the resonant circuit 2 may include a primary side 21, a magnetic integrated transformer 22, and a secondary side 23. Among them, the first end of the primary side 21 is connected to the bus capacitor C1, the second end of the primary side 21 is connected to the primary winding of the magnetic integrated transformer 22, the first end of the secondary side 23 is connected to the high-voltage secondary winding of the magnetic integrated transformer 22, the second end of the secondary side 23 is used to connect to the power battery 4, and the low-voltage secondary winding of the magnetic integrated transformer 22 is connected to the low-voltage side conversion circuit 3.

[0079] The low voltage side conversion circuit 3 can have various structures. In one embodiment, Figure 2 As shown, the low-voltage side conversion circuit 3 may include a current doubler circuit 31 and a step-down circuit 32 connected in series, wherein the current doubler circuit 31 is used to connect to the low-voltage secondary winding of the magnetic integrated transformer 22, and the step-down circuit 32 is used to connect to the low-voltage system 5.

[0080] In another embodiment, if Figure 3 As shown, the low-voltage side conversion circuit 3 may include a current doubler circuit 31, a first capacitor C2 and a step-down circuit 32 connected in sequence, wherein the current doubler circuit 31 is used to connect to the low-voltage secondary winding of the magnetic integrated transformer 22, and the step-down circuit 32 is used to connect to the low-voltage system 5.

[0081] Specifically, if Figure 4 and Figure 5 As shown, the power factor correction circuit 1 may include: an input inductor L1, and a first phase bridge arm (including a first switch tube Q1 and a second switch tube Q2) and a second phase bridge arm (including a third switch tube Q3 and a fourth switch tube Q4) connected in parallel.

[0082] Among them, the first end of the input inductor L1 is used to connect to the first end of the AC side AC (i.e., the live wire L), and the second end of the input inductor L1 is connected to the midpoint of the first phase bridge arm; the bus capacitor C1 is connected in parallel with the second phase bridge arm; the midpoint of the second phase bridge arm is used to connect to the second end of the AC side AC (i.e., the neutral wire N).

[0083] like Figure 4 and Figure 5 As shown, the primary side 21 may include a third phase bridge arm (including a fifth switch tube Q5 and a sixth switch tube Q6) and a fourth phase bridge arm (including a seventh switch tube Q7 and an eighth switch tube Q8) connected in parallel; the secondary side 23 may include a fifth phase bridge arm (including a ninth switch tube Q9 and a tenth switch tube Q10) and a sixth phase bridge arm (including an eleventh switch tube Q11 and a twelfth switch tube Q12) connected in parallel; the magnetic integrated transformer 22 may be a resonant topology, specifically including: a primary winding, a high-voltage secondary winding, a low-voltage secondary winding, a resonant inductor Ls arranged between the midpoint of the third phase bridge arm and the first end of the primary winding, and a resonant capacitor Cr arranged between the midpoint of the fourth phase bridge arm and the second end of the primary winding.

[0084] Among them, the bus capacitor C1 is connected in parallel with the third phase bridge arm, the first end of the high-voltage secondary winding of the magnetic integrated transformer 22 is connected to the midpoint of the fifth phase bridge arm, and the second end of the high-voltage secondary winding of the magnetic integrated transformer 22 is connected to the midpoint of the sixth phase bridge arm; the sixth phase bridge arm is connected in parallel with the power battery 4.

[0085] like Figure 4 and Figure 5 As shown, the current doubling circuit 31 includes a thirteenth switch tube Q13 and a fourteenth switch tube Q14, wherein the first end of the thirteenth switch tube Q13 is connected to the first end of the low-voltage secondary winding of the magnetic integrated transformer 22, the second end of the thirteenth switch tube Q13 is connected to the first end of the fourteenth switch tube Q14, and the second end of the fourteenth switch tube Q14 is connected to the second end of the low-voltage secondary winding of the magnetic integrated transformer 22.

[0086] like Figure 4 and Figure 5 As shown, the step-down circuit 32 includes a fifteenth switch tube Q15, a diode D1, a second capacitor C3 and an energy storage inductor L2. Among them, the first end of the fifteenth switch tube Q15 is connected to the second end of the thirteenth switch tube Q13 and the first end of the fourteenth switch tube Q14 respectively, the second end of the fifteenth switch tube Q15 is connected to the first end of the diode D1 and the first end of the energy storage inductor L2 respectively, the second end of the energy storage inductor L2 is connected to the positive electrode of the low-voltage system 5 and the first end of the second capacitor C3 respectively; the second end of the diode D1, the second end of the second capacitor C3 and the negative electrode of the low-voltage system 5 are respectively connected to the midpoint of the low-voltage secondary winding of the magnetic integrated transformer 22. The above-mentioned second capacitor C3 can reduce the voltage fluctuation at the second end of the fifteenth switch tube Q15.

[0087] like Figure 5 As shown, when the low-voltage side conversion circuit 3 includes a current doubler circuit 31, a first capacitor C2 and a step-down circuit 32 connected in sequence, the first end of the first capacitor C2 is connected to the second end of the thirteenth switch tube Q13 and the first end of the fifteenth switch tube Q15, respectively, and the second end of the first capacitor C2 is connected to the midpoint of the low-voltage secondary winding of the magnetic integrated transformer 22 and the second end of the diode D1, respectively.

[0088] Figure 6 is a flow chart of a charging control method according to an exemplary embodiment. The charging control method can be applied to a vehicle charger, for example, Figure 4 or Figure 5 The on-board charger shown in the figure. Figure 6 As shown, the charging control method may include the following S101.

[0089] In S101, when the on-board charger is in the first working mode, the power factor correction circuit is subjected to dual-loop control of the power outer loop and the AC current inner loop, the resonant circuit is subjected to fixed-frequency open-loop control, and the secondary side drive signal of the resonant circuit follows the primary side drive signal of the resonant circuit.

[0090] In the present disclosure, the on-board charger may include three working modes, namely, the first working mode, the second working mode and the third working mode. The first working mode refers to a mode in which the AC side supplies power to both the power battery and the low-voltage system, the second working mode refers to a mode in which the power battery only supplies power to the low-voltage system, and the third working mode refers to a mode in which the power battery supplies power to both the AC side and the low-voltage system.

[0091] When the on-board charger is in the first working mode, the power factor correction circuit is used to perform power factor correction on the input signal on the AC side, and output the power factor corrected current signal to the primary side of the resonant circuit; the primary side of the resonant circuit is used to convert the power factor corrected current signal (AC power) into DC power, which is input to the secondary side of the resonant circuit and the low-voltage side conversion circuit after voltage regulation and resonance by the magnetic integrated transformer. The secondary side of the resonant circuit rectifies the DC power output by the magnetic integrated transformer and outputs it to the power battery to supply power to the power battery; at the same time, the low-voltage side conversion circuit rectifies and steps down the DC power output by the magnetic integrated transformer and outputs it to the low-voltage system to supply power to the low-voltage system. Figure 7 As shown, when the on-board charger is in the first working mode, the energy on the AC side flows to the power battery via the power factor correction circuit, the primary side, the magnetic integrated transformer, and the secondary side in sequence to charge the power battery. At the same time, the energy on the AC side flows to the low-voltage system via the power factor correction circuit, the primary side, the magnetic integrated transformer, and the low-voltage side conversion circuit in sequence to charge the low-voltage battery and / or power the low-voltage electrical appliances.

[0092] When the on-board charger is in the second working mode, the secondary side of the resonant circuit rectifies the DC power of the power battery and outputs it to the low-voltage side conversion circuit. The low-voltage side conversion circuit rectifies and steps down the DC power output from the secondary side and outputs it to the low-voltage system to supply power to the low-voltage system. Figure 8 As shown, when the on-board charger is in the second working mode, the energy of the power battery flows to the low-voltage system via the secondary side and the low-voltage side conversion circuit to charge the low-voltage battery and / or power the low-voltage electrical appliances.

[0093] When the on-board charger is in the third working mode, the secondary side of the resonant circuit rectifies the DC power of the power battery and outputs it to the power factor correction circuit and the low-voltage side conversion circuit. The power factor correction circuit converts the DC power output from the secondary side into AC power and outputs it to the AC side to supply power to the AC side. At the same time, the low-voltage side conversion circuit rectifies and steps down the DC power output from the secondary side and outputs it to the low-voltage system to supply power to the low-voltage system. Fig. 9 As shown, when the on-board charger is in the third working mode, the energy of the power battery flows to the AC side via the secondary side, the magnetic integrated transformer, the primary side, and the power factor correction circuit to power the AC side. At the same time, the energy of the power battery flows to the low-voltage system via the secondary side and the low-voltage side conversion circuit to charge the low-voltage battery and / or power the low-voltage electrical appliances.

[0094] In the above technical solution, when the AC side simultaneously supplies power to the power battery and the low-voltage system (i.e., the on-board charger is in the first working mode), the power factor correction circuit of the on-board charger is controlled by the dual loop of the power outer loop and the AC current inner loop, and the resonant circuit is controlled by the fixed frequency open loop, and the secondary side drive signal of the resonant circuit follows the primary side drive signal of the resonant circuit. Since the secondary side drive signal of the resonant circuit follows the primary side drive signal of the resonant circuit, that is, when the on-board charger is in the first working mode, the secondary side of the resonant circuit is turned on, therefore, when the resonant current passes through the zero point, the power battery can reversely supplement the power factor correction circuit through the turned-on secondary side, so that even when the output power of the main circuit is small or unloaded, a high bus voltage of the power factor correction circuit can be maintained, thereby ensuring the power supply capacity of the auxiliary circuit under different load conditions (e.g., full load). The fixed frequency control of the resonant circuit can avoid the problem of insufficient power supply capacity of the auxiliary circuit caused by frequent operation of the primary side due to variable frequency control. In addition, only the current of the power factor correction circuit is controlled without voltage control, and the resonant circuit is open-loop controlled at a fixed frequency, which can simplify the control logic and eliminate the need for complex control hardware or software, thereby reducing vehicle costs. In addition, when the resonant current passes through the zero point, the power battery can reversely supplement the power factor correction circuit through the turned-on secondary side, thereby reducing the capacity requirements of the bus capacitor at the output end of the power factor correction circuit, reducing the capacitance of the bus capacitor, and achieving the purpose of using a smaller bus capacitor such as a film capacitor to replace the electrolytic capacitor.

[0095] The following is a detailed description of the specific implementation method of performing dual-loop control of the power outer loop and the AC current inner loop on the power factor correction circuit in S101. Specifically, it can be achieved by the following steps (a1) to (a3):

[0096] Step (a1): Obtain the rated charging power of the power battery, the effective value of the voltage on the AC side, and the actual current on the AC side.

[0097] In the present disclosure, the effective value of the voltage on the AC side can be detected by a voltage sensor disposed at the input end of the AC side, or the effective value of the voltage on the AC side can be monitored by a control chip in a power factor correction circuit. In addition, the actual current on the AC side can be detected by a current sensor disposed at the input end of the AC side.

[0098] Step (a2): Determine the reference current according to the rated charging power of the power battery and the effective value of the voltage on the AC side.

[0099] When the low-voltage side conversion circuit includes a current doubler circuit and a voltage step-down circuit connected in series, such as Fig.10 As shown, the ratio of the rated charging power Power to the effective value Ui_rms of the voltage on the AC side can be determined as the reference current Iref.

[0100] When the low-voltage side conversion circuit includes a current doubler circuit, a first capacitor and a step-down circuit connected in sequence, the reference charging power can be first determined based on the rated charging power, wherein the reference charging power is less than the rated charging power; then, the ratio of the reference charging power to the effective value of the voltage is determined as the reference current.

[0101] For example, Fig.11 As shown, Power / 2 can be determined as the reference charging power, that is, the ratio of Power / 2 to the effective value Ui_rms of the voltage on the AC side is determined as the reference current Iref.

[0102] Step (a3): Control the switch action of the power factor correction circuit according to the deviation between the reference current and the actual current on the AC side.

[0103] like Fig.10 and Fig.11 As shown, a sinusoidal pulse width modulation (SPWM) signal can be generated by a proportional-integral (PI) controller according to the deviation between the reference current Iref and the actual current IL1 on the AC side, and the operation of the switch tubes (i.e., Q1, Q2, Q3, and Q4) of the power factor correction circuit can be controlled according to the SPWM signal.

[0104] In a possible implementation manner, the charging control method may further include the following:

[0105] Determine the charging voltage of the power battery;

[0106] At this time, the above-mentioned fixed-frequency open-loop control of the resonant circuit may include:

[0107] If the charging voltage is less than a preset voltage threshold (for example, 300V), the primary duty cycle of the resonant circuit is determined according to the deviation between the bus voltage reference value and the AC peak voltage, and the first preset duty cycle; the primary side of the resonant circuit is controlled to operate according to the first preset frequency and the primary duty cycle, and the secondary side of the resonant circuit is controlled to operate according to the first preset frequency and the first preset duty cycle.

[0108] In the present disclosure, when the on-board charger is in the first working mode, the charging voltage of the power battery can be determined. For example, the charging voltage of the power battery can be obtained through a battery management system.

[0109] When the charging voltage of the power battery is less than the preset voltage threshold, both the primary and secondary sides of the resonant circuit operate at a fixed frequency (i.e., the first preset frequency), wherein the duty cycle of the secondary side is fixed (i.e., the first preset duty cycle), and the duty cycle of the primary side can be adjusted based on the deviation between the bus voltage reference value and the AC peak voltage, and the first preset duty cycle. That is, the secondary side operates in a fixed frequency fixed duty cycle mode, and the primary side operates in a fixed frequency adjustable duty cycle mode.

[0110] The following is a detailed description of the specific implementation method of determining the primary duty cycle of the resonant circuit based on the deviation between the bus voltage reference value and the AC peak voltage and the first preset duty cycle. In one implementation, it can be achieved by the following steps (b1) and (b2):

[0111] Step (b1): Determine the adjustment amount of the primary duty cycle of the resonant circuit according to the deviation between the bus voltage reference value and the AC peak voltage.

[0112] Step (b2): Determine the difference between the first preset duty cycle and the adjustment amount as the primary duty cycle.

[0113] In the present disclosure, the adjustment amount of the primary duty cycle of the resonant circuit is greater than or equal to zero and less than or equal to a preset adjustment amount threshold.

[0114] like Fig.12 As shown, according to the deviation between the bus voltage reference value Ubus_ref and the AC peak voltage Ubus_peak, the adjustment amount Duty_Limit of the primary duty cycle of the resonant circuit is determined by the PI controller; then, the first preset duty cycle ( Fig.12 The difference between the primary duty cycle and the primary duty cycle adjustment amount Duty_Limit is determined as the primary duty cycle. Afterwards, a pulse width modulation (PWM) signal can be generated based on the determined primary duty cycle, and the primary side (i.e., Q5, Q6, Q7, and Q8) of the resonant circuit can be controlled based on the PWM signal; at the same time, based on the first preset duty cycle ( Fig.12 50% is used as an example) to generate a PWM signal, and based on the PWM signal, the secondary side (i.e., Q9, Q10, Q11, and Q12) of the resonant circuit is controlled. The control timing of the primary side and the secondary side is as follows: Fig.13 As shown, where ILs is the resonant current. Fig.13In the figure, t1 is the time from the driving rising edge of Q5 and Q8 in the primary side to the zero point of the resonant current, that is, the driving rising edge dead time of Q9 and Q12 in the secondary side of the resonant circuit, and also the driving rising edge dead time of Q15 in the low-voltage side conversion circuit. t2 is the time that Q9 and Q12 in the secondary side are turned on more than Q5 and Q8 in the primary side.

[0115] For example, the preset adjustment amount threshold is 30%, that is, Fig.12 As shown, the adjustment amount Duty_Limit of the primary duty cycle of the resonant circuit is in the range of [0%, 30%], the first preset duty cycle is 50%, and the primary duty cycle is in the range of [20%, 50%].

[0116] In one implementation manner, the PI controller may determine a reference adjustment amount corresponding to the deviation according to a pre-established correspondence relationship between the reference deviation and the reference adjustment amount, as the adjustment amount of the primary duty cycle of the resonant circuit.

[0117] In the above embodiment, by reducing the primary duty cycle of the resonant circuit (such as Fig.13 As shown in the figure), the AC peak voltage is increased to meet the high voltage input requirement on the AC side. At the same time, the minimum value of the primary duty cycle is limited (for example, the above-mentioned 20%) to avoid excessive AC peak voltage, thereby avoiding damage to the switch tube of the power factor correction circuit caused by the power factor correction circuit charging into the uncontrolled rectification mode (wherein, when the AC peak voltage is greater than the bus voltage of the power factor correction circuit, the uncontrolled rectification mode is triggered).

[0118] In addition, the primary duty cycle is the difference between the first preset duty cycle (i.e., the secondary duty cycle) and the adjustment amount, i.e., the secondary duty cycle is greater than the primary duty cycle. In this way, when the low-voltage side conversion circuit is working, the bus voltage of the power factor correction circuit will be pulled down when the resonant current passes through the zero point (e.g., Fig.14 As shown, the A1 curve represents the AC side voltage, the B1 curve represents the bus voltage of the power factor correction circuit, and the E1 curve represents the resonant current). The lowered bus voltage of the power factor correction circuit can be reversely supplemented by the power battery through the resonant circuit (such as Fig.15 As shown, wherein the A3 curve represents the AC side voltage, the B3 curve represents the bus voltage of the power factor correction circuit, and the E3 curve represents the resonant current), thereby ensuring the power supply capacity of the auxiliary circuit under different load conditions (for example, full load).

[0119] In a possible implementation manner, the above-mentioned fixed-frequency open-loop control of the resonant circuit may further include:

[0120] If the charging voltage is greater than or equal to the preset voltage threshold, the primary side and the secondary side of the resonant circuit are controlled to operate according to the second preset frequency and the second preset duty cycle.

[0121] In the present disclosure, when the charging voltage of the power battery is greater than or equal to the preset voltage threshold, the primary side and the secondary side of the resonant circuit both operate at a fixed frequency and a fixed duty cycle, wherein the primary side duty cycle and the secondary side duty cycle are fixed (i.e., the second preset duty cycle), and the frequencies of the primary side and the secondary side are also fixed (i.e., the second preset frequency). That is, the primary side and the secondary side of the resonant circuit both operate in a fixed frequency and fixed duty cycle manner.

[0122] like Fig.16 As shown, based on the second preset duty cycle ( Fig.16 50% is used as an example) to generate a PWM signal, and based on the PWM signal, the primary side (i.e., Q5, Q6, Q7, and Q8) and the secondary side (i.e., Q9, Q10, Q11, and Q12) of the resonant circuit are controlled. The control timing of the primary side and the secondary side is as follows: Fig.17 As shown. Fig.17 In the figure, t1 is the time length from the driving rising edge of Q5 and Q8 in the primary side to the zero point of the resonant current, t4 is the time length from the driving rising edge of Q6 and Q7 in the primary side to the zero point of the resonant current, wherein the driving rising edge of Q15 in the low-voltage side conversion circuit is synchronized with the zero point of the resonant current, t3 is the dead time of the driving falling edge of Q5 and Q8 in the primary side and Q9 and Q12 in the secondary side, and t1 is also the dead time of the driving rising and falling edges of Q5 and Q8 in the primary side and Q9 and Q12 in the secondary side.

[0123] When the low-voltage side conversion circuit is working, the bus voltage of the power factor correction circuit will be pulled down when the resonant current passes through zero (such as Fig.18 As shown, curve A represents the AC side voltage, curve B represents the bus voltage of the power factor correction circuit, and curve E represents the resonant current). The lowered bus voltage of the power factor correction circuit can be reversely supplemented by the power battery through the resonant circuit (such as Fig.19 As shown, wherein the A2 curve represents the AC side voltage, the B2 curve represents the bus voltage of the power factor correction circuit, and the E2 curve represents the resonant current), thereby ensuring the power supply capacity of the auxiliary circuit under different load conditions (for example, full load).

[0124] In a possible implementation manner, the charging control method may further include the following steps:

[0125] When the on-board charger is in the second working mode, the resonant circuit is subjected to fixed-frequency open-loop control, and the primary-side driving signal follows the secondary-side driving signal.

[0126] In the present disclosure, when the on-board charger is in the second operating mode, the power factor correction circuit does not work. At this time, the primary and secondary sides of the resonant circuit can be controlled to operate according to the third preset frequency and the third preset duty cycle, that is, the primary and secondary sides of the resonant circuit both operate in a fixed frequency and fixed duty cycle manner.

[0127] like Fig.16 As shown, the third preset duty cycle ( Fig.16 50% is used as an example) to generate a PWM signal, and based on the PWM signal, the primary side (i.e., Q5, Q6, Q7, and Q8) and the secondary side (i.e., Q9, Q10, Q11, and Q12) of the resonant circuit are controlled. The control timing of the primary side and the secondary side is as follows: Fig. 20 As shown. Fig. 20 Among them, t5 is the time length from the driving rising edge of Q9 and Q12 in the secondary side to the zero point of the resonant current, that is, the rising edge dead time of Q5 and Q8 in the primary side of the resonant circuit, t6 is the dead time of the driving falling edge of Q9 and Q12 in the secondary side and the driving falling edge of Q5 and Q8 in the primary side, and t7 is the time length from the driving rising edge of Q10 and Q11 in the secondary side to the zero point of the resonant current.

[0128] In a possible implementation manner, the charging control method may further include the following steps:

[0129] When the on-board charger is in the third working mode, the power factor correction circuit is subjected to dual-loop control of the bus voltage outer loop and the AC current inner loop, the resonant circuit is subjected to fixed-frequency open-loop control, and the primary side drive signal follows the secondary side drive signal.

[0130] In the present disclosure, when the on-board charger is in the third working mode, the power factor correction circuit can be subjected to dual-loop control of the bus voltage outer loop and the AC current inner loop, and the primary and secondary sides of the resonant circuit are controlled to operate according to a fourth preset frequency and a fourth preset duty cycle, that is, the primary and secondary sides of the resonant circuit are operated in a fixed frequency and fixed duty cycle manner, and the primary side drive signal follows the secondary side drive signal.

[0131] like Fig.16 As shown, based on the fourth preset duty cycle ( Fig.16 50% is used as an example) to generate a PWM signal, and based on the PWM signal, the primary side (i.e., Q5, Q6, Q7, and Q8) and the secondary side (i.e., Q9, Q10, Q11, and Q12) of the resonant circuit are controlled. The control timing of the primary side and the secondary side is as follows: Fig.21 shown.

[0132] The following is a detailed description of the specific implementation method of the dual-loop control of the bus voltage outer loop and the AC current inner loop of the power factor correction circuit. Specifically, it can be achieved through the following steps (c1) to (c3):

[0133] Step (c1): Obtain the AC side reference voltage, the AC side actual voltage, and the AC side actual current.

[0134] Step (c2): Determine the feedback current according to the deviation between the reference voltage on the AC side and the actual voltage on the AC side.

[0135] Step (c3): Control the switch action of the power factor correction circuit according to the feedback current and the actual current on the AC side.

[0136] like Fig. 22 As shown, the feedback current can be determined by the PI controller according to the deviation between the reference voltage Uac_ref on the AC side and the actual voltage Uac on the AC side; then, the SPWM signal is generated by the PI controller according to the feedback current and the actual current (-IL1) on the AC side, and the operation of the switch tubes (i.e., Q1, Q2, Q3, and Q4) of the power factor correction circuit is controlled according to the SPWM signal.

[0137] In addition, in order to reduce the bus ripple of the power factor correction circuit, the resonant circuit and the low-voltage side conversion circuit can be frequency-doubled, that is, the frequency of the switching tube of the low-voltage side conversion circuit is an integer multiple of the frequency of the switching tube of the resonant circuit.

[0138] For example, Fig.13 , Fig.17 , Fig. 20 , Fig.21 As shown, the frequency of the switching tube of the low-voltage side conversion circuit is twice the frequency of the switching tube of the resonant circuit.

[0139] In order to reduce the stress of the resonant circuit, the switch of the buck circuit can be turned on laterally. Specifically, Fig.13 and Fig.17 As shown, when the on-board charger is in the first working mode, the driving rising edge of the switch tube (i.e., Q15) of the buck circuit lags behind the driving rising edge of the primary side of the resonant circuit by a target time length (i.e., t1), and the driving rising edge of the switch tube of the buck circuit is synchronized with the driving rising edge of the secondary side of the resonant circuit, wherein the target time length is the time length from the driving rising edge of the primary side to the zero crossing point of the resonant current. Fig. 20 and 21As shown, when the on-board charger is in the second working mode or the third working mode, the driving rising edge of the switch tube (i.e., Q15) of the buck circuit lags behind the driving rising edge of the secondary side of the resonant circuit by a reference time length (i.e., t5), and the driving rising edge of the switch tube of the buck circuit is synchronized with the driving rising edge of the primary side of the resonant circuit, wherein the reference time length is the time length from the driving rising edge of the secondary side to the zero-crossing point of the resonant current.

[0140] Fig.23 It is a block diagram of a charging control device according to an exemplary embodiment. The charging control device 300 is applied to a vehicle charger, and the vehicle charger includes a power factor correction circuit, a bus capacitor, a resonant circuit, and a low-voltage side conversion circuit connected in sequence, wherein the power factor correction circuit is used to connect to the AC side, the resonant circuit is used to connect to the power battery, and the low-voltage side conversion circuit is used to connect to the low-voltage system;

[0141] The charging control device 300 includes:

[0142] The control module 301 is used to perform dual-loop control of the power outer loop and the AC current inner loop of the power factor correction circuit when the on-board charger is in the first working mode, perform fixed-frequency open-loop control on the resonant circuit, and make the secondary side drive signal of the resonant circuit follow the primary side drive signal of the resonant circuit, wherein the first working mode refers to a mode in which the AC side simultaneously supplies power to the power battery and the low-voltage system.

[0143] In the above technical solution, when the AC side simultaneously supplies power to the power battery and the low-voltage system (i.e., the on-board charger is in the first working mode), the power factor correction circuit of the on-board charger is controlled by the dual loop of the power outer loop and the AC current inner loop, and the resonant circuit is controlled by the fixed frequency open loop, and the secondary side drive signal of the resonant circuit follows the primary side drive signal of the resonant circuit. Since the secondary side drive signal of the resonant circuit follows the primary side drive signal of the resonant circuit, that is, when the on-board charger is in the first working mode, the secondary side of the resonant circuit is turned on, therefore, when the resonant current passes through the zero point, the power battery can reversely supplement the power factor correction circuit through the turned-on secondary side, so that even when the output power of the main circuit is small or unloaded, a high bus voltage of the power factor correction circuit can be maintained, thereby ensuring the power supply capacity of the auxiliary circuit under different load conditions (e.g., full load). The fixed frequency control of the resonant circuit can avoid the problem of insufficient power supply capacity of the auxiliary circuit caused by frequent operation of the primary side due to variable frequency control. In addition, only the current of the power factor correction circuit is controlled without voltage control, and the resonant circuit is open-loop controlled at a fixed frequency, which can simplify the control logic and eliminate the need for complex control hardware or software, thereby reducing vehicle costs. In addition, when the resonant current passes through the zero point, the power battery can reversely supplement the power factor correction circuit through the turned-on secondary side, thereby reducing the capacity requirements of the bus capacitor at the output end of the power factor correction circuit, reducing the capacitance of the bus capacitor, and achieving the purpose of using a smaller bus capacitor such as a film capacitor to replace the electrolytic capacitor.

[0144] Optionally, the charging control device 300 further includes:

[0145] A determination module, used to determine the charging voltage of the power battery;

[0146] The control module 301 includes:

[0147] A first determination submodule, configured to determine the primary duty cycle of the resonant circuit according to a deviation between a bus voltage reference value and an AC peak voltage and a first preset duty cycle if the charging voltage is less than a preset voltage threshold;

[0148] The first control submodule is used to control the primary side of the resonant circuit to operate according to a first preset frequency and the primary side duty cycle, and to control the secondary side of the resonant circuit to operate according to the first preset frequency and the first preset duty cycle.

[0149] Optionally, the first determining submodule includes:

[0150] A second determination submodule is used to determine an adjustment amount of the primary duty cycle of the resonant circuit according to a deviation between a bus voltage reference value and an AC peak voltage, wherein the adjustment amount is greater than or equal to zero and less than or equal to a preset adjustment amount threshold;

[0151] The third determining submodule is used to determine the difference between the first preset duty cycle and the adjustment amount as the primary duty cycle.

[0152] Optionally, the control module 301 further includes:

[0153] The second control submodule is used to control the primary side and the secondary side of the resonant circuit to operate according to a second preset frequency and a second preset duty cycle if the charging voltage is greater than or equal to the preset voltage threshold.

[0154] Optionally, the control module 301 includes:

[0155] An acquisition submodule, used to acquire the rated charging power of the power battery, the effective value of the voltage on the AC side, and the actual current on the AC side;

[0156] a fourth determination submodule, configured to determine a reference current according to the rated charging power and the effective value of the voltage;

[0157] The third control submodule is used to control the switch action of the power factor correction circuit according to the deviation between the reference current and the actual current.

[0158] Optionally, the low-voltage side conversion circuit comprises a current doubler circuit, a first capacitor and a step-down circuit connected in sequence, wherein the current doubler circuit is connected to the resonant circuit, and the step-down circuit is used to be connected to the low-voltage system;

[0159] The fourth determining submodule includes:

[0160] a fifth determining submodule, configured to determine a reference charging power according to the rated charging power, wherein the reference charging power is less than the rated charging power;

[0161] The sixth determination submodule is used to determine the ratio of the reference charging power to the effective value of the voltage as a reference current.

[0162] Optionally, the low-voltage side conversion circuit comprises a current doubler circuit and a voltage step-down circuit connected in series, wherein the current doubler circuit is connected to the resonant circuit, and the voltage step-down circuit is used to be connected to the low-voltage system;

[0163] The fourth determination submodule is used to determine the ratio of the rated charging power to the effective value of the voltage as a reference current.

[0164] Optionally, the control module 301 is also used to perform fixed-frequency open-loop control on the resonant circuit and make the primary drive signal follow the secondary drive signal when the on-board charger is in a second operating mode, and the second operating mode refers to a mode in which the power battery only supplies power to the low-voltage system.

[0165] Optionally, the control module 301 is also used to perform dual-loop control of the bus voltage outer loop and the AC current inner loop of the power factor correction circuit when the on-board charger is in the third operating mode, perform fixed-frequency open-loop control on the resonant circuit, and make the primary drive signal follow the secondary drive signal. The third operating mode refers to a mode in which the power battery simultaneously supplies power to the AC side and the low-voltage system.

[0166] Optionally, the frequency of the switch tube of the low-voltage side conversion circuit is an integer multiple of the frequency of the switch tube of the resonant circuit.

[0167] Optionally, the low-voltage side conversion circuit includes:

[0168] A current doubler circuit and a voltage step-down circuit connected in series; or

[0169] A current doubler circuit, a first capacitor and a voltage step-down circuit connected in sequence;

[0170] Among them, when the on-board charger is in the first working mode, the driving rising edge of the switch tube of the buck circuit lags behind the driving rising edge of the primary side of the resonant circuit by a target time length, and the driving rising edge of the switch tube of the buck circuit is synchronized with the driving rising edge of the secondary side of the resonant circuit. The target time length is the time length from the driving rising edge of the primary side to the zero crossing point of the resonant current.

[0171] Optionally, the bus capacitor is a film capacitor or a ceramic capacitor.

[0172] Regarding the charging control device in the above embodiment, the specific manner in which each module performs operations has been described in detail in the embodiment of the method, and will not be elaborated here.

[0173] The present disclosure also provides a computer program product, including a computer program, which implements the steps of the charging control method described in any embodiment of the present disclosure when the computer program is executed by a processor.

[0174] The present disclosure also provides a computer-readable storage medium having computer program instructions stored thereon, and when the program instructions are executed by a processor, the steps of the charging control method described in any embodiment of the present disclosure are implemented.

[0175] The present disclosure also provides a controller, comprising:

[0176] a first memory having a computer program stored thereon;

[0177] The first processor is used to execute the computer program in the first memory to implement the steps of the charging control method described in any embodiment of the present disclosure.

[0178] The present disclosure also provides a vehicle, comprising:

[0179] Power battery;

[0180] Low pressure system;

[0181] An on-board charger, wherein the on-board charger comprises a power factor correction circuit, a bus capacitor, a resonant circuit and a low-voltage side conversion circuit connected in sequence, the power factor correction circuit is used to connect to the AC side, the resonant circuit is used to connect to the power battery, and the low-voltage side conversion circuit is used to connect to the low-voltage system; and

[0182] The above-mentioned controller provided by the present disclosure.

[0183] Fig.24 6 is a block diagram of a vehicle 600 according to an exemplary embodiment. For example, the vehicle 600 may be a hybrid vehicle, a non-hybrid vehicle, an electric vehicle, a fuel cell vehicle, or other types of vehicles. The vehicle 600 may be an autonomous vehicle, a semi-autonomous vehicle, or a non-autonomous vehicle.

[0184] Reference Fig.24 , the vehicle 600 may include various subsystems, for example, an infotainment system 610, a perception system 620, a decision control system 630, a drive system 640, and a computing platform 650. The vehicle 600 may also include more or fewer subsystems, and each subsystem may include multiple components. In addition, each subsystem and each component of the vehicle 600 may be interconnected by wire or wireless means.

[0185] In some embodiments, the infotainment system 610 may include a communication system, an entertainment system, and a navigation system, among others.

[0186] The perception system 620 may include several sensors for sensing information about the environment around the vehicle 600. For example, the perception system 620 may include a global positioning system (the global positioning system may be a GPS system, or a Beidou system or other positioning systems), an inertial measurement unit (IMU), a laser radar, a millimeter wave radar, an ultrasonic radar, and a camera.

[0187] The decision control system 630 may include a computing system, a vehicle controller, a steering system, a throttle, and a braking system.

[0188] The drive system 640 may include components that provide powered motion for the vehicle 600. In one embodiment, the drive system 640 may include an engine, an energy source, a transmission system, and wheels. The engine may be one or a combination of an internal combustion engine, an electric motor, and an air compression engine. The engine is capable of converting energy provided by the energy source into mechanical energy.

[0189] Some or all functions of the vehicle 600 are controlled by a computing platform 650. The computing platform 650 may include at least one second processor 651 and a second memory 652, and the second processor 651 may execute instructions 653 stored in the second memory 652.

[0190] The second processor 651 may be any conventional processor, such as a commercially available CPU. The processor may also include a graphics processor (Graphic Process Unit, GPU), a field programmable gate array (Field Programmable Gate Array, FPGA), a system on chip (System on Chip, SOC), an application specific integrated circuit (Application Specific Integrated Circuit, ASIC) or a combination thereof.

[0191] The second memory 652 can be implemented by any type of volatile or non-volatile memory device or a combination thereof, such as static random access memory (SRAM), electrically erasable programmable read-only memory (EEPROM), erasable programmable read-only memory (EPROM), programmable read-only memory (PROM), read-only memory (ROM), magnetic memory, flash memory, magnetic disk or optical disk.

[0192] In addition to the instructions 653 , the second memory 652 may also store data, such as road maps, route information, and data such as the location, direction, and speed of the vehicle. The data stored in the second memory 652 may be used by the computing platform 650 .

[0193] In the embodiment of the present disclosure, the second processor 651 may execute instruction 653 to complete all or part of the steps of the above-mentioned charging control method.

[0194] The preferred embodiments of the present disclosure are described in detail above in conjunction with the accompanying drawings; however, the present disclosure is not limited to the specific details in the above embodiments. Within the technical concept of the present disclosure, a variety of simple modifications can be made to the technical solution of the present disclosure, and these simple modifications all fall within the protection scope of the present disclosure.

[0195] It should also be noted that the various specific technical features described in the above specific embodiments can be combined in any suitable manner without contradiction. In order to avoid unnecessary repetition, the present disclosure will not further describe various possible combinations.

[0196] In addition, various embodiments of the present disclosure may be arbitrarily combined, and as long as they do not violate the concept of the present disclosure, they should also be regarded as the contents disclosed by the present disclosure.

Claims

1. A charging control method, characterized in that: Applied to an on-board charger, the on-board charger comprises a power factor correction circuit, a bus capacitor, a resonant circuit and a low-voltage side conversion circuit connected in sequence, wherein the power factor correction circuit is used to connect to the AC side, the resonant circuit is used to connect to the power battery, and the low-voltage side conversion circuit is used to connect to the low-voltage system; The charging control method comprises: When the on-board charger is in the first working mode, the power factor correction circuit is subjected to dual-loop control of the power outer loop and the AC current inner loop, the resonant circuit is subjected to fixed-frequency open-loop control, and the secondary side drive signal of the resonant circuit follows the primary side drive signal of the resonant circuit, wherein the first working mode refers to a mode in which the AC side simultaneously supplies power to the power battery and the low-voltage system; Wherein, the charging control method further includes: Determining a charging voltage of the power battery; The performing fixed-frequency open-loop control on the resonant circuit comprises: If the charging voltage is less than a preset voltage threshold, the adjustment amount of the primary duty cycle of the resonant circuit is determined according to the deviation between the bus voltage reference value and the AC peak voltage, wherein the adjustment amount is greater than or equal to zero and less than or equal to a preset adjustment amount threshold; Determine the difference between the first preset duty cycle and the adjustment amount as the primary duty cycle of the resonant circuit; The primary side of the resonant circuit is controlled to operate according to a first preset frequency and the primary side duty cycle, and the secondary side of the resonant circuit is controlled to operate according to the first preset frequency and the first preset duty cycle.

2. The charging control method according to claim 1, characterized in that: The performing fixed-frequency open-loop control on the resonant circuit further includes: If the charging voltage is greater than or equal to the preset voltage threshold, the primary side and the secondary side of the resonant circuit are controlled to operate according to a second preset frequency and a second preset duty cycle.

3. The charging control method according to claim 1, characterized in that: The dual-loop control of the power factor correction circuit, namely, an outer power loop and an inner AC current loop, comprises: Obtaining the rated charging power of the power battery, the effective value of the voltage on the AC side, and the actual current on the AC side; Determining a reference current according to the rated charging power and the effective value of the voltage; The action of the switch tube of the power factor correction circuit is controlled according to the deviation between the reference current and the actual current.

4. The charging control method according to claim 3, characterized in that: The low-voltage side conversion circuit comprises a current doubler circuit, a first capacitor and a step-down circuit connected in sequence, wherein the current doubler circuit is connected to the resonant circuit, and the step-down circuit is used to be connected to the low-voltage system; The determining of the reference current according to the rated charging power and the effective value of the voltage includes: Determining a reference charging power according to the rated charging power, wherein the reference charging power is less than the rated charging power; The ratio of the reference charging power to the effective value of the voltage is determined as a reference current.

5. The charging control method according to claim 3, characterized in that: The low-voltage side conversion circuit comprises a current doubler circuit and a voltage step-down circuit connected in series, wherein the current doubler circuit is connected to the resonant circuit, and the voltage step-down circuit is used to be connected to the low-voltage system; The determining of the reference current according to the rated charging power and the effective value of the voltage includes: The ratio of the rated charging power to the effective value of the voltage is determined as a reference current.

6. The charging control method according to claim 1, characterized in that: The charging control method further includes: When the on-board charger is in the second working mode, the resonant circuit is controlled in a fixed-frequency open-loop manner, and the primary drive signal follows the secondary drive signal. The second working mode refers to a mode in which the power battery only supplies power to the low-voltage system.

7. The charging control method according to claim 1, characterized in that: The charging control method further includes: When the on-board charger is in the third working mode, the power factor correction circuit is subjected to dual-loop control of the bus voltage outer loop and the AC current inner loop, the resonant circuit is subjected to fixed-frequency open-loop control, and the primary drive signal follows the secondary drive signal. The third working mode refers to a mode in which the power battery supplies power to the AC side and the low-voltage system at the same time.

8. The charging control method according to any one of claims 1 to 7, characterized in that: The frequency of the switch tube of the low-voltage side conversion circuit is an integer multiple of the frequency of the switch tube of the resonant circuit.

9. The charging control method according to any one of claims 1 to 7, characterized in that: The low voltage side conversion circuit comprises: A current doubler circuit and a voltage step-down circuit connected in series; or A current doubler circuit, a first capacitor and a voltage step-down circuit connected in sequence; Among them, when the on-board charger is in the first working mode, the driving rising edge of the switch tube of the buck circuit lags behind the driving rising edge of the primary side of the resonant circuit by a target time length, and the driving rising edge of the switch tube of the buck circuit is synchronized with the driving rising edge of the secondary side of the resonant circuit. The target time length is the time length from the driving rising edge of the primary side to the zero crossing point of the resonant current.

10. The charging control method according to any one of claims 1 to 7, characterized in that: The bus capacitor is a film capacitor or a ceramic capacitor.

11. A computer-readable storage medium having a computer program stored thereon, characterized in that: When the computer program is executed by a processor, the steps of the charging control method according to any one of claims 1 to 10 are implemented.

12. A computer program product, characterized in that The invention comprises a computer program, which, when executed by a processor, implements the steps of the charging control method according to any one of claims 1 to 10.

13. A controller, characterized in that: include: a first memory having a computer program stored thereon; The first processor is used to execute the computer program in the first memory to implement the steps of the charging control method according to any one of claims 1 to 10.

14. A vehicle, characterized in that: include: Power battery; Low pressure system; An on-board charger, wherein the on-board charger comprises a power factor correction circuit, a bus capacitor, a resonant circuit and a low-voltage side conversion circuit connected in sequence, the power factor correction circuit is used to connect to the AC side, the resonant circuit is used to connect to the power battery, and the low-voltage side conversion circuit is used to connect to the low-voltage system; and A controller according to claim 13.

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