93 results about "Eta squared" patented technology

A method includes amplifying the plurality of received signals, generating a plurality of time domain samples of the amplified signals with at least an analog-to-digital converter (ADC), determining at least a candidate power according to root-mean-square (RMS) powers of a first group of symbols received at the receiver antennas, and setting the gain of the amplifier according to a selected candidate power with the processor. The received RMS power for one antenna is determined as the square root of the averaged product of each received symbol and its complex conjugate for all symbols of the first group. The candidate power can be determined considering a subgroup of antennas using an RMS value, an arithmetical mean value, or a geometric mean value of this subgroup.

A system and method for improved Time Of Arrival (TOA) distance measurements between nodes of a wireless ad-hoc network. Specifically, the present invention is a system and method of distance estimation using square-root raised-cosine pulse shaping and chip matched filters on direct sequence spreading waveforms, the multiplication of which produces raised-cosine filtered pulse responses. The responses are used to identify a time when a function is at a maximum, corresponding to the actual signal reception time. The system and method produces a raised-cosine filtered pulse response and an auto-correlation function based on a received signal. A peak value of the auto-correlation function is calculated based on a quadratic approximation, which is corrected using a signal sampling phase offset detected between the raised-cosine filtered pulse response and the calculated peak value. The calculated peak value is then corrected to represent an actual reception time for received signals.

The invention belongs to the seismic data processing and relates to a method by utilizing an equivalent N point smooth spectrum for the simulation of deconvolution. The implementation steps are that the seismic data is collected; the Fourier transform is made for the seismic data at a certain time window; a low pass filter operator of the time domain with an interception frequency of FE and a sampling rate of DT is calculated, which is taken as the equivalent N point smooth operator; FE and DT satisfy the equation that FE*DT is equal to X*DF*1.024; the estimate value of the amplitude spectrum of the seismic wavelet and the reverse wavelet are obtained, which are convoluted with the original seismic data; and the deconvolution seismic data of the time window is obtained. The single peak hypothesis is not applied for the amplitude spectrum of the seismic wavelet in the invention, which suits for complex amplitude spectrum of the seismic wavelet; compared with the least square polynomial fitting, the shape of the simulated amplitude spectrum curve of the seismic record is not affected by the global influence; the invention has the advantages of high calculation efficiency, better stability and improved resolution of seismic profiles.

The invention discloses an input saturation-considered unmanned surface vehicle full-state constraint trajectory tracking control method, relates to an unmanned surface vehicle control method, and aims at solving the problem that existing unmanned surface vehicle trajectory tracking control-oriented control methods do not process state constraint and saturation problems. According to the method, akinetic model of a 3-degree of freedom and multiple-input-multiple-output unmanned surface vehicle; a saturated closed-loop system is established and a self-adaptive method is selected to estimate squares of unknown interference upper limits and control input difference upper limits; and self-adaptive laws are designed for unknown interferences and control inputs according to the self-adaptive method, and a controller is designed according to a pseudo-inverse condition so as to control the unmanned surface vehicle. The method is suitable for the control of unmanned surface vehicles.

A method for estimating channel impulse response (CIR) in a communication system includes converting RF analog signals to obtain baseband digitized signals, sampling the baseband digitized signals according to the symbol period or bit period, cross-correlating at least part of the samples and a predetermined set of training sequence symbols, and calculating the ratio of the maximum square of the modulus (power) value and the second largest value among the outputs of the cross-correlations. If the ratio is larger than a first predetermined value, the method outputs the cross-correlation values as the CIR according to the time step index of the maximum power value, and if the ratio is not larger than the first predetermined value, the method calculates the energy of a predetermined window and outputs the cross-correlation values as the CIR according to the time step index of the maximum energy.

A method of measuring instantaneous signal-dependent nonlinear distortion in a system under test in response to a test signal having a varying frequency sinusoidal component, such as a swept frequency signal or a multi-burst signal, uses a time window to locate a frequency of interest in the corresponding varying frequency component of a signal output from the system under test. Once the location of the frequency of interest is located in the output signal, a spectrum of the portion of the output signal within the time window is generated and the magnitudes of the spectral peaks, including the spectral peak for the frequency of interest or nominal frequency and all isolated peaks representing distortion frequencies, are measured. The amount of distortion is calculated as a ratio of the square-root of the sum of the magnitudes of the distortion frequencies to the magnitude of the nominal frequency.

A first characteristic value extracting unit extracts a characteristic value from a picture transmitted from a transmission side, and a second characteristic value extracting unit extracts a characteristic value from a picture received on a reception side. These extracted characteristic values are supplied to a central monitoring unit through low speed lines, respectively. In the central monitoring unit, an MSE (mean square error) is assessed from the data by an MSE assessing unit. The first and second characteristic value extracting units divide an input picture into blocks, subject the blocks to an orthogonal transformation, or subject the blocks to PN sequence multiplication before the orthogonal transformation, and extract and output orthogonal transformation coefficients. The MSE assessing unit determines the differences between corresponding coefficients on the transmission side and the reception side and squares the differences, adds the squared differences for every coefficients or every blocks, and assess an MSE based on the added values referred to a table. With this operation, the MSE can be effectively assessed using a smaller amount of extracted data (accordingly, slower speed lines can be used in the central monitoring unit).

The present invention relates to an optical coherent receiver and an apparatus for and a method of monitoring performance thereof. The apparatus for monitoring performance of the optical coherent receiver makes use of a first signal and a second signal from the optical coherent receiver to monitor performance of the optical coherent receiver, and comprises a first subtracter, for subtracting the second signal from the first signal to obtain a first subtraction result; a squarer, for obtaining a square of the first subtraction result; a delayer, for delaying the first subtraction result; a multiplier, for multiplying the first subtraction result with the delayed first subtraction result; and a second subtracter, for subtracting the result of the multiplier from the result of the squarer.

An efficient method for solving a model predictive control problem is described. A large sparse matrix equation is formed based upon the model predictive control problem. The square root of H, Hr, is then formed directly, without first forming H. A square root (LSMroot) of a large sparse matrix of the large sparse matrix equation is then formed using Hr in each of a plurality of iterations of a quadratic programming solver, without first forming the large sparse matrix and without recalculating Hr in each of the plurality of iterations. The solution of the large sparse matrix equation is completed based upon LSMroot.

An efficient undeniable digital signature scheme based on a quadratic field is disclosed. Public keys (D, P, k, t) and secret keys (D1, q) are defined by generating two primes p, q (p, q>4, p=3 mod 4, √{square root over (p/3)}<q), computing D1=−p and D=D1q², obtaining a bit length k of √{square root over (|D1|)}/4 and a bit length t of q−(D1/q) where (D1/q) denotes Kronecker symbol, and generating a kernel element P of a map from a class group Cl(D) to a class group Cl(D1). Then the signature verification is realized by first checking whether a norm N(S) of the signature S is smaller than k bits or not, and judging that the signature S is illegal when the norm N(S) is larger than k bits, or generating a challenge C when the norm N(S) is not larger than k bits, by computing the message ideal M of the message m, generating a random integer r smaller than t bits, computing H=(M/S)^r, generating a random ideal B whose norm is smaller than k−1 bits, and computing the challenge C=BH, at a verifier side; then computing a response W by mapping the challenge C to the class group Cl(D1) and pulling the mapped challenge C back to the class group Cl(D) and squaring a result of mapping and pulling back, using the secret keys (D1, q), at the signer side; and then checking whether W=B² holds or not, and judging that the signature S is legal when W=B² holds or that the signature S is illegal otherwise, at the verifier side.

A method and apparatus are provided for generating a code by quickly computing a state of a Linear Feedback Shift Register (LFSR) in a mobile communication system, in which a code for the communication system is generated including an n-stage LFSR and operating in sleep mode and active mode set at a preset time interval from the sleep mode. Current state values of the LFSR are combined with n different mask patterns such that the current state values are shifted by {2⁰,2¹, . . . ,2ⁿ⁻¹}. A combination result is provided as a new state value of the LFSR at an arbitrary time variably set in the sleep mode. To transform a current state value of the LFSR to a new state value after an arbitrary time, the code generation method employs a square and multiply algorithm without use of mask patterns.

A method is disclosed for operating a synchronous space division multiple access, code division multiple access communications system. The method operates, within a coverage area of a base station (BS) or radio base unit (RBU) having a multi-element antenna array, for estimating a SSV for individual ones of a plurality of active subscriber stations (SSs) and assigns a spreading code to a subscriber station (SS) that minimizes the similarity of the determined SSVs of the SSs in a spreading code set. A metric used to measure the similarity of the spatial signature vectors of the SSs comprises the squared sum of the inner products of same code SSs' SSV with a current SS's SSV. The step of assigning includes calculating the magnitude of the squared inner product of the SSVs of all pairs of active SSs; using the calculated values for determining ξ_n(c) for each spreading code that is not already used some specified maximum number of times; and assigning to a SS the spreading code with a minimum ξ_n(c).

A non-linear correction current ICTAT2 (current complementary to the square of absolute temperature) is generated from a current IPTAT (current proportional to absolute temperature) and a current ICTAT (current complementary to absolute temperature), both modified in a circuit having a topology and components which capitalize on the logarithmic relationship between transistor collector current and base-emitter voltage. The resulting ICTAT2 current (current complementary to the square of absolute temperature) is injected into a node of a bandgap reference circuit to compensate for non-linear temperature effects on output voltage. A more general correction circuit generates both IPTAT2 and ICTAT2, and applies each to a respective multiplier which, in a preferred embodiment, is a current DAC configured as a multiplier. Control inputs CTL1 and CTL2 to respective multipliers set the amplitudes of the modified IPTAT2 and ICTAT2 output currents, which are then summed to generate the compensating current Icomp which is injected to the appropriate node in the bandgap reference circuit as described above. By adjusting the relative amplitudes of the IPTAT2 and ICTAT2 currents, a wide range of compensating current versus voltage curves is produced, allowing the optimization of a wide range of bandgap reference circuits. An optimal value for CTL1 is determined by holding CTL2 constant, then measuring curvature at a plurality of CTL1 values. That CTL1 value closest to the interpolated value at which curvature is minimized is then used.

The invention relates to a method for calculating a current reference value of a three-phase four-wire grid-connected voltage source type PWM rectifier. On the condition of unbalanced drop of grid voltage, the elimination of the active power fluctuation and the suppression of the direct current bus voltage fluctuation serve as the control target. According to the method, on the premise that the requirements of the control target are met, the maximum value in reference values of three-phase current amplitudes can be minimized simultaneously. The method comprises that firstly, three voltage sensors of the rectifier detect to obtain three-phase grid voltage ea, eb and ec, fundamental wave amplitudes Ea, Eb and Ec and fundamental wave phases phi a, phi b and phi c of the three-phase grid voltage can be obtained after processing by three single-phase phase-locked loop structures, and different current reference value calculation methods can be determined according to the criterion that whether the quadratic sum of any two phase amplitudes in grid voltage amplitudes is smaller than the square of the third phase amplitude.

This invention relates to an apparatus and a method for monitoring statistical characteristics of phase noises, as well as to a coherent optical communication receiver. The apparatus for monitoring statistical characteristics of phase noises comprises an argument calculating unit (203), for obtaining an argument of a signal input thereto; an unwrapping unit (204), for unwrapping the argument obtained by the argument calculating unit (203) to obtain a phase signal (205); a delaying unit (207), for delaying the phase signal; a differentiating unit (209), for obtaining a difference between a phase 10 signal currently obtained by the unwrapping unit (204) and a phase signal delayed by the delaying unit (207); a modulus squaring unit (210), for obtaining a square of the modulus of the difference; and an averaging unit (211), for averaging squares of moduli of a plurality of differences obtained by the modulus squaring unit (210) to obtain a mean-squared differential phase 15 (MSDP) value.

The invention discloses an estimation method of a four-wheeled independent drive electric automobile road adhesion coefficient. The method includes the steps: calculating vertical tire force of four wheels under a current vehicle driving state; calculating longitudinal tire force of the corresponding wheels under different road adhesion coefficients of current slipping rate; calculating current longitudinal tire force of the wheels; calculating a road friction coefficient; performing subtracting on the longitudinal tire force of the corresponding wheels under the different road adhesion coefficients of the current slipping rate and the current longitudinal tire force of the wheels, and taking a square; taking a minimum value of the difference square, judging the road adhesion coefficient corresponding to the minimum value as a current road adhesion coefficient, comparing the current road adhesion coefficient with the road friction coefficient, and taking a maximum value between the current road adhesion coefficient with the road friction coefficient; updating an estimation value of the current road adhesion coefficient if the duration time of an estimation value of the changed roadadhesion coefficient is longer than 0.5 second; keeping invariability of an estimation value of the road adhesion coefficient of previous moment. The method can be used for adjustment of drive anti-skid strategies, and the driving performance of a vehicle is improved.

Two linear quadratic tracking controllers and a minimal prototype controller are presented for the control of a discrete single input and single output (SISO) tracking control system. The minimal prototype controller is an unconstrained controller. Depending on the models of the set point and the plant transfer function, this controller might be desirable. But usually one would choose one of the two linear quadratic controllers which minimize the sum of squared errors between the output and the set point variables with a penalty on that of the input variable. The one degree of freedom (1-DOF) controller performs well, but for nonminimum phase systems the two and a half degrees of freedom (2.5-DOF) controller is the stronger one as it can suppress the inverse response of a non-minimum phase system. The 1-DOF controller gives the stochastic regulating controller counterpart known as the linear quadratic Gaussian controller. A digital control chip for implementation of the controllers is also disclosed.

A method for detecting a cyclostationary signal in a signal to be analyzed, received from a transmitter by a receiver or read from a recording medium by a reader device. According to this method, the value of a discrimination function J is estimated, expressed as a quadratic form of the cyclic correlation coefficients of the signal to be analyzed for a set (I*_M) of non-zero time shifts and a set (I_K) of cyclic frequencies, and the value

is compared with a wrong detection rate η in order to determine whether said cyclostationary signal is present in the signal to be analyzed, wherein γ(ν,x) is the normalized lower incomplete gamma function, ν is the product of the cardinal (M) of said set of non-zero time shifts and of the cardinal (K) of said set of cyclic frequencies, U is the width of the autocorrelation window on which the cyclic correlation coefficients are calculated, and σ⁴ is the square of the noise variance.

The invention discloses a kinematics-based five-axis numerical control machining tool attitude planning method, which comprises the steps of: defining a tool axis vector as a vector description of a tool axis direction in a workpiece coordinate system; adopting variations of a tool axis vector v at a tool location point P<L, i>, and tool axis vectors v<i-1> and v<i+1> at tool location points P<L, i-1> and P<L, i+1> adjacent to the tool location point P<L,i> on the same tool path as metrics of the vector description; specifically adopting a value obtained through extracting root of a sum ofsquares of included angles between the adjacent tool axis vectors as metric indexes; and establishing a tool axis vector integral smoothing model considering kinematics space mapping based on a universal structure machine tool kinematics model and tool axis vector smoothing metric indexes, and completing tool attitude planning method. The kinematics-based five-axis numerical control machining toolattitude planning method greatly improves the machining precision and machining efficiency of the multi-axis numerical control machine tool, reduces interference between the tool and the workpiece, and prevents the occurrence of accidents.